STEL-1175+125/CM - Intel - Datasheet.Live

STEL-1175

Data Sheet

STEL-1175+125

(125 MHz)

32-Bit Resolution CMOS

Phase Modulated

Numerically

Controlled Oscillator

STEL-1175+125 2

■■

■VERY HIGH CLOCK FREQUENCY

- 125 MHz MAXIMUM OVER FULL

MILITARY TEMPERATURE RANGE

■■

■HIGH FREQUENCY RESOLUTION

- 32-BITS, 30 milli-Hz @ 125 MHz

■■

■WIDE OUTPUT BANDWIDTH

- 0 TO 50 MHz @ 125 MHz CLOCK

■■

■SHORT CLOCK TO OUTPUT DELAY FOR

DIRECT CLOCK CONNECT TO 1175 AND

DAC

■■

■PRECISION PHASE MODULATION

- 12-BITS, 0.09° RESOLUTION, CAN BE

USED FOR LINEAR PM OR PULSE-

SHAPED PSK

■■

■SINE OR COSINE SIGNAL GENERATION

- 12-BIT OUTPUTS

■■

■HIGH SPECTRAL PURITY

ALL SPURS < -75 dBc

(AT DIGITAL OUTPUT)

■■

■MICROPROCESSOR COMPATIBLE

INPUTS

■■

■LOW POWER DISSIPATION

■■

■68 PIN PLCC PACKAGE

(COMMERCIAL TEMPERATURE RANGE)

■■

■68 PIN CERAMIC LCC PACKAGE

(MILITARY TEMPERATURE RANGE)

TYPICAL APPLICATIONS

■■

■FREQUENCY SYNTHESIZERS

■■

■PSK MODULATORS

■■

■DIGITAL SIGNAL PROCESSORS

■■

■FAST HOPPED FREQUENCY SOURCES

FUNCTIONAL DESCRIPTION

The STEL-1175 Modulated Numerically Controlled

Oscillator (MNCO) uses digital techniques to provide a

cost-effective solution for low noise signal sources. The

device can operate at clock frequency up to 125 MHz and

provides high frequency resolution and high spectral purity

of outputs up to 50 MHz. The STEL-1175 also features

phase modulation at rates up to 25% of the clock

frequency. The 12-bit output can be selected to be a sine

or cosine function, so that two STEL-1175 NCOs can be

used to generate quadrature signals with independent

phase modulation. Two independent frequency control

registers are provided, allowing high speed frequency

hopping or binary FSK at rates to 25% of the clock

frequency. The device combines low power 0.5µ CMOS

technology with a unique architectural design resulting in

a power efficient, high-speed sinusoidal waveform

generator able to achieve fine tuning resolution and high

spectral purity at clock frequencies up to 125 MHz. The

NCO is designed to provide a simple interface to an 8-bit

microprocessor bus.

BLOCK DIAGRAM

PHLCK

PHLD

PHASE

MOD

CONTROL

PHSEL

FRLD

ADDRESS

SELECT

LOGIC

ADDR

CSEL

WRSTB

∆-PHASE

BUFFER

REGISTERS

DATA 8

FRSEL

CLOCK

SINE

MUX

32 ∆-PHASE

32-BIT

PHASE

ACCUMU-

LATOR

PHASE

ALU

12 PSYNC

SIN/COS

LUT

PHASE

OUTPUT

12 PHASE

12 OUT

COUT

FSYNC

TCP 39074-12/17/98

CIN

ROUND

RESET TO ALL REGISTERS

FEATURES

3STEL-1175+125

PIN CONNECTIONS

1 PHASE1

2 PHASE2

3 PHASE3

4 PHASE4

5 PHASE5

6 DATA0

7 DATA1

8 DATA2

9 DATA3

10 DATA4

11 DATA5

12 DATA6

13 DATA7

14 PHASE6

15 PHASE7

16 PHASE8

17 PHASE9

18 PHASE10

19 PHASE11

20 WRSTB

21 PHSEL

22 I.C.

23 RESET

24 ROUND

25 SINE

26 FRSEL

27 VDD

28 VSS

29 FRLD

30 COUT

31 CSEL

32 PHLD

33 PHCLK

34 VSS

35 VDD

36 OUT0(LSB)

37 OUT1

38 OUT2

39 OUT3

40 OUT4

41 N.C.

42 VSS

43 VDD

44 OUT5

45 OUT6

46 OUT7

47 OUT8

48 OUT9

49 OUT10

50 OUT11

51 VSS

52 VDD

53 N.C.

54 N.C.

55 N.C.

56 FSYNC

57 PSYNC

58 ADDR0

59 VSS

60 VDD

61 ADDR1

62 ADDR2

63 ADDR3

64 CLOCK

65 CIN

66 VDD

67 VSS

68 PHASE0

Notes: 1. I.C. denotes Internal Connection. These pins must be left unconnected. Do not use for vias.

2. Connect all unused inputs to Vss, leave unused outputs unconnected.

Package: 68 pin PLCC

Thermal coefficient, θja = 35°/W

Package: 68 pin CLDCC

Thermal coefficient, θja = 34°C/W

PIN CONFIGURATION

The NCO maintains a record of phase which is accurate to

32 bits. At each clock cycle, the number stored in the 32-

bit ∆-Phase register is added to the previous value of the

phase accumulator. The number in the phase accumulator

represents the current phase of the synthesized sine and

cosine functions. The number in the ∆-Phase register

represents the phase change for each cycle of the clock.

This number is directly related to the output frequency by

the following:

fc x ∆∆

∆∆

∆-Phase

fo=232

where: fo is the frequency of the output signal

and: fc is the clock frequency.

The sine and cosine functions are generated from the 13

most significant bits of the phase accumulator. The

frequency of the NCO is determined by the number stored

in the ∆-Phase Register, which may be programmed by an

8-bit microprocessor.

The NCO generates a sampled sine wave where the

sampling function is the clock. The practical upper limit of

the NCO output frequency is about 40% of the clock

frequency due to spurious components that are created by

sampling. Those components are at frequencies greater

than half the clock frequency and can be removed by

filtering.

The phase noise of the NCO output signal may be

determined from the phase noise of the clock signal input

and the ratio of the output frequency to the clock

STEL-1175+125 4

MUX BLOCK

This block is used to select which ∆-Phase Buffer Register

is used as the source of frequency data for the ∆-Phase

∆∆

∆-PHASE REGISTER BLOCK

This block controls the updating of the ∆-Phase word used

in the Accumulator. The frequency data from the Mux

Block is loaded into this block after a falling edge on the

FRLD input. This block also generates the FSYNC

output, which indicates the instant at which any frequency

change made at the inputs affects the OUT11-0 signals.

PHASE ACCUMULATOR BLOCK

This block forms the core of the NCO function. It is a

high-speed, pipelined, 32-bit parallel accumulator,

generating a new sum in every clock cycle. A carry input

(the CIN input) allows the resolution of the accumulator

to be expanded by means of an auxiliary NCO or phase

accumulator. The overflow signal is discarded (and is

available at the COUT pin), since the required output is

the modulo(232) sum only. This represents the modulo(2þ)

phase angle.

PHASE ALU BLOCK

The Phase ALU performs the addition of the PM data to

the Phase Accumulator output. The PM data word is 12

bits wide, and this is added to the 13 most significant bits

from the Phase Accumulator to form the modulated phase

used to address the lookup table. This block also generates

the PSYNC output, which indicates the instant at which

any phase change made at the inputs affects the OUT11-0

signals.

SINE/COSINE LOOKUP TABLE BLOCK

This block is the sine/cosine memory. The 13 bits from

the Phase ALU are used to address this memory to

generate the 12-bit OUT11-0 outputs. The output will be a

sine signal when the SINE input is high, and will be a

cosine signal when this input is low.

PHASE OUTPUT REGISTER BLOCK

The twelve most significant bits from the Phase ALU

Block are latched into the Phase Output Register on the

rising edges of the PHCLK input. The output of this

INPUT SIGNALS

RESET

The RESET input is asynchronous and active low, and

clears all the registers in the device. When RESET goes

low, all registers are cleared within 20 nsecs, and normal

operation will resume after this signal returns high. The

data on the OUT11-0 bus will then be invalid for 6 rising

frequency. This ratio squared times the phase noise power

of the clock specified in a given bandwidth is the phase

noise power that may be expected in that same bandwidth

relative to the output frequency.

The NCO achieves its high operating frequency by making

extensive use of pipelining in its architecture. The pipeline

delays within the NCO represent 19 clock cycles. The dual

∆-Phase registers used in the STEL-1175 allow the

frequency to be updated as rapidly as every fourth clock

cycle, i.e. at 25% of the clock frequency. The pipeline delay

associated with the phase modulator is only 12 clock cycles,

since the phase modulating function is at the output of the

accumulator. The phase modulation may also be changed

as rapidly as every fourth clock cycle, at 25% of the clock

frequency, resulting in a maximum modulation rate of 30

MHz with a clock frequency of 125 MHz. Note that when

a phase or frequency change occurs at the output the

change is instantaneous, i.e., it occurs in one clock cycle,

with complete phase coherence.

FUNCTION BLOCK DESCRIPTION

ADDRESS SELECT LOGIC BLOCK

This block controls the writing of data into the device via

the DATA7-0 inputs. The data is written into the device on

the rising edge of the WRSTB input, and the register into

which the data is written is selected by the ADDR3-0 inputs.

The CSEL input can be used to selectively enable the

writing of data from the bus.

PHASE MODULATION CONTROL BLOCK

This block includes the Phase Modulation Buffer Register

and controls the source of the phase modulation (PM) data

by means of the PHSEL input. When this signal is low,

data from the DATA7-0 and ADDR3-0 inputs is written

directly into the Phase ALU after a falling edge on the

PHLD input. When PHSEL is high, data is written into

the Phase Modulation Buffer Register from the DATA7-0

bus on the rising edge of the WRSTB input. The data will

then be transferred into the Phase ALU after the next

falling edge of PHLD. The source of the PM data applied

to the Phase ALU will be the Phase Buffer Register in this

mode.

∆∆

∆-PHASE BUFFER REGISTERS A & B BLOCK

The two ∆-Phase Buffer Registers are used to temporarily

store the ∆-Phase data written into the device. This allows

the data to be written asynchronously as four bytes per 32-

bit ∆-Phase word. The data is transferred from these

registers into the ∆-Phase Register after a falling edge on

the FRLD input.

5STEL-1175+125

clock edges, and thereafter will remain at the value

corresponding to zero phase (801H) until new frequency

or phase modulation data is loaded with the FRLD or

PHLD inputs after the RESET returns high.

CLOCK

All synchronous functions performed within the NCO are

referenced to the rising edge of the CLOCK input. The

CLOCK signal should be nominally a square wave at a

maximum frequency of 125 MHz. A non-repetitive

CLOCK waveform is permissible as long as the minimum

duration positive or negative pulse on the waveform is

always greater than 4 nanoseconds.

CSEL

The Chip Select input is used to control the writing of

data into the chip. It is active low. When this input is high

all data writing via the DATA7-0 bus is inhibited.

DATA7 through DATA0

The 8-bit DATA7-0 bus is used to program the two 32-bit

∆-Phase Registers and the 12-bit Phase Modulation

data programmed into the ∆-Phase registers in this way

determines the output frequency of the NCO.

ADDR3 through ADDR0

The four address lines ADDR3-0 control the use of the

DATA7-0 bus for writing frequency data to the ∆-Phase

Buffer Registers, and phase data to the Phase Buffer

ADDR3ADDR1ADDR0Register Field

000∆-Phase Bits 7 0(LSB)

001∆-Phase Bits15  8

010∆-Phase Bits 23  16

011∆-Phase Bits 31  24

1 0 0 Phase Bits 3* 0(LSB)

1 0 1 Phase Bits 11*  4

ADDR3ADDR2Register Selected

00 ∆-Phase Buffer Register 'A'

01 ∆-Phase Buffer Register 'B'

1 X Phase Buffer Register

* Note: The Phase Buffer Register is a 12-bit register.

When the least significant byte of this register is selected

(ADDR3-0 =1X00), DATA7-4 is written into Bits 30 of

the register. In all cases, it is not necessary to reload

unchanged bytes, and the byte loading sequence may be

random.

WRSTB

The Write Strobe input is used to latch the data on the

DATA7-0 bus into the device. On the rising edge of the

WRSTB input, the information on the 8-bit data

bus is transferred to the buffer register selected by the

ADDR3-0bus.

FRSEL

The Frequency Register Select line controls the mux

which selects the ∆-Phase Buffer Register in use. When

this signal is high ∆-Phase Buffer Register 'A' is selected as

the source for the ∆-Phase Register, and the frequency

corresponding to the data stored in this register will be

generated by the NCO after the next FRLD command.

When this line is low, ∆-Phase Buffer Register 'B' is

selected as the source.

FRLD

The Frequency Load input is used to control the transfer

of the data from the ∆-Phase Buffer Registers to the ∆-

Phase Register. The data at the output of the Mux Block

must be valid during the clock cycle following the falling

edge of FRLD. The data is then transferred during the

subsequent cycle. The frequency of the NCO output will

change 19 rising clock edges after the FRLD command

due to pipelining delays.

PHSEL

The Phase Source Select input selects the source of data

for the Phase ALU. When it is high the source is the Phase

Buffer Register. It is loaded from the DATA7-

0 bus by setting address line ADDR3 high, as shown in the

tables. When PHSEL is low, the sources for the phase

modulation data are the DATA7-0 and ADDR3-0 inputs,

and the data will be loaded independently of the states of

WRSTB and CSEL. The data on these 12 inputs is

presented directly as a parallel 12-bit word to the Phase

ALU, allowing high-speed phase modulation. The 12-bit

value is latched into the Phase ALU by means of the PHLD

input. The data on the ADDR3-0 lines is mapped onto Phase

Bits 3 to 0 and the data on the DATA7-0 lines are mapped

onto Phase Bits 11 to 4 in this case. When using the parallel

phase load mode CSEL and/or WRSTB should remain

high to ensure that the phase data is not written into the

phase and frequency buffer registers of the STEL-1175.

PHLD

The Phase Load input is used to control the latching of

the Phase Modulation data into the Phase ALU. The 12-

bit data at the output of the Phase Modulation Control

Block must be valid during the clock cycle following the

falling edge of PHLD. The data is then transferred during

the subsequent cycle. The 12-bit phase data is added to the

12 most significant bits of the accumulator output, so that

the MSB of the phase data represents a 180° phase change.

The source of this data will be determined by the state of

STEL-1175+125 6

PHSEL. The phase of the NCO output will change 12

rising clock edges after the PHLD command, due to

pipeline delays.

CIN

The Carry Input is an arithmetic carry to the least

significant bit of the Phase Accumulator. Normal

operation of the NCO requires that CIN be set at a logic

0. When CIN is set at a logic 1 the effective value of the

Ð-Phase register is increased by one. This allows the

resolution of the accumulator to be expanded for higher

frequency resolution by connecting the COUT pin of the

lower order NCO to this input.

SINE

When the SINE input signal is set low the output signal

appearing on the OUT pin will be a cosine function and

when it is set high the DDS output will be a sine function.

After a reset the device will always start at a phase angle of

zero, irrespective of the status of the SINE input. In this

way, by using two devices, one set in the sine mode and

the other set in the cosine mode, quadrature outputs may

be obtained. The quadrature phase relationship of the two

outputs will be maintained at all times provided the two

devices are operated from common RESET, FRLD and

CLOCK signals. The use of phase modulation will, of

course, modify this relationship, unless the devices are also

phase modulated together.

ROUND

The ROUND input controls the precision of the

OUT11-0 output. When the ROUND input is set high, the

sine or cosine signals appearing on the OUT11-0 bus are

accurate to 12 bits. In some instances it may be desirable

to use only the 8 MSBs of this output. In such

circumstances the signals appearing on the OUT11-0 bus

can be rounded to present a more accurate 8-bit

representation of the signal on OUT11-4 by setting the

ROUND input low.

PHCLK

The register at the PHASE11-0 outputs allow the data

appearing on these lines to be strobed and frozen on the

rising edges of the Phase Clock input. For continuous

operation the PHCLK line and the CLOCK line should

be tied together. When the PHASE11-0 outputs are not

used PHCLK should be set low.

OUTPUT SIGNALS

OUT11-0

The signal appearing on the OUT11-0 output bus is derived

from the 13 most significant bits of the Phase

Accumulator. The 12-bit sine or cosine function is

presented in offset binary format. When the phase

modulation is zero and the SINE input is set high, the

value of the output for a given phase value follows the

relationship:

OUT11-0=2047 x sin (360 x (phase+0.5)/8192)°+2048

The result is accurate to within 1 LSB. When the phase

accumulator is zero, e.g., after a reset, the decimal value of

the output is 2049 (801H). However, when ROUND is

set low, the value appearing on the OUT11-0 output will be

rounded and will follow the relationship:

OUT11-4=127 x sin (360 x (phase+0.5)/8192)°+128

The data appearing on the OUT3-0 outputs will not be

meaningful under these circumstances.

When the phase modulation is zero and the SINE input is

set low, the value of the output for a given phase value

follows the relationship:

OUT11-0=2047 x cos (360 x (phase+0.5)/8192)°+2048

The result is accurate to within 1 LSB. When the phase

accumulator is zero, e.g., after a reset, the decimal value of

the output is 4095 (FFFH). However, when ROUND is

set low, the value appearing on the OUT11-0 outputs will

be rounded and will follow the relationship:

OUT11-4=127 x cos (360 x (phase+0.5)/8192)°+128

The data appearing on the OUT3-0 output will not be

meaningful under these circumstances.

PHASE11-0

The 12 MSBs of the Phase ALU output are available on

the PHASE11-0 lines. This signal is clocked on the rising

edges of the PHCLK line.

COUT

Each time the value of the phase accumulator exceeds the

maximum value that can be represented by a 32 bit number

the Carry Out signal goes high for one clock cycle.

FSYNC

The Frequency Sync output indicates the instant in time

when a frequency change made at the inputs affects the

OUT11-0 signals. The normally high FSYNC output goes

low for one clock cycle 18 clock cycles after an FRLD

command to indicate the end of the pipeline delay and the

start of the new steady state condition.

PSYNC

The Phase Sync output indicates the instant in time when

a phase change made at the inputs affects the OUT11-0

signals. The normally high PSYNC output goes low for

one clock cycle 11 clock cycles after a PHLD command,

to indicate the end of the pipeline delay and the start of the

new steady state condition.

7STEL-1175+125

ELECTRICAL CHARACTERISTICS

ABSOLUTE MAXIMUM RATINGS

Warning: Stresses greater than those shown below may cause permanent damage to the device.

Exposure of the device to these conditions for extended periods may also affect device reliability.

All voltages are referenced to VSS.

Symbol Parameter Range Units

Tstg Storage Temperature 40 to +125 °C (Plastic package)

65 to +150 °C (Ceramic package)

VDDmax Supply voltage on VDD 0.3 to + 7 volts

VI(max) Input voltage 0.3 to VDD + 0.3 volts

IiDC input current ± 10 mA

RECOMMENDED OPERATING CONDITIONS

Symbol Parameter Range Units

VDD Supply Voltage +5 ± 5% Volts (Commercial)

+5 ± 10% Volts (Military)

TaOperating Temperature (Ambient) 0 to +70 °C (Commercial)

55 to +125 °C (Military)

D.C. CHARACTERISTICS (Operating Conditions: VDD= 5.0 V ±5%, VSS = 0 V, Ta= 0° to 70° C, Commercial

VDD= 5.0 V ±10%, VSS = 0 V, Ta = 55° to 125°C,Military)

Symbol Parameter Min. Typ. Max. Units Conditions

IDD(Q) Supply Current, Quiescent 1.0 m A Static, no clock

IDD Supply Current, Operational 3.0 mA/MHz

VIH(min) High Level Input Voltage

Standard Operating Conditions 2.0 volts Logic '1'

Extended Operating Conditions 2.25 volts Logic '1'

VIL(max) Low Level Input Voltage 0.8 volts Logic '0'

IIH(min) High Level Input Current 10 35 110 µ A CIN and CSEL, VIN = VDD

IIH(min) High Level Input Current 10 µ A All other inputs, VIN = VDD

IIL(max) Low Level Input Current 10 µ A CIN and CSEL, VIN = VSS

IIL(max) Low Level Input Current 15 45 130 µ A All other inputs, VIN = VSS

VOH(min) High Level Output Voltage 2.4 4.5 volts IO = 8.0 mA

VOL(max) Low Level Output Voltage 0.2 0.4 volts IO = +8.0 mA

IOS Output Short Circuit Current 20 65 130 m A VOUT = VDD, VDD = max

10 45 130 m A VOUT = VSS, VDD = max

CIN Input Capacitance 2 pF All inputs

COUT Output Capacitance 4 pF All outputs

{

STEL-1175+125 8

NCO RESET SEQUENCE

NCO FREQUENCY CHANGE SEQUENCE

DATA 7-0

OUT 11-0

FRLD

FSYNC

CLOCK

WRSTB

CSEL

ADDR 3-0 DON'T CARE DON'T CARE

DON'T CARE

19 CLOCK

EDGES

OLD FREQUENCY NEW FREQUENCY

DON'T CARE

tSU

tHD tWR

tCH tCL

tSU

tCD

RESET

CLOCK

OUT 11-0 801 H

NOT VALID

12345

6 CLOCK

EDGES

tRS

tSR

9STEL-1175+125

NCO PHASE CHANGE SEQUENCE

1. PHSEL=0. DIRECT LOADING.

ADDR 3-0

DATA 7-0

OUT 11-0

PHLD

PSYNC

CLOCK

DON'T CARE

12 CLOCK EDGES

OLD PHASE NEW PHASE

DON'T CARE

tSU

tHD

tSU

ELECTRICAL CHARACTERISTICS

A.C. CHARACTERISTICS (Operating Conditions: VDD= 5.0 V ±5%, VSS = 0 V, Ta= 0° to 70° C, Commercial

VDD= 5.0 V ±10%, VSS = 0 V, Ta = 55° to 125° C, Military)

tRS RESET pulse width

tSR RESET to CLOCK Setup

tSU DATA, ADDR or CSEL

to WRSTB or PHLD Setup,

and FRLD or PHLD to

CLOCK Setup

tHD DATA, ADDR or CSEL

to WRSTB or PHLD Hold,

and DATA and ADDR

to CLOCK Hold

tCH CLOCK high

tCL CLOCK low

tWWRSTB, FRLD or PHLD

pulse width

tCD CLOCK to output delay

3 3 nsec.

3 4 nsec. fCLK = 125 MHz

3 5 nsec.

3626 nsec. Load = 15 pF

STEL-1175+125

(Commercial) (Military)

Symbol Parameter Min. Max. Min. Max. Units Conditions

3 3 nsec.

2 3 nsec.

10 25 nsec.

STEL-1175+125 10

NCO PHASE CHANGE SEQUENCE

2. PHSEL=1. BUS LOADING.

WRSTB

ADDR 3-0

DATA 7-0

OUT 11-0

PHLD

PSYNC

CLOCK

CSEL

DON'T CARE DON'T CARE

DON'T CARE

12 CLOCK

EDGES

OLD PHASE NEW PHASE

DON'T CARE

tSU

tHD tWR

tSU

HIGH-SPEED FREQUENCY CHANGE

The frequency of the STEL-1175 NCO can be changed as

rapidly as 25% of the clock frequency. This is done by

synchronizing the writing to the two ∆-Phase Buffer

Registers, and updating both every eight clock cycles. The

timing for this procedure is shown below. Each ∆-Phase

Buffer Register is loaded while the contents of the other

are being transferred into the ∆-Phase Register. The

sequence for a load cycle begins on the rising edge of the

clock following a falling edge of FRLD. In the diagram on

page 11, ∆-Phase Buffer Register A is being loaded in

cycles 1 through 4, while the contents of ∆-Phase Buffer

during the falling edge of FRLD. The reverse process

happens during cycles 5 through 8, and the process then

repeats starting in cycle 9. The FRLD signal can be used

to clock a bistable latch to generate the FRSEL signal.

The maximum update rate is 25%.

11 STEL-1175+125

The sine or cosine signals generated by the STEL-1175

have 12 bits of amplitude resolution and 13 bits of phase

resolution which results in spurious levels which are

theoretically at least 75 dB down. The highest output

frequency the NCO can generate is half the clock

frequency (fc/2), and the spurious components at

frequencies greater than fc/2 can be removed by filtering.

SPECTRAL PURITY

In many applications the NCO is used with a digital to

analog converter (DAC) to generate an analog waveform

which approximates an ideal sinewave. The spectral purity

of this synthesized waveform is a function of many

variables including the phase and amplitude quantization,

the ratio of the clock frequency to output frequency, and

the dynamic characteristics of the DAC.

HIGH-SPEED FREQUENCY CHANGE

USING THE STEL-1175

IN A HIGH-SPEED

PHASE MODULATOR

By routing the data and address

lines from the microcontroller via

2:1 multiplexers (e.g. 74HC157)

the MNCO can be set up from the

microcontroller and then phase

modulated at high-speed from an

external source. The PHSEL line

should be set to a logic 0 to enable

this mode of operation. The

system shown modulates all 12

bits. In a typical PSK system only

1 to 4 bits of modulation will be

used, simplifying the system

considerably.

APPLICATIONS INFORMATION

FRLD

CLOCK

WRSTB

ADDR

FRSEL

0100 0101 011000110000 0001 0010

123456789

0111 0000

0111

WBP 54815.c-11/20/98

A/B

WRITE WRSTB

FRLD

A/B

STEL-1175

MNCO

FREQ. LOAD

DATA0-7

ADDR0-3

PHASE0-11

FREQ. /PH SEL

PHASE LOAD

FROM

PHASE

MOD.

FROM

µC

PHLD

STEL-1175+125 12

As the output frequency fo of the NCO approaches fc/2,

the "image" spur at fc fo (created by the sampling process)

also approaches fc/2 from above. If the programmed

output frequency is very close to fc/2 it will be virtually

impossible to remove this image spur by filtering. For this

reason, the maximum practical output frequency of the

NCO should be limited to about 40% of the clock

frequency.

A spectral plot of the NCO output after conversion with a

DAC (Sony CX20202A-1) is shown below. In this case,

the clock frequency is 60 MHz and the output frequency is

programmed to 6.789 MHz. This 10-bit DAC gives better

performance than any of the currently available 12-bit

DACs at clock frequencies higher than 10 or 20 MHz.

The maximum non-harmonic spur level observed over the

entire useful output frequency range in this case is 74

dBc. The spur levels are limited by the dynamic linearity of

the DAC. It is important to remember that when the

output frequency exceeds 25% of the clock frequency, the

second harmonic frequency will be higher than the Nyquist

frequency, 50% of the clock frequency. When this

happens, the image of the harmonic at the frequency fc

2fo, which is not harmonically related to the output signal,

will become intrusive since its frequency falls as the output

frequency rises, eventually crossing the fundamental

output when its frequency crosses through fc/3. It would

be necessary to select a DAC with better dynamic linearity

to improve the harmonic spur levels. (The dynamic

linearity of a DAC is a function of both its static linearity

and its dynamic characteristics, such as settling time and

slew rates.) At higher output frequencies the waveform

produced by the DAC will have large output changes from

sample to sample. For this reason, the settling time of the

DAC should be short in comparison to the clock period.

As a general rule, the DAC used should have the lowest

possible glitch energy as well as the shortest possible

settling time.

TYPICAL SPECTRUM

Center Frequency: 6.7 MHz

Frequency Span: 10.0 MHz

Reference Level: 5 dBm

Resolution Bandwidth: 1 KHz

Video Bandwidth: 3 kHz

Scale: Log, 10 dB/div

Output frequency: 6.789 MHz

Clock frequency: 60 MHz

13 STEL-1175+125

Care must be taken in interfacing the STEL-1175 with

the DAC. The clock to output delay in the STEL-1175 is

typically 4 nS, but does change with processing variations,

voltage, temperature, and loading. The circuit design must

take this delay into account so that the input to the DAC is

stable at the instant it is clocked into the DAC. The hold

time of the DAC must be less than the minimum clock to

output delay. The set-up time of the DAC must be less

than the clock period minus the maximum clock to output

delay.

STEL-1175 TO DAC INTERFACE

TYPICAL SCHEMATIC DIAGRAM

For example, for 125 MHz, the set-up of the DAC must

be less than 2 nS and the hold time less than 2 nS. For 80

MHz operation, the set-up time of the DAC must be less

than 6.5 nS and the hold time less than 2 nS. This allows

operation with most commercial DACs, such as the Harris

HI5721.

>°

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