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* This page was dynamically generated by Analog Devices, Inc. and inserted into this data sheet. Note: Dynamic changes to

the content on this page does not constitute a change to the revision number of the product data sheet. This content may be

frequently modified.

REV. A–2–

(VS = 5.0 V, –40ⴗC ≤ TA ≤ 105ⴗC, unless otherwise noted.)

Parameter Symbol Conditions Min Typ Max Unit

ACCURACY

TMP17F T

= 25ⴗC

±2.5 ⴗC

TMP17G T

= 25ⴗC

±3.5 ⴗC

TMP17F Over Rated Temperature ±3.5 ⴗC

TMP17G Over Rated Temperature ±4.5 ⴗC

POWER SUPPLY REJECTION RATIO

4 V < V

< 5 V PSRR 0.5 ⴗC/V

5 V < V

< 15 V PSRR 0.3 ⴗC/V

15 V < V

< 30 V PSRR 0.3 ⴗC/V

Nonlinearity Over Rated Temperature

0.5 ⴗC

OUTPUT

Nominal Current Output T

= 25ⴗC (298.2 K) 298.2 µA

Scale Factor Over Rated Temperature 1 µA/ⴗC

Repeatability Note 3 0.2 ⴗC

Long Term Stability T

= 150ⴗC for 500 Hrs

0.2 ⴗC/month

POWER SUPPLY

Supply Range +V

430V

NOTES

An external calibration trim can be used to zero the error @ 25ⴗC.

Defined as the maximum deviation from a mathematically best fit line.

Maximum deviation between 25ⴗC readings after a temperature cycle between –40ⴗC and +105ⴗC. Errors of this type are noncumulative.

Operation at 150ⴗC. Errors of this type are noncumulative.

Specifications subject to change without notice.

ABSOLUTE MAXIMUM RATINGS*

Maximum Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . 30 V

Operating Temperature Range . . . . . . . . . . . –40ⴗC to +105ⴗC

Maximum Forward Voltage (1 to 2) . . . . . . . . . . . . . . . . . 44 V

Maximum Reverse Voltage (2 to 1) . . . . . . . . . . . . . . . . . . 20 V

Dice Junction Temperature . . . . . . . . . . . . . . . . . . . . . . 175ⴗC

Storage Temperature Range . . . . . . . . . . . . . –65ⴗC to +160ⴗC

Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . . . 300ⴗC

*Stresses above those listed under Absolute Maximum Ratings may cause perma-

nent damage to the device. This is a stress rating only and functional operation at

or above this specification is not implied. Exposure to the above maximum rating

conditions for extended periods may affect device reliability.

TEMPERATURE SCALE CONVERSION EQUATIONS

K +223ⴗ+273ⴗ+298ⴗ+323ⴗ+373ⴗ+423ⴗ

ⴗC –50ⴗ0ⴗ+25ⴗ+50ⴗ+100ⴗ+150ⴗ

ⴗF –100ⴗ0ⴗ+100ⴗ+200ⴗ+300ⴗ

+32ⴗ+70ⴗ+212ⴗ

ⴗC = (ⴗF – 32) ⴗF = ⴗC + 32 K = ⴗC + 273.15

METALLIZATION DIAGRAM

V+

V–

62mils

37mils

CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily

accumulate on the human body and test equipment and can discharge without detection. Although the

TMP17 features proprietary ESD protection circuitry, permanent damage may occur on devices

subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended

to avoid performance degradation or loss of functionality.

TMP17F/G–SPECIFICATIONS

ORDERING GUIDE

Max Cal Max Error Nonlinearity

Error –40ⴗC to –40ⴗC to Package

Model @ +25ⴗC+105ⴗC+105ⴗCOption

TMP17FS 2.5ⴗC3.5ⴗC0.5ⴗCR-8

TMP17GS 3.5ⴗC4.5ⴗC0.5ⴗCR-8

REV. A –3–

Typical Performance Characteristics–TMP17

TEMPERATURE – ⴗC

–6

–50 125–25

TEMPERATURE ERROR – ⴗC

0255075100

–2

–4

–1

–3

–5

V+ = +5V

MAX LIMIT

MIN LIMIT

TPC 1. Accuracy vs. Temperature

TIME – sec

100

00305

PERCENT OF CHANGE – %

10 15 20 25

V+ = +5V

SOIC PACKAGE

SOLDERED TO

0.5" ⴛ 0.3" Cu PCB

TPC 2. Thermal Response in Stirred Oil Bath

AIR VELOCITY – FPM

00 600100

TIME CONSTANT – sec

200 300 400 500

TRANSITION FROM ⴙ100ⴗC STIRRED

BATH TO FORCED ⴙ25ⴗC AIR

Vⴙ = ⴙ5V

SOIC PACKAGE SOLDERED

TO 0.5“ ⴛ 0.3” Cu PCB

TPC 3. Thermal Time Constant in Forced Air

SUPPLY VOLTAGE – V

500

400

0061

OUTPUT CURRENT – ␮A

2345

300

200

100

450

350

250

150

= +105ⴗC

= +25ⴗC

= –40ⴗC

CONSTANT I

OUT

UP TO 30V

OUT

= 378␮A

OUT

= 298␮A

OUT

= 233␮A

TPC 4. V-I Characteristics

2µs

200mV

100

VIN = 0V TO 5V

RL = 1k⍀

TA = 25ⴗC

TPC 5. Output Turn-On Settling Time

REV. A–4–

TMP17

THEORY OF OPERATION

The TMP17 uses a fundamental property of silicon transistors

to realize its temperature proportional output. If two identical

transistors are operated at a constant ratio of collector current

densities, r, then the difference in base-emitter voltages will be

(kT/q)(ln r). Since both k, Boltzmann’s constant, and q, the

charge of an electron, are constant, the resulting voltage is

directly Proportional to Absolute Temperature (PTAT). In the

TMP17, this difference voltage is converted to a PTAT current

by low temperature coefficient thin film resistors. This PTAT

current is then used to force the total output current to be pro-

portional to degrees Kelvin. The result is a current source with

an output equal to a scale factor times the temperature (K) of

the sensor. A typical V-I plot of the circuit at 125ⴗC and the

temperature extremes is shown in TPC 4.

Factory trimming of the scale factor to 1 µA/K is accomplished at

the wafer level by adjusting the TMP17’s temperature reading

so it corresponds to the actual temperature. During laser trim-

ming, the IC is at a temperature within a few degrees of 25ⴗC

and is powered by a 5 V supply. The device is then packaged and

automatically temperature tested to specification.

FACTORS AFFECTING TMP17 SYSTEM PRECISION

The accuracy limits in the Specifications table make the TMP17

easy to apply in a variety of diverse applications. To calculate a

total error budget in a given system, it is important to correctly

interpret the accuracy specifications, nonlinearity errors, the

response of the circuit to supply voltage variations, and the effect

of the surrounding thermal environment. As with other electronic

designs, external component selection will have a major effect

on accuracy.

CALIBRATION ERROR, ABSOLUTE ACCURACY, AND

NONLINEARITY SPECIFICATIONS

Two primary limits of error are given for the TMP17 such that

the correct grade for any given application can easily be chosen

for the overall level of accuracy required. They are the calibration

accuracy at +25ⴗC and the error over temperature from –40ⴗC

to +105ⴗC. These specifications correspond to the actual error

the user would see if the current output of a TMP17 were

converted to a voltage with a precision resistor. Note that the

maximum error at room temperature or over an extended range,

including the boiling point of water, can be read directly from

the Specifications table. The error limits are a combination of

initial error, scale factor variation, and nonlinearity deviation

from the ideal 1 µA/K output. TPC 1 graphically depicts the

guaranteed limits of accuracy for a TMP17GS.

The TMP17 has a highly linear output in comparison to older

technology sensors (i.e., thermistors, RTDs, and thermocouples),

thus a nonlinearity error specification is separated from the

absolute accuracy given over temperature. As a maximum deviation

from a best-fit straight line, this specification represents the only

error that cannot be trimmed out. Figure 2 is a plot of typical

TMP17 nonlinearity over the full rated temperature range.

TEMPERATURE – ⴗC

0.2

0.1

–0.3

–40 105–25

NONLINEARITY – ⴗC

025 70

–0.1

–0.2

TYPICAL NONLINEARITY

Figure 2. Nonlinearity Error

TRIMMING FOR HIGHER ACCURACY

Calibration error at 25ⴗC can be removed with a single tem-

perature trim. Figure 3 shows how to adjust the TMP17’s scale

factor in the basic voltage output circuit.

–TMP17

–

VOUT = 1mV/K

100⍀

950⍀

Figure 3. Basic Voltage Output (Single Temperature Trim)

To trim the circuit, the temperature must be measured by a refer-

ence sensor and the value of R should be adjusted so the output

OUT

) corresponds to 1 mV/K. Note that the trim procedure

should be implemented as close as possible to the temperature

for which highest accuracy is desired. In most applications, if a

single temperature trim is desired, it can be implemented where

the TMP17 current-to-output voltage conversion takes place

(e.g., output resistor, offset to an op amp). Figure 4 illustrates

the effect on total error when using this technique.

TEMPERATURE – ⴗC

1.0

0.5

–40 105–25

TOT AL ERROR – ⴗC

025

–0.5

–1.0

ACCURACY

WITHOUT TRIM

AFTER SINGLE

TEMPERATURE

CALIBRATION

Figure 4. Effect of Scale Factor Trim on Accuracy

REV. A –5–

TMP17

If greater accuracy is desired, initial calibration and scale factor

errors can be removed by using the TMP17 in the circuit of

Figure 5.

–

VOUT = 100mV/ⴗC

–

TMP17

V–

OP196

REF43

+5V

8.66k⍀

7.87k⍀

1k⍀

97.6k⍀

5k⍀

Figure 5. Two Temperature Trim Circuit

With the transducer at 0ⴗC, adjustment of R1 for a 0 V output

nulls the initial calibration error and shifts the output from K to ⴗC.

Tweaking the gain of the circuit at an elevated temperature by

adjusting R2 trims out scale factor error. The only error remaining

over the temperature range being trimmed for is nonlinearity.

Atypical plot of two trim accuracy is given in Figure 6.

TEMPERATURE – ⴗC

0.2

0.1

–0.3

–40 105–25

TOT AL ERROR – ⴗC

025 75

–0.1

–0.2

Figure 6. Typical Two Trim Accuracy

SUPPLY VOLTAGE AND THERMAL ENVIRONMENT

EFFECTS

The power supply rejection characteristics of the TMP17 mini-

mize errors due to voltage irregularity, ripple, and noise. If a

supply is used other than 5 V (used in factory trimming), the

power supply error can be removed with a single temperature

trim. The PTAT nature of the TMP17 will remain unchanged.

The general insensitivity of the output allows the use of lower

cost unregulated supplies and means that a series resistance of

several hundred ohms (e.g., CMOS multiplexer, meter coil

resistance) will not degrade the overall performance.

The thermal environment in which the TMP17 is used determines

two performance traits: the effect of self-heating on accuracy and

the response time of the sensor to rapid changes in temperature.

In the first case, a rise in the IC junction temperature above the

ambient temperature is a function of two variables: the power

consumption level of the circuit and the thermal resistance

between the chip and the ambient environment (␪

). Self-heating

error in °C can be derived by multiplying the power dissipation

by ␪

. Because errors of this type can vary widely for surroundings

with different heat sinking capacities, it is necessary to specify ␪

under several conditions. Table I shows how the magnitude of

self-heating error varies relative to the environment. In typical

free air applications at 25ⴗC with a 5 V supply, the magnitude of

the error is 0.2ⴗC or less. A small glued-on heat sink will reduce

the temperature error in high temperature, large supply voltage

situations.

Table I. Thermal Characteristics

Medium ␪

(ⴗC/W) ␶ (sec)*

Still Air 158 52

Moving Air @ 500 FPM 60 10

Fluorinert Liquid 35 2

*␶ is an average of one time constant (63.2% of final value). In cases where the

thermal response is not a simple exponential function, the actual thermal

response may be better than indicated.

Response of the TMP17 output to abrupt changes in ambient

temperature can be modeled by a single time constant ␶ expo-

nential function. TPC 2 and TPC 3 show typical response time

plots for media of interest.

The time constant, ␶, is dependent on ␪

and on the thermal

capacities of the chip and the package. Table I lists the effective

␶ (time to reach 63.2% of the final value) for several different

media. Copper printed circuit board connections will sink or

conduct heat directly through the TMP17’s soldered leads.

When faster response is required, a thermally conductive grease

or glue between the TMP17 and the surface temperature being

measured should be used.

MOUNTING CONSIDERATIONS

If the TMP17 is thermally attached and properly protected, it can

be used in any temperature measuring situation where the maxi-

mum range of temperatures encountered is between –40ⴗC and

+105ⴗC. Thermally conductive epoxy or glue is recommended

under typical mounting conditions. In wet environments, conden-

sation at cold temperatures can cause leakage current related errors

and should be avoided by sealing the device in nonconductive

epoxy paint or conformal coating.

APPLICATIONS

Connecting several TMP17 devices in parallel adds the currents

through them and produces a reading proportional to the average

temperature. TMP17s connected in series will indicate the lowest

temperature, because the coldest device limits the series current

flowing through the sensors. Both of these circuits are depicted

in Figure 7.

–

TMP17

+5V

333.3⍀

(0.1%) V

AVG

(1mV/1K)

–

10k⍀

(0.1%) V

AVG

(10mV/1K)

+15V

TMP17

Figure 7. Average and Minimum Temperature

Connections

REV. A–6–

The circuit in Figure 8 demonstrates a method in which a voltage

output can be derived in a differential temperature measurement.

–

–TMP17 +

–V

OP196

10k⍀

VOUT = (T1 – T2) ⴛ (10mV/ⴗC)

10k⍀

5M⍀

50k⍀

–TMP17

Figure 8. Differential Measurements

R1 can be used to trim out the inherent offset between the two

devices. By increasing the gain resistor (10 kΩ), temperature mea-

surements can be made with higher resolution. If the magnitude

of V1 and V2 is not the same, the difference in power consumption

between the two devices can cause a differential self-heating error.

Cold junction compensation (CJC) used in thermocouple signal

conditioning can be implemented using a TMP17 in the circuit

configuration of Figure 9. Expensive simulated ice baths or hard

to trim, inaccurate bridge circuits are no longer required.

–

TMP17

OP193

+7.5V

RG1

RG2

(1k⍀)

100k⍀

10k⍀

1k⍀

REFERENCE

JUNCTION

MEASURING

JUNCTION 2.5V

REF43

VOUT

THERMOCOUPLE

TYPE

APPROX.

R V ALUE

52⍀

41⍀

61⍀

6⍀

Figure 9. Thermocouple Cold Junction Compensation

The circuit shown can be optimized for any ambient temperature

range or thermocouple type by simply selecting the correct value

for the scaling resistor R. The TMP17 output (1 µA/K) ⫻ R

should approximate the line best fit to the thermocouple curve

(slope in V/ⴗC) over the most likely ambient temperature range.

Additionally, the output sensitivity can be chosen by selecting

the resistors R

and R

for the desired noninverting gain. The

offset adjustment shown simply references the TMP17 to ⴗC. Note

that the TC of the reference and the resistors are the primary

contributors to error. Temperature rejection of 40 to 1 can be

easily achieved using the above technique.

Although the TMP17 offers a noise immune current output, it

is not compatible with process control/industrial automation

current loop standards. Figure 10 is an example of a temperature

to 4–20 mA transmitter for use with 40 V, 1 kΩ systems.

In this circuit the 1 µA/K output of the TMP17 is amplified to

1mA/°C and offset so that 4 mA is equivalent to 17°C and 20 mA

is equivalent to 33°C. R

is trimmed for proper reading at an

intermediate reference temperature. With a suitable choice of

resistors, any temperature range within the operating limits of

the TMP17 may be chosen.

5k⍀

35.7k⍀

12.7k⍀

10⍀

10k⍀

10mV/ⴗC

–

REF01E

–

TMP17

5k⍀500⍀

OP97

1mA/ⴗC

17ⴗC 4mA

33ⴗC 20mA

–20V

+–

+20V

Figure 10. Temperature to 4 –20 mA Current Transmitter

Reading temperature with a TMP17 in a microprocessor based

system can be implemented with the circuit shown in Figure 11.

–

–TMP17

OP196

RGAIN

VOUT = 100mV/(ⴗC OR ⴗF)

+5V

V–

ROFFSET/RGAIN

RCAL

ROFFSET

2.5V

REF43

ROFFSET

9.1k⍀

9.8k⍀

RGAIN

100k⍀

180k⍀

ⴗC

ⴗF

Figure 11. Temperature to Digital Output

By using a differential input A/D converter and choosing the current

to voltage conversion resistor correctly, any range of temperatures

(up to the 145ⴗC span the TMP17 is rated for) centered at any

point can be measured using a minimal number of components.

In this configuration, the system will resolve up to 1ⴗC.

A variable temperature controlling thermostat can easily be built

using the TMP17 in the circuit in Figure 12.

SET

10k⍀

REF01E

–

TMP17

+AD790

COMPARATOR

HYST

(OPTIONAL)

LOW

27.3k⍀

HIGH

62.7k⍀

10V

10k⍀C

+15V

TEMP > SETPOINT

OUTPUT HIGH

TEMP < SETPOINT

OUTPUT LOW

PULL-UP

Figure 12. Variable Temperature Thermostat

TMP17

REV. A

TMP17

–7–

HIGH

and R

LOW

determine the limits of temperature controlled

by the potentiometer R

SET

. The circuit shown operates over the

temperature range –25ⴗC to +105ⴗC. The reference maintains a

constant set point voltage and ensures that approximately 7 V

appear across the sensor. If it is necessary to guardband for

extraneous noise, hysteresis can be added by tying a resistor

from the output to the ungrounded end of R

LOW.

Multiple remote temperatures can be measured using several

TMP17s with a CMOS multiplexer or a series of 5 V logic gates

because of the device’s current-mode output and supply-voltage

compliance range. The on resistance of a FET switch or output

impedance of a gate will not affect the accuracy, as long as 4 V

is maintained across the transducer. Muxes and logic driving

circuits should be chosen to minimize leakage current related

errors. Figure 13 illustrates a locally controlled mux switching

the signal current from several remote TMP17s. CMOS or TTL

gates can also be used to switch the TMP17 supply voltages,

with the multiplexed signal being transmitted over a single twisted

pair to the load.

–

–15V

DECODER/

DRIVER

TTL DTL TO

CMOS I/O

ENCHANNEL

SELECT

AD7501

10k⍀

VOUT

+15V

REMOTE

TMP17s

–

Figure 13. Remote Temperature Multiplexing

To minimize the number of muxes required when a large number

of TMP17s are being used, the circuit can be configured in a

matrix. That is, a decoder can be used to switch the supply voltage

to a column of TMP17s while a mux is used to control which

row of sensors is being measured. The maximum number of

TMP17s that can be used is the product of the number of channels

of the decoder and mux.

An example circuit controlling 80 TMP17s is shown in Figure 14.

A 7-bit digital word is all that is required to select one of the

sensors. The enable input of the multiplexer turns all the sensors

off for minimum dissipation while idling.

AD7501

8-CHANNEL MUX

OUT

10k⍀

+15V

–15V

ROW

SELECT

4028 BCD TO DECIMAL DECODER

COLUMN

SELECT

+15V

80–TMP17s

Figure 14. Matrix Multiplexer

To convert the TMP17 output to °C or °F, a single inexpensive

reference and op amp can be used as shown in Figure 15. Although

this circuit is similar to the two temperature trim circuit shown

in Figure 5, there are two important differences. First, the gain

resistor is fixed, alleviating the need for an elevated temperature

trim. Acceptable accuracy can be achieved by choosing an inex-

pensive resistor with the correct tolerance. Second, the TMP17

calibration error can be trimmed out at a known convenient

temperature (e.g., room temperature) with a single potentiometer

adjustment. This step is independent of the gain selection.

–

TMP17

OP196

RGAIN

VOUT = 100mV/(ⴗC OR ⴗF)

+5V

V–

ROFFSET/RGAIN

RCAL

ROFFSET

2.5V

REF43

ROFFSET

9.1k⍀

9.8k⍀

RGAIN

100k⍀

180k⍀

ⴗC

ⴗF

Figure 15. Celsius or Fahrenheit Thermometer

REV. A

C00336–0–1/03(A)

PRINTED IN U.S.A.

–8–

TMP17

OUTLINE DIMENSIONS

8-Lead Standard Small Outline Package [SOIC]

Narrow Body

(R-8)

Dimensions shown in millimeters and (inches)

0.25 (0.0098)

0.19 (0.0075)

1.27 (0.0500)

0.41 (0.0160)

0.50 (0.0196)

0.25 (0.0099) ⴛ 45ⴗ

8ⴗ

0ⴗ

1.75 (0.0688)

1.35 (0.0532)

SEATING

PLANE

0.25 (0.0098)

0.10 (0.0040)

5.00 (0.1968)

4.80 (0.1890)

4.00 (0.1574)

3.80 (0.1497)

1.27 (0.0500)

BSC

6.20 (0.2440)

5.80 (0.2284)

0.51 (0.0201)

0.33 (0.0130)

COPLANARITY

0.10

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS

(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR

REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN

COMPLIANT TO JEDEC STANDARDS MS-012AA

Revision History

Location Page

1/03—Data Sheet changed from REV. 0 to REV. A.

Deleted Obsolete TPC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3

Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8