LMH6723,LMH6724,LMH6725
LMH6723/LMH6724/LMH6725 Single/Dual/Quad 370 MHz 1 mA Current Feedback
Operational Amplifier
Literature Number: SNOSA83G
LMH6723/LMH6724/LMH6725
Single/Dual/Quad 370 MHz 1 mA Current Feedback
Operational Amplifier
General Description
The LMH6723/LMH6724/LMH6725 provides a 260 MHz
small signal bandwidth at a gain of +2 V/V and a 600 V/µs
slew rate while consuming only 1 mA from ±5V supplies.
The LMH6723/LMH6724/LMH6725 supports video applica-
tions with its 0.03% and 0.11˚ differential gain and phase for
NTSC and PAL video signals. The LMH6723/LMH6724/
LMH6725 also offers a flat gain response of 0.1 dB to 100
MHz. Additionally, the LMH6723/LMH6724/LMH6725 can
deliver 110 mA of linear output current. This level of perfor-
mance, as well as a wide supply range of 4.5 to 12V, makes
the LMH6723/LMH6724/LMH6725 an ideal op amp for a
variety of portable applications. The LMH6723/LMH6724/
LMH6725’s small packages (TSSOP, SOIC & SOT23), low
power requirement and high performance allow the
LMH6723/LMH6724/LMH6725 to serve a wide variety of
portable applications.
The LMH6723/LMH6724/LMH6725 is manufactured in Na-
tional’s VIP10™complimentary bipolar process.
Features
nLarge signal bandwidth and slew rate 100% tested
n370 MHz bandwidth (A
V
=1,V
OUT
= 0.5 V
PP
)−3dB
BW
n260 MHz (A
V
=+2V/V,V
OUT
= 0.5 V
PP
)−3dBBW
n1 mA supply current
n110 mA linear output current
n0.03%, 0.11˚ differential gain, phase
n0.1 dB gain flatness to 100 MHz
nFast slew rate: 600 V/µs
nUnity gain stable
nSingle supply range of 4.5 to 12V
nImproved replacement for CLC450, CLC452, (LMH6723)
Applications
nLine driver
nPortable video
nA/D driver
nPortable DVD
Typical Application
20078936
Single Supply Cable Driver
VIP10™is a trademark of National Semiconductor Corporation.
August 2005
LMH6723/LMH6724/LMH6725 Single/Dual/Quad 370 MHz 1 mA Current Feedback Op Amp
© 2005 National Semiconductor Corporation DS200789 www.national.com
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
V
CC
(V
+
-V
-
)±6.75V
I
OUT
120 mA (Note 3)
Common Mode Input Voltage ±V
CC
Maximum Junction Temperature +150˚C
Storage Temperature Range −65˚C to +150˚C
Soldering Information
Infrared or Convection (20 sec) 235˚C
Wave Soldering (10 sec) 260˚C
ESD Tolerance (Note 4)
Human Body Model 2000V
Machine Model (Note 4) 200V
Operating Ratings (Note 3)
Thermal Resistance
Package (θ
JA
)
8-Pin SOIC 166˚C/W
5-Pin SOT23 230˚C/W
14-Pin SOIC 130˚C/W
14-Pin TSSOP 160˚C/W
Operating Temperature Range −40˚C to +85˚C
Nominal Supply Voltage 4.5V to 12V
±5V Electrical Characteristics
Unless otherwise specified, A
V
= +2, R
F
= 1200Ω,R
L
= 100Ω.Boldface limits apply at temperature extremes. (Note 2)
Symbol Parameter Conditions Min Typ Max Units
Frequency Domain Response
SSBW −3 dB Bandwidth Small Signal V
OUT
= 0.5 V
PP
260 MHz
LSBW −3dB Bandwidth Large Signal V
OUT
= 4.0 V
PP
LMH6723 90 110
MHz
LMH6724
LMH6725
85 95
UGBW −3 dB Bandwidth Unity Gain V
OUT
=.2V
PP
A
V
= 1 V/V 370 MHz
.1dB BW .1 dB Bandwidth V
OUT
= 0.5 V
PP
100 MHz
DG Differential Gain R
L
= 150Ω, 4.43 MHz 0.03 %
DP Differential Phase R
L
= 150Ω, 4.43 MHz 0.11 deg
Time Domain Response
TRS Rise and Fall Time 4V Step 2.5 ns
TSS Settling Time to 0.05% 2V Step 30 ns
SR Slew Rate 4V Step 500 600 V/µs
Distortion and Noise Response
HD2 2
nd
Harmonic Distortion 2 V
PP
, 5 MHz −65 dBc
HD3 3
rd
Harmonic Distortion 2 V
PP
, 5 MHz −63 dBc
Equivalent Input Noise
VN Non-Inverting Voltage Noise >1 MHz 4.3 nV/
NICN Inverting Current Noise >1 MHz 6 pA/
ICN Non-Inverting Current Noise >1 MHz 6 pA/
Static, DC Performance
V
IO
Input Offset Voltage 1 ±3
±3.7 mV
I
BN
Input Bias Current Non-Inverting −2 ±4
±5µA
I
BI
Input Bias Current Inverting 0.4 ±4
±5µA
PSRR Power Supply Rejection Ratio DC, 1V Step LMH6723 59
57
64
dB
LMH6724 59
55
64
LMH6725 59
56
64
LMH6723/LMH6724/LMH6725
www.national.com 2
±5V Electrical Characteristics (Continued)
Unless otherwise specified, A
V
= +2, R
F
= 1200Ω,R
L
= 100Ω.Boldface limits apply at temperature extremes. (Note 2)
Symbol Parameter Conditions Min Typ Max Units
CMRR Common Mode Rejection Ratio DC, 1V Step LMH6723 57
55
60
dB
LMH6724 57
53
60
LMH6725 57
54
60
I
CC
Supply Current (per amplifier) R
L
=∞1 1.2
1.4
mA
Miscellaneous Performance
R
IN+
Input Resistance Non-Inverting 100 kΩ
R
IN−
Input Resistance
(Output Resistance of Input
Buffer)
Inverting 500 Ω
C
IN
Input Capacitance Non-Inverting 1.5 pF
R
OUT
Output Resistance Closed Loop 0.01 Ω
V
O
Output Voltage Range R
L
=∞LMH6723 ±4
±3.9
±4.1
V
LMH6724
LMH6725
±4
±3.85
±4.1
V
OL
Output Voltage Range, High R
L
= 100Ω3.6
3.5
3.7
V
Output Voltage Range, Low R
L
= 100Ω−3.25
−3.1
−3.45
CMVR Input Voltage Range Common Mode, CMRR >50 dB ±4.0 V
I
O
Output Current Sourcing, V
OUT
=0 95
70
110
mA
Sinking, V
OUT
= 0 −80
−70
110
±2.5V Electrical Characteristics
Unless otherwise specified, A
V
= +2, R
F
= 1200Ω,R
L
= 100Ω.Boldface limits apply at temperature extremes. (Note 2)
Symbol Parameter Conditions Min Typ Max Units
Frequency Domain Response
SSBW −3 dB Bandwidth Small Signal V
OUT
= 0.5 V
PP
210 MHz
LSBW −3 dB Bandwidth Large Signal V
OUT
= 2.0 V
PP
LMH6723
LMH6724
95 125
MHz
LMH6725 90 100
UGBW −3 dB Bandwidth Unity Gain V
OUT
= 0.5 V
PP
,A
V
= 1 V/V 290 MHz
.1dB BW .1 dB Bandwidth V
OUT
= 0.5 V
PP
100 MHz
DG Differential Gain R
L
= 150Ω, 4.43 MHz .03 %
DP Differential Phase R
L
= 150Ω, 4.43 MHz 0.1 deg
Time Domain Response
TRS Rise and Fall Time 2V Step 4 ns
SR Slew Rate 2V Step 275 400 V/µs
Distortion and Noise Response
HD2 2
nd
Harmonic Distortion 2 V
PP
, 5 MHz −67 dBc
HD3 3
rd
Harmonic Distortion 2 V
PP
, 5 MHz −67 dBc
Equivalent Input Noise
VN Non-Inverting Voltage >1 MHz 4.3 nV/
LMH6723/LMH6724/LMH6725
www.national.com3
±2.5V Electrical Characteristics (Continued)
Unless otherwise specified, A
V
= +2, R
F
= 1200Ω,R
L
= 100Ω.Boldface limits apply at temperature extremes. (Note 2)
Symbol Parameter Conditions Min Typ Max Units
NICN Inverting Current >1MHz 6 pA/
ICN Non-Inverting Current >1MHz 6 pA/
Static, DC Performance
V
IO
Input Offset Voltage −0.5 ±3
±3.4 mV
I
BN
Input Bias Current Non-Inverting −2.7 ±4
±5µA
I
BI
Input Bias Current Inverting −0.7 ±4
±5µA
PSRR Power Supply Rejection Ratio DC, 0.5V Step LMH6723 59
57
62
dB
LMH6724 58
55
62
LMH6725 59
56
62
CMRR Common Mode Rejection Ratio DC, 0.5V Step LMH6723 57
53
59
dB
LMH6724 55
52
59
LMH6725 57
52
59
I
CC
Supply Current (per amplifier) R
L
=∞.9 1.1
1.3 mA
Miscellaneous Performance
R
IN+
Input Resistance Non-Inverting 100 kΩ
R
IN−
Input Resistance
(Output Resistance of Input
Buffer)
Inverting 500 Ω
C
IN
Input Capacitance Non-Inverting 1.5 pF
R
OUT
Output Resistance Closed Loop .02 Ω
V
O
Output Voltage Range R
L
=∞±1.55
±1.4
±1.65 V
V
OL
Output Voltage Range, High R
L
= 100ΩLMH6723 1.35
1.27
1.45
V
LMH6724
LMH6725
1.35
1.26
1.45
Output Voltage Range, Low R
L
= 100ΩLMH6723 −1.25
−1.15
−1.38
V
LMH6724
LMH6725
−1.25
−1.15
−1.38
CMVR Input Voltage Range Common Mode, CMRR >50 dB ±1.45 V
I
O
Output Current Sourcing 70
60
90
mA
Sinking −30
−30
−60
LMH6723/LMH6724/LMH6725
www.national.com 4
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications, see the Electrical Characteristics tables.
Note 2: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of
the device such that TJ=T
A. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self heating where TJ>TA.
See Applications Section for information on temperature derating of this device. Min/Max ratings are based on product characterization and simulation. Individual
parameters are tested as noted.
Note 3: The maximum continuous output current (IOUT) is determined by device power dissipation limitations. See the Power Dissipation section of the Application
Section for more details.
Note 4: Human Body Model, 1.5 kΩin series with 100 pF. Machine Model, 0ΩIn series with 200 pF.
Connection Diagrams
5-Pin SOT23 8-Pin SOIC
20078937
Top View 20078938
Top View
14-Pin TSSOP & SOIC 8-Pin SOIC
20078944
Top View 20078947
Top View
Ordering Information
Package Part Number Package Marking Transport Media NSC Drawing
5-Pin SOT23 LMH6723MF AB1A 1k Units Tape and Reel MF05A
LMH6723MFX 3k Units Tape and Reel
8-Pin SOIC LMH6723MA LMH6723MA 95 Units/Rail M08A
LMH6723MAX 2.5k Units Tape and Reel
8-Pin SOIC LMH6724MA LMH6724MA 95 Units/Rail M08A
LMH6724MAX 2.5k Units Tape and Reel
14-Pin SOIC LMH6725MA LMH6725MA 55 Units/Rail M14A
LMH6725MAX 2.5k Units Tape and Reel
14-Pin TSSOP LMH6725MT LMH6725MT 94 Units/Rail MTC14
LMH6725MTX 2.5k Units Tape and Reel
LMH6723/LMH6724/LMH6725
www.national.com5
Typical Performance Characteristics A
V
=2,R
F
= 1200Ω,R
L
= 100Ω, unless otherwise specified.
Frequency Response vs. V
OUT
,A
V
= 2 Frequency Response vs. V
OUT
,A
V
=2
20078928 20078926
Frequency Response vs. V
OUT
,A
V
= 1 Frequency Response vs. V
OUT
,A
V
=1
20078929 20078927
Large Signal Frequency Response Frequency Response vs. Supply Voltage
20078921 20078930
LMH6723/LMH6724/LMH6725
www.national.com 6
Typical Performance Characteristics A
V
=2,R
F
= 1200Ω,R
L
= 100Ω, unless otherwise
specified. (Continued)
Suggested R
F
vs. Gain Non-Inverting Suggested R
F
vs. Gain Inverting
20078905 20078906
Frequency Response vs. R
F
Frequency Response vs. R
F
20078922 20078923
Open Loop Gain & Phase Open Loop Gain & Phase
20078917 20078918
LMH6723/LMH6724/LMH6725
www.national.com7
Typical Performance Characteristics A
V
=2,R
F
= 1200Ω,R
L
= 100Ω, unless otherwise
specified. (Continued)
HD2 & HD3 vs. V
OUT
HD2 & HD3 vs. V
OUT
20078911 20078913
HD2 & HD3 vs. Frequency HD2 & HD3 vs. Frequency
20078912 20078914
Frequency Response vs. C
L
Frequency Response vs. C
L
20078925 20078924
LMH6723/LMH6724/LMH6725
www.national.com 8
Typical Performance Characteristics A
V
=2,R
F
= 1200Ω,R
L
= 100Ω, unless otherwise
specified. (Continued)
Suggested R
OUT
vs. C
L
Suggested R
OUT
vs. C
L
20078920 20078919
PSRR vs. Frequency PSRR vs. Frequency
20078915 20078916
Closed Loop Output Resistance CMRR vs. Frequency
20078907 20078908
LMH6723/LMH6724/LMH6725
www.national.com9
Typical Performance Characteristics A
V
=2,R
F
= 1200Ω,R
L
= 100Ω, unless otherwise
specified. (Continued)
Differential Gain & Phase Channel Matching (LMH6724)
20078910 20078948
Channel Matching (LMH6724) Crosstalk (LMH6724)
20078949 20078946
Channel Matching (LMH6725) Channel Matching (LMH6725)
20078940 20078941
LMH6723/LMH6724/LMH6725
www.national.com 10
Typical Performance Characteristics A
V
=2,R
F
= 1200Ω,R
L
= 100Ω, unless otherwise
specified. (Continued)
Crosstalk (LMH6725)
20078945
Application Section
GENERAL INFORMATION
The LMH6723/LMH6724/LMH6725 is a high speed current
feedback amplifier manufactured on National Semiconduc-
tor’s VIP10 (Vertically Integrated PNP) complimentary bipo-
lar process. LMH6723/LMH6724/LMH6725 offers a unique
combination of high speed and low quiescent supply current
making it suitable for a wide range of battery powered and
portable applications that require high performance. This
amplifier can operate from 4.5V to 12V nominal supply volt-
ages and draws only 1 mA of quiescent supply current at
10V supplies (±5V typically). The LMH6723/LMH6724/
LMH6725 has no internal ground reference so single or split
supply configurations are both equally useful.
EVALUATION BOARDS
National Semiconductor provides the following evaluation
boards as a guide for high frequency layout and as an aid in
device testing and characterization. Many of the datasheet
plots were measured with these boards.
Device Package Board Part #
LMH6723MA SOIC-8 CLC730227
LMH6723MF SOT-23 CLC730216
LMH6724MA SOIC-8 CLC730036
LMH6725MA SOIC-14 CLC730231
These evaluation boards can be shipped when a device
sample request is placed with National Semiconductor.
FEEDBACK RESISTOR SELECTION
One of the key benefits of a current feedback operational
amplifier is the ability to maintain optimum frequency re-
sponse independent of gain by using appropriate values for
the feedback resistor (R
F
). The Electrical Characteristics and
Typical Performance plots were generated with an R
F
of
1200Ω, a gain of +2V/V and ±5V or ±2.5V power supplies
(unless otherwise specified). Generally, lowering R
F
from it’s
recommended value will peak the frequency response and
extend the bandwidth; however, increasing the value of R
F
will cause the frequency response to roll off faster. Reducing
the value of R
F
too far below it’s recommended value will
cause overshoot, ringing and, eventually, oscillation.
Figure 1 shows the LMH6723/LMH6724/LMH6725’s fre-
quency response as R
F
is varied (R
L
= 100Ω,A
V
= +2). This
plot shows that an R
F
of 800Ωresults in peaking. An R
F
of
1200Ωgives near maximal bandwidth and gain flatness with
good stability. Since each application is slightly different it is
worth some experimentation to find the optimal R
F
for a
given circuit. In general a value of R
F
that produces ~0.1 dB
of peaking is the best compromise between stability and
maximal bandwidth. Note that it is not possible to use a
current feedback amplifier with the output shorted directly to
the inverting input. The buffer configuration of the LMH6723/
LMH6724/LMH6725 requires a 2000Ωfeedback resistor for
stable operation. For other gains see the charts "R
F
vs. Non
20078922
FIGURE 1. Frequency Response vs. R
F
LMH6723/LMH6724/LMH6725
www.national.com11
Application Section (Continued)
Inverting Gain" and "R
F
vs. Inverting Gain". These charts
provide a good place to start when selecting the best feed-
back resistor value for a variety of gain settings.
For more information see Application Note OA-13 which
describes the relationship between R
F
and closed-loop fre-
quency response for current feedback operational amplifiers.
The value for the inverting input impedance for the
LMH6723/LMH6724/LMH6725 is approximately 500Ω. The
LMH6723/LMH6724/LMH6725 is designed for optimum per-
formance at gains of +1 to +5V/V and −1 to −4V/V. Higher
gain configurations are still useful; however, the bandwidth
will fall as gain is increased, much like a typical voltage
feedback amplifier.
Figure 2 and Figure 3 show the value of R
F
versus gain. A
higher R
F
is required at higher gains to keep R
G
from de-
creasing too far below the input impedance of the inverting
input. This limitation applies to both inverting and non-
inverting configurations. For the LMH6723/LMH6724/
LMH6725 the input resistance of the inverting input is ap-
proximately 500Ωand 100Ωis a practical lower limit for R
G
.
The LMH6723/LMH6724/LMH6725 begins to operate in a
gain bandwidth limited fashion in the region where R
F
must
be increased for higher gains. Note that the amplifier will
operate with R
G
values well below 100Ω; however, results
will be substantially different than predicted from ideal mod-
els. In particular, the voltage potential between the Inverting
and Non-Inverting inputs cannot be expected to remain
small.
For inverting configurations the impedance seen by the
source is R
G
|| R
T
. For most sources this limits the maximum
inverting gain since R
F
is determined by the desired gain as
shown in Figure 3. The value of R
G
is then R
F
/Gain. Thus for
an inverting gain of −4 V/V the input impedance is equal to
100Ω. Using a termination resistor, this can be brought down
to match a 50Ωor 75Ωsource; however, a 150Ωsource
cannot be matched without a severe compromise in R
F
.
ACTIVE FILTERS
When using any current feedback operational amplifier as an
active filter it is necessary to be careful using reactive com-
ponents in the feedback loop. Reducing the feedback imped-
ance, especially at higher frequencies, will almost certainly
cause stability problems. Likewise capacitance on the invert-
ing input should be avoided. See Application Notes OA-7
and OA-26 for more information on Active Filter applications
for Current Feedback Op Amps.
When using the LMH6723/LMH6724/LMH6725 as a low-
pass filter the value of R
F
can be substantially reduced from
the value recommended in the R
F
vs. Gain charts. The
benefit of reducing R
F
is increased gain at higher frequen-
cies, which improves attenuation in the stop band. Stability
problems are avoided because in the stop band additional
device bandwidth is used to cancel the input signal rather
than amplify it. The benefit of this change depends on the
particulars of the circuit design. With a high pass filter con-
figuration reducing R
F
will likely result in device instability
and is not recommended.
20078905
FIGURE 2. RF vs. Non-Inverting Gain
20078906
FIGURE 3. R
F
vs. Inverting Gain
20078933
FIGURE 4. Typical Application with Suggested Supply
Bypassing
LMH6723/LMH6724/LMH6725
www.national.com 12
Application Section (Continued)
DRIVING CAPACITIVE LOADS
Capacitive output loading applications will benefit from the
use of a series output resistor as shown in Figure 5. The
charts "Suggested R
OUT
vs. Cap Load" give a recommended
value for selecting a series output resistor for mitigating
capacitive loads. The values suggested in the charts are
selected for .5 dB or less of peaking in the frequency re-
sponse. This gives a good compromise between settling
time and bandwidth. For applications where maximum fre-
quency response is needed and some peaking is tolerable,
the value of R
OUT
can be reduced slightly from the recom-
mended values.
There will be amplitude lost in the series resistor unless the
gain is adjusted to compensate; this effect is most noticeable
with heavy loads (R
L
<150Ω).
An alternative approach is to place R
OUT
inside the feedback
loop as shown in Figure 6. This will preserve gain accuracy,
but will still limit maximum output voltage swing.
INVERTING INPUT PARASITIC CAPACITANCE
Parasitic capacitance is any capacitance in a circuit that was
not intentionally added. It is produced through electrical
interaction between conductors and can be reduced but
never entirely eliminated. Most parasitic capacitances that
cause problems are related to board layout or lack of termi-
nation on transmission lines. Please see the section on
Layout Considerations for hints on reducing problems due to
parasitic capacitances on board traces. Transmission lines
should be terminated in their characteristic impedance at
both ends.
High speed amplifiers are sensitive to capacitance between
the inverting input and ground or power supplies. This shows
up as gain peaking at high frequency. The capacitor raises
device gain at high frequencies by making R
G
appear
smaller. Capacitive output loading will exaggerate this effect.
One possible remedy for this effect is to slightly increase the
value of the feedback (and gain set) resistor. This will tend to
offset the high frequency gain peaking while leaving other
parameters relatively unchanged. If the device has a capaci-
tive load as well as inverting input capacitance, using a
series output resistor as described in the section on "Driving
Capacitive Loads" will help.
When higher currents are required than a single amplifier
can provide, the circuit of Figure 7 can be used. Although the
example circuit was intended for the LMH6725 quad op amp,
higher thermal efficiency can be obtained by using four
separate SOIC op amps. Careful attention to a few key
components will optimize performance from this circuit. The
first thing to note is that the buffers need slightly higher value
feedback resistors than if the amplifiers were individually
configured. As well, R
11
and C
1
provide mid circuit frequency
compensation to further improve stability. The composite
amplifier has approximately twice the phase delay of a single
circuit. The larger values of R
8
,R
9
and R
10
, as well as the
high frequency attenuation provided by C
1
and R
11
, ensure
that the circuit does not oscillate.
Resistors R
4
,R
5
,R
6
, and R
7
are necessary to ensure even
current distribution between the amplifiers. Since they are
inside the feedback loop they have no effect on the gain of
the circuit. The circuit shown in Figure 7 has a gain of 5. The
frequency response of this circuit is shown in Figure 8.
20078934
FIGURE 5. Decoupling Capacitive Loads
20078935
FIGURE 6. Series Output Resistor inside feedback loop
20078942
FIGURE 7. High Output Current Composite Amplifier
LMH6723/LMH6724/LMH6725
www.national.com13
Application Section (Continued)
LAYOUT CONSIDERATIONS
Whenever questions about layout arise, use the evaluation
board as a guide. Evaluation boards are shipped with
sample requests.
To reduce parasitic capacitances ground and power planes
should be removed near the input and output pins. Compo-
nents in the feedback loop should be placed as close to the
device as possible. For long signal paths controlled imped-
ance lines should be used, along with impedance matching
at both ends.
Bypass capacitors should be placed as close to the device
as possible. Bypass capacitors from each rail to ground are
applied in pairs. The larger electrolytic bypass capacitors
can be located anywhere on the board; however, the smaller
ceramic capacitors should be placed as close to the device
as possible.
VIDEO PERFORMANCE
The LMH6723/LMH6724/LMH6725 has been designed to
provide good performance with both PAL and NTSC com-
posite video signals. The LMH6723/LMH6724/LMH6725 is
specified for PAL signals. Typically, NTSC performance is
marginally better due to the lower frequency content of the
signal. Performance degrades as the loading is increased;
therefore, best performance will be obtained with back ter-
minated loads. The back termination reduces reflections
from the transmission line and effectively masks transmis-
sion line and other parasitic capacitances from the amplifier
output stage. Figure 4 shows a typical configuration for
driving a 75Ωcable. The amplifier is configured for a gain of
2 to make up for the 6dB of loss in R
OUT
.
SINGLE 5V SUPPLY VIDEO
With a 5V supply the LMH6723/LMH6724/LMH6725 is able
to handle a composite NTSC video signal, provided that the
signal is AC coupled and level shifted so that the signal is
centered around V
CC
/2.
POWER DISSIPATION
Follow these steps to determine the maximum power dissi-
pation for the LMH6723/LMH6724/LMH6725:
1. Calculate the quiescent (no-load) power: P
AMP
=I
CC
*
(V
S
)V
S
=V
+
-V
-
2. Calculate the RMS power dissipated in the output stage:
P
D
(rms) = rms ((V
S
-V
OUT
)*I
OUT
) where V
OUT
and I
OUT
are the voltage and current across the external load and
V
S
is the total supply current.
3. Calculate the total RMS power: P
T
=P
AMP
+P
D
The maximum power that the LMH6723/LMH6724/LMH6725
package can dissipate at a given temperature can be de-
rived with the following equation:
P
MAX
= (150o-T
AMB
)/ θ
JA
, where T
AMB
= Ambient tempera-
ture (˚C) and θ
JA
= Thermal resistance, from junction to
ambient, for a given package (˚C/W). For the SOIC-8 pack-
age θ
JA
is 166˚C/W and for the SOT it is 230˚C/W. The
SOIC-14 has a θ
JA
of 130˚C/W. The TSSOP-14 has a θ
JA
of
160˚C/W.
ESD PROTECTION
The LMH6723/LMH6724/LMH6725 is protected against
electrostatic discharge (ESD) on all pins. The LMH6723/
LMH6725 will survive 2000V Human Body Model or 200V
Machine Model events.
Under closed loop operation the ESD diodes have no effect
on circuit performance. There are occasions, however, when
the ESD diodes will be evident. If the LMH6723/LMH6724/
LMH6725 is driven into a slewing condition the ESD diodes
will clamp large differential voltages until the feedback loop
restores closed loop operation. Also, if the device is powered
down and a large input signal is applied, the ESD diodes will
conduct.
20078943
FIGURE 8. Composite Amplifier Frequency Response
LMH6723/LMH6724/LMH6725
www.national.com 14
Physical Dimensions inches (millimeters)
unless otherwise noted
5-Pin SOT23
NS Product Number MF05A
8-Pin SOIC
NS Product Number M08A
LMH6723/LMH6724/LMH6725
www.national.com15
Physical Dimensions inches (millimeters) unless otherwise noted (Continued)
14-Pin SOIC
NS Product Number M14A
14-Pin TSSOP
NS Product Number MTC14
LMH6723/LMH6724/LMH6725
www.national.com 16
Notes
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves
the right at any time without notice to change said circuitry and specifications.
For the most current product information visit us at www.national.com.
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS
WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR
CORPORATION. As used herein:
1. Life support devices or systems are devices or systems
which, (a) are intended for surgical implant into the body, or
(b) support or sustain life, and whose failure to perform when
properly used in accordance with instructions for use
provided in the labeling, can be reasonably expected to result
in a significant injury to the user.
2. A critical component is any component of a life support
device or system whose failure to perform can be reasonably
expected to cause the failure of the life support device or
system, or to affect its safety or effectiveness.
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National Semiconductor manufactures products and uses packing materials that meet the provisions of the Customer Products
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Support Center
Email: new.feedback@nsc.com
Tel: 1-800-272-9959
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Email: europe.support@nsc.com
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Email: jpn.feedback@nsc.com
Tel: 81-3-5639-7560
www.national.com
LMH6723/LMH6724/LMH6725 Single/Dual/Quad 370 MHz 1 mA Current Feedback Op Amp
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