VA
VOUTA
VOUTB
NC
NC
SCLK
DIN
VREFIN
GND
SON
1
2
3
4
5
10
9
8
7
6
SYNC
VA
VOUTA
VOUTB
NC
NC
SCLK
DIN
VREFIN
GND
VSSOP
1
2
3
4
5
10
9
8
7
6
SYNC
DAC102S085
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DAC102S085 10-Bit Micro Power DUAL Digital-to-Analog Converter with Rail-to-Rail
Output
Check for Samples: DAC102S085
1FEATURES DESCRIPTION
The DAC102S085 is a full-featured, general purpose
23• Ensured Monotonicity DUAL 10-bit voltage-output digital-to-analog converter
• Low Power Operation (DAC) that can operate from a single +2.7V to 5.5V
• Rail-to-Rail Voltage Output supply and consumes 0.6 mW at 3V and 1.6 mW at
5V. The DAC102S085 is packaged in 10-lead SON
• Power-on Reset to 0V and VSSOP packages. The 10-lead SON package
• Simultaneous Output Updating makes the DAC102S085 the smallest DUAL DAC in
• Wide power supply range (+2.7V to +5.5V) its class. The on-chip output amplifier allows rail-to-
rail output swing and the three wire serial interface
• Industry's Smallest Package operates at clock rates up to 40 MHz over the entire
• Power Down Modes supply voltage range. Competitive devices are limited
to 25 MHz clock rates at supply voltages in the 2.7V
APPLICATIONS to 3.6V range. The serial interface is compatible with
standard SPI™, QSPI, MICROWIRE and DSP
• Battery-Powered Instruments interfaces.
• Digital Gain and Offset Adjustment The reference for the DAC102S085 serves both
• Programmable Voltage & Current Sources channels and can vary in voltage between 1V and VA,
• Programmable Attenuators providing the widest possible output dynamic range.
The DAC102S085 has a 16-bit input shift register that
KEY SPECIFICATIONS controls the outputs to be updated, the mode of
operation, the powerdown condition, and the binary
• Resolution: 10 Bits input data. Both outputs can be updated
• INL: ±2 LSB (Max) simultaneously or individually depending on the
• DNL: =0.35 / -0.25 LSB (Max) setting of the two mode of operation bits.
• Settling time: 6 µs (Max) A power-on reset circuit ensures that the DAC output
• Zero Code Error: +15mV (Max) powers up to zero volts and remains there until there
is a valid write to the device. A power-down feature
• Full-Scale Error: -0.75% FS (Max) reduces power consumption to less than a microWatt
• Supply Power with three different termination options.
– Normal: 0.6 mW (3V) / 1.6 mW (5V) (Typ) The low power consumption and small packages of
– Power Down: 0.3 µW (3V) / 0.8 µW (5V) the DAC102S085 make it an excellent choice for use
(Typ) in battery operated equipment.
The DAC102S085 is one of a family of pin compatible
DACs, including the 8-bit DAC084S085 and the 12-bit
DAC122S085. The DAC102S085 operates over the
extended industrial temperature range of −40°C to
+105°C.
Pin Configuration
1Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
2SPI is a trademark of Motorola, Inc..
3All other trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date. Copyright © 2006–2013, Texas Instruments Incorporated
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
POWER-ON
RESET
DAC
REGISTER
INPUT
CONTROL
LOGIC
10
POWER-DOWN
CONTROL
LOGIC
VREFIN
DAC102S085
VOUTA
10 BIT DAC
REF
10
SCLK DIN
SYNC
BUFFER
BUFFER
10 VOUTB
2.5k 100k
2.5k 100k
10 BIT DAC
REF
DAC102S085
SNAS364E –MAY 2006–REVISED MARCH 2013
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Block Diagram
PIN DESCRIPTIONS
SON
VSSOP Symbol Type Description
Pin No.
1 VASupply Power supply input. Must be decoupled to GND.
2 VOUTA Analog Output Channel A Analog Output Voltage.
3 VOUTB Analog Output Channel B Analog Output Voltage.
4 NC Not Connected
5 NC Not Connected
6 GND Ground Ground reference for all on-chip circuitry.
Unbuffered reference voltage shared by all channels. Must be decoupled
7 VREFIN Analog Input to GND.
Serial Data Input. Data is clocked into the 16-bit shift register on the
8 DIN Digital Input falling edges of SCLK after the fall of SYNC.
Frame synchronization input for the data input. When this pin goes low, it
enables the input shift register and data is transferred on the falling edges
9 SYNC Digital Input of SCLK. The DAC is updated on the 16th clock cycle unless SYNC is
brought high before the 16th clock, in which case the rising edge of
SYNC acts as an interrupt and the write sequence is ignored by the DAC.
Serial Clock Input. Data is clocked into the input shift register on the
10 SCLK Digital Input falling edges of this pin.
Exposed die attach pad can be connected to ground or left floating.
PAD
11 Ground Soldering the pad to the PCB offers optimal thermal performance and
(SON only) enhances package self-alignment during reflow.
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
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I/O
GND
TO INTERNAL
CIRCUITRY
DAC102S085
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Absolute Maximum Ratings(1)(2)(3)
Supply Voltage, VA6.5V
Voltage on any Input Pin −0.3V to 6.5V
Input Current at Any Pin(4) 10 mA
Package Input Current(4) 20 mA
Power Consumption at TA= 25°C See(5)
Human Body Model 2500V
ESD Susceptibility(6) Machine Model 250V
Junction Temperature +150°C
Storage Temperature −65°C to +150°C
(1) Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is functional, but do not ensure specific performance limits. For ensured specifications and test conditions, see the
Electrical Characteristics. The ensured specifications apply only for the test conditions listed. Some performance characteristics may
degrade when the device is not operated under the listed test conditions. Operation of the device beyond the maximum Operating
Ratings is not recommended.
(2) All voltages are measured with respect to GND = 0V, unless otherwise specified.
(3) If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/Distributors for availability and
specifications.
(4) When the input voltage at any pin exceeds 5.5V or is less than GND, the current at that pin should be limited to 10 mA. The 20 mA
maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input current of 10
mA to two.
(5) The absolute maximum junction temperature (TJmax) for this device is 150°C. The maximum allowable power dissipation is dictated by
TJmax, the junction-to-ambient thermal resistance (θJA), and the ambient temperature (TA), and can be calculated using the formula
PDMAX = (TJmax −TA) / θJA. The values for maximum power dissipation will be reached only when the device is operated in a severe
fault condition (e.g., when input or output pins are driven beyond the operating ratings, or the power supply polarity is reversed).
(6) Human body model is 100 pF capacitor discharged through a 1.5 kΩresistor. Machine model is 220 pF discharged through ZERO
Ohms.
Operating Ratings(1)(2)
Operating Temperature Range −40°C ≤TA≤+105°C
Supply Voltage, VA+2.7V to 5.5V
Reference Voltage, VREFIN +1.0V to VA
Digital Input Voltage(3) 0.0V to 5.5V
Output Load 0 to 1500 pF
SCLK Frequency Up to 40 MHz
(1) Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is functional, but do not ensure specific performance limits. For ensured specifications and test conditions, see the
Electrical Characteristics. The ensured specifications apply only for the test conditions listed. Some performance characteristics may
degrade when the device is not operated under the listed test conditions. Operation of the device beyond the maximum Operating
Ratings is not recommended.
(2) All voltages are measured with respect to GND = 0V, unless otherwise specified.
(3) The inputs are protected as shown below. Input voltage magnitudes up to 5.5V, regardless of VA, will not cause errors in the conversion
result. For example, if VAis 3V, the digital input pins can be driven with a 5V logic device.
Package Thermal Resistances(1)(2)
Package θJA
10-Lead VSSOP 240°C/W
10-Lead SON 250°C/W
(1) Soldering process must comply with Texas Instruments' Reflow Temperature Profile specifications. Refer to www.ti.com/packaging.
(2) Reflow temperature profiles are different for lead-free packages.
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Electrical Characteristics(1)
The following specifications apply for VA= +2.7V to +5.5V, VREFIN = VA, CL= 200 pF to GND, fSCLK = 30 MHz, input code
range 12 to 1011. Boldface limits apply for TMIN ≤TA≤TMAX and all other limits are at TA= 25°C, unless otherwise
specified. Units
Symbol Parameter Conditions Typical(2) Limits(2) (Limits)
STATIC PERFORMANCE
Resolution 10 Bits (min)
Monotonicity 10 Bits (min)
INL Integral Non-Linearity ±0.7 ±2 LSB (max)
+0.08 +0.35 LSB (max)
DNL Differential Non-Linearity VA= 2.7V to 5.5V −0.03 −0.25 LSB (min)
ZE Zero Code Error IOUT = 0 +5 +15 mV (max)
FSE Full-Scale Error IOUT = 0 −0.1 −0.75 %FSR (max)
GE Gain Error All ones Loaded to DAC register −0.2 −1.0 %FSR
ZCED Zero Code Error Drift −20 µV/°C
VA= 3V −0.7 ppm/°C
TC GE Gain Error Tempco VA= 5V −1.0 ppm/°C
OUTPUT CHARACTERISTICS
0V (min)
Output Voltage Range See(3) VREFIN V (max)
High-Impedance Output Leakage
IOZ ±1 µA (max)
Current(3)
VA= 3V, IOUT = 200 µA 1.3 mV
VA= 3V, IOUT = 1 mA 6.0 mV
ZCO Zero Code Output VA= 5V, IOUT = 200 µA 7.0 mV
VA= 5V, IOUT = 1 mA 10.0 mV
VA= 3V, IOUT = 200 µA 2.984 V
VA= 3V, IOUT = 1 mA 2.934 V
FSO Full Scale Output VA= 5V, IOUT = 200 µA 4.989 V
VA= 5V, IOUT = 1 mA 4.958 V
VA= 3V, VOUT = 0V, Input Code = 3FFh -56 mA
Output Short Circuit Current
IOS (source) VA= 5V, VOUT = 0V, Input Code = 3FFh -69 mA
VA= 3V, VOUT = 3V, Input Code = 000h 52 mA
IOS Output Short Circuit Current (sink) VA= 5V, VOUT = 5V, Input Code = 000h 75 mA
IOContinuous Output Current(3) Available on each DAC output 11 mA (max)
RL=∞1500 pF
CLMaximum Load Capacitance RL= 2kΩ1500 pF
ZOUT DC Output Impedance 7.5 Ω
REFERENCE INPUT CHARACTERISTICS
Input Range Minimum 0.2 1.0 V (min)
VREFIN Input Range Maximum VAV (max)
Input Impedance 60 kΩ
(1) To ensure accuracy, it is required that VAand VREFIN be well bypassed.
(2) Typical figures are at TJ= 25°C, and represent most likely parametric norms. Test limits are specified to AOQL (Average Outgoing
Quality Level).
(3) This parameter is specified by design and/or characterization and is not tested in production.
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Electrical Characteristics(1) (continued)
The following specifications apply for VA= +2.7V to +5.5V, VREFIN = VA, CL= 200 pF to GND, fSCLK = 30 MHz, input code
range 12 to 1011. Boldface limits apply for TMIN ≤TA≤TMAX and all other limits are at TA= 25°C, unless otherwise
specified. Units
Symbol Parameter Conditions Typical(2) Limits(2) (Limits)
LOGIC INPUT CHARACTERISTICS
IIN Input Current(4) ±1 µA (max)
VA= 3V 0.9 0.6 V (max)
VIL Input Low Voltage(4) VA= 5V 1.5 0.8 V (max)
VA= 3V 1.4 2.1 V (min)
VIH Input High Voltage(4) VA= 5V 2.1 2.4 V (min)
CIN Input Capacitance(4) 3pF (max)
POWER REQUIREMENTS
Supply Voltage Minimum 2.7 V (min)
VASupply Voltage Maximum 5.5 V (max)
VA= 2.7V to 3.6V 210 270 µA (max)
fSCLK = 30 MHz VA= 4.5V to 5.5V 320 410 µA (max)
Normal Supply Current (output
INunloaded) VA= 2.7V to 3.6V 190 µA
fSCLK = 0 VA= 4.5V to 5.5V 290 µA
Power Down Supply Current (output VA= 2.7V to 3.6V 0.10 1.0 µA (max)
IPD unloaded, SYNC = DIN = 0V after All PD Modes(4) VA= 4.5V to 5.5V 0.15 1.0 µA (max)
PD mode loaded) VA= 2.7V to 3.6V 0.6 1.0 mW (max)
fSCLK = 30 MHz VA= 4.5V to 5.5V 1.6 2.3 mW (max)
Normal Supply Power (output
PNunloaded) VA= 2.7V to 3.6V 0.6 mW
fSCLK = 0 VA= 4.5V to 5.5V 1.5 mW
Power Down Supply Current (output VA= 2.7V to 3.6V 0.3 3.6 µW (max)
PPD unloaded, SYNC = DIN = 0V after All PD Modes(4) VA= 4.5V to 5.5V 0.8 5.5 µW (max)
PD mode loaded)
(4) This parameter is specified by design and/or characterization and is not tested in production.
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A.C. and Timing Characteristics
Values shown in this table are design targets and are subject to change before product release.
The following specifications apply for VA= +2.7V to +5.5V, VREFIN = VA, CL= 200 pF to GND, fSCLK = 30 MHz, input code
range 12 to 1011. Boldface limits apply for TMIN ≤TA≤TMAX and all other limits are at TA= 25°C, unless otherwise
specified. Units
Symbol Parameter Conductions Typical(1) Limits(1) (Limits)
fSCLK SCLK Frequency 40 30 MHz (max)
100h to 300h code change
tsOutput Voltage Settling Time(2) 4.5 6µs (max)
RL= 2 kΩ, CL= 200 pF
SR Output Slew Rate 1 V/µs
Glitch Impulse Code change from 200h to 1FFh 12 nV-sec
Digital Feedthrough 0.5 nV-sec
Digital Crosstalk 1 nV-sec
DAC-to-DAC Crosstalk 3 nV-sec
Multiplying Bandwidth VREFIN = 2.5V ± 0.1Vpp 160 kHz
VREFIN = 2.5V ± 1.0Vpp
Total Harmonic Distortion 70 dB
input frequency = 10kHz
VA= 3V 6 µsec
tWU Wake-Up Time VA= 5V 39 µsec
1/fSCLK SCLK Cycle Time 25 33 ns (min)
tCH SCLK High time 7 10 ns (min)
tCL SCLK Low Time 7 10 ns (min)
SYNC Set-up Time prior to SCLK
tSS 410 ns (min)
Falling Edge
Data Set-Up Time prior to SCLK Falling
tDS 1.5 3.5 ns (min)
Edge
Data Hold Time after SCLK Falling
tDH 1.5 3.5 ns (min)
Edge
tCFSR SCLK fall prior to rise of SYNC 0 3ns (min)
tSYNC SYNC High Time 6 10 ns (min)
(1) Typical figures are at TJ= 25°C, and represent most likely parametric norms. Test limits are specified to AOQL (Average Outgoing
Quality Level).
(2) This parameter is specified by design and/or characterization and is not tested in production.
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Specification Definitions
DIFFERENTIAL NON-LINEARITY (DNL) is the measure of the maximum deviation from the ideal step size of 1
LSB, which is VREF / 1024 = VA/ 1024.
DAC-to-DAC CROSSTALK is the glitch impulse transferred to a DAC output in response to a full-scale change
in the output of another DAC.
DIGITAL CROSSTALK is the glitch impulse transferred to a DAC output at mid-scale in response to a full-scale
change in the input register of another DAC.
DIGITAL FEEDTHROUGH is a measure of the energy injected into the analog output of the DAC from the digital
inputs when the DAC outputs are not updated. It is measured with a full-scale code change on the data bus.
FULL-SCALE ERROR is the difference between the actual output voltage with a full scale code (3FFh) loaded
into the DAC and the value of VAx 1023 / 1024.
GAIN ERROR is the deviation from the ideal slope of the transfer function. It can be calculated from Zero and
Full-Scale Errors as GE = FSE - ZE, where GE is Gain error, FSE is Full-Scale Error and ZE is Zero Error.
GLITCH IMPULSE is the energy injected into the analog output when the input code to the DAC register
changes. It is specified as the area of the glitch in nanovolt-seconds.
INTEGRAL NON-LINEARITY (INL) is a measure of the deviation of each individual code from a straight line
through the input to output transfer function. The deviation of any given code from this straight line is measured
from the center of that code value. The end point method is used. INL for this product is specified over a limited
range, per the Electrical Tables.
LEAST SIGNIFICANT BIT (LSB) is the bit that has the smallest value or weight of all bits in a word. This value is
LSB = VREF / 2n(1)
where VREF is the supply voltage for this product, and "n" is the DAC resolution in bits, which is 10 for the
DAC102S085.
MAXIMUM LOAD CAPACITANCE is the maximum capacitance that can be driven by the DAC with output
stability maintained.
MONOTONICITY is the condition of being monotonic, where the DAC has an output that never decreases when
the input code increases.
MOST SIGNIFICANT BIT (MSB) is the bit that has the largest value or weight of all bits in a word. Its value is
1/2 of VA.
MULTIPLYING BANDWIDTH is the frequency at which the output amplitude falls 3dB below the input sine wave
on VREFIN with a full-scale code loaded into the DAC.
POWER EFFICIENCY is the ratio of the output current to the total supply current. The output current comes from
the power supply. The difference between the supply and output currents is the power consumed by the device
without a load.
SETTLING TIME is the time for the output to settle to within 1/2 LSB of the final value after the input code is
updated.
TOTAL HARMONIC DISTORTION (THD) is the measure of the harmonics present at the output of the DACs
with an ideal sine wave applied to VREFIN. THD is measured in dB.
WAKE-UP TIME is the time for the output to exit power-down mode. This is the time from the falling edge of the
16th SCLK pulse to when the output voltage deviates from the power-down voltage of 0V.
ZERO CODE ERROR is the output error, or voltage, present at the DAC output after a code of 000h has been
entered.
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DB15 DB0
SCLK
DIN
SYNC
tSYNC
tDS
tDH
tCL tCH
1 / fSCLK
tCFSR
|
|
||
1 2 13 14 15 16
tSS
OUTPUT
VOLTAGE
DIGITAL INPUT CODE
00 1024
ZE
FSE
GE = FSE - ZE
FSE = GE + ZE
1023 x VREFIN
1024
DAC102S085
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Transfer Characteristic
Figure 1. Input / Output Transfer Characteristic
Timing Diagrams
Figure 2. Serial Timing Diagram
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Typical Performance Characteristics
VREF = VA, fSCLK = 30 MHz, TA= 25C, Input Code Range 12 to 1011, unless otherwise stated
INL at VA= 3.0V INL at VA= 5.0V
Figure 3. Figure 4.
DNL at VA= 3.0V DNL at VA= 5.0V
Figure 5. Figure 6.
INL/DNL vs VREFIN at VA= 3.0V INL/DNL vs VREFIN at VA= 5.0V
Figure 7. Figure 8.
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Typical Performance Characteristics (continued)
VREF = VA, fSCLK = 30 MHz, TA= 25C, Input Code Range 12 to 1011, unless otherwise stated
INL/DNL vs fSCLK at VA= 2.7V INL/DNL vs VA
Figure 9. Figure 10.
INL/DNL vs Clock Duty Cycle at VA= 3.0V INL/DNL vs Clock Duty Cycle at VA= 5.0V
Figure 11. Figure 12.
INL/DNL vs Temperature at VA= 3.0V INL/DNL vs Temperature at VA= 5.0V
Figure 13. Figure 14.
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Typical Performance Characteristics (continued)
VREF = VA, fSCLK = 30 MHz, TA= 25C, Input Code Range 12 to 1011, unless otherwise stated
Zero Code Error vs. VAZero Code Error vs. VREFIN
Figure 15. Figure 16.
Zero Code Error vs. fSCLK Zero Code Error vs. Clock Duty Cycle
Figure 17. Figure 18.
Zero Code Error vs. Temperature Full-Scale Error vs. VA
Figure 19. Figure 20.
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Typical Performance Characteristics (continued)
VREF = VA, fSCLK = 30 MHz, TA= 25C, Input Code Range 12 to 1011, unless otherwise stated
Full-Scale Error vs. VREFIN Full-Scale Error vs. fSCLK
Figure 21. Figure 22.
Full-Scale Error vs. Clock Duty Cycle Full-Scale Error vs. Temperature
Figure 23. Figure 24.
Supply Current vs. VASupply Current vs. Temperature
Figure 25. Figure 26.
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Typical Performance Characteristics (continued)
VREF = VA, fSCLK = 30 MHz, TA= 25C, Input Code Range 12 to 1011, unless otherwise stated
5V Glitch Response Power-On Reset
Figure 27. Figure 28.
3V Wake-Up Time 5V Wake-Up Time
Figure 29. Figure 30.
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VA
R
R
R
R
To Output Amplifier
R
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Functional Description
DAC SECTION
The DAC102S085 is fabricated on a CMOS process with an architecture that consists of switches and resistor
strings that are followed by an output buffer. The reference voltage is externally applied at VREFIN and is shared
by both DACs.
For simplicity, a single resistor string is shown in Figure 31. This string consists of 1024 equal valued resistors
with a switch at each junction of two resistors, plus a switch to ground. The code loaded into the DAC register
determines which switch is closed, connecting the proper node to the amplifier. The input coding is straight
binary with an ideal output voltage of:
VOUTA,B = VREFIN x (D / 1024)
where
• D is the decimal equivalent of the binary code that is loaded into the DAC register. (D can take on any value
between 0 and 1023. This configuration ensures that the DAC is monotonic.) (2)
Figure 31. DAC Resistor String
OUTPUT AMPLIFIERS
The output amplifiers are rail-to-rail, providing an output voltage range of 0V to VAwhen the reference is VA. All
amplifiers, even rail-to-rail types, exhibit a loss of linearity as the output approaches the supply rails (0V and VA,
in this case). For this reason, linearity is specified over less than the full output range of the DAC. However, if the
reference is less than VA, there is only a loss in linearity in the lowest codes. The output capabilities of the
amplifier are described in the Electrical Tables.
The output amplifiers are capable of driving a load of 2 kΩin parallel with 1500 pF to ground or to VA. The zero-
code and full-scale outputs for given load currents are available in the Electrical Characteristics.
REFERENCE VOLTAGE
The DAC102S085 uses a single external reference that is shared by both channels. The reference pin, VREFIN, is
not buffered and has an input impedance of 60 kΩ. It is recommended that VREFIN be driven by a voltage source
with low output impedance. The reference voltage range is 1.0V to VA, providing the widest possible output
dynamic range.
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MSB
A1 A0 OP1 OP0 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0 X X
DATA BITS
0 0 Write to specified register but do not update outputs.
0 1 Write to specified register and update outputs.
1 0 Write to all registers and update outputs.
1 1 Power-down outputs.
LSB
0 0 DAC A
0 1 DAC B
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SERIAL INTERFACE
The three-wire interface is compatible with SPI™, QSPI and MICROWIRE, as well as most DSPs and operates
at clock rates up to 40 MHz. See the Timing Diagrams for information on a write sequence.
A write sequence begins by bringing the SYNC line low. Once SYNC is low, the data on the DIN line is clocked
into the 16-bit serial input register on the falling edges of SCLK. To avoid misclocking data into the shift register,
it is critical that SYNC not be brought low simultaneously with a falling edge of SCLK (see Figure 2). On the 16th
falling clock edge, the last data bit is clocked in and the programmed function (a change in the DAC channel
address, mode of operation and/or register contents) is executed. At this point the SYNC line may be kept low or
brought high. Any data and clock pusles after the 16th falling clock edge will be ignored. In either case, SYNC
must be brought high for the minimum specified time before the next write sequence is initiated with a falling
edge of SYNC.
Since the SYNC and DIN buffers draw more current when they are high, they should be idled low between write
sequences to minimize power consumption.
INPUT SHIFT REGISTER
The input shift register, Figure 32, has sixteen bits. The first bit must be set to "0" and the second bit is an
address bit. The address bit determines whether the register data is for DAC A or DAC B. This bit is followed by
two bits that determine the mode of operation (writing to a DAC register without updating the outputs of both
DACs, writing to a DAC register and updating the outputs of both DACs, writing to the register of both DACs and
updating their outputs, or powering down both outputs). The final twelve bits of the shift register are the data bits.
The data format is straight binary (MSB first, LSB last), with all 0's corresponding to an output of 0V and all 1's
corresponding to a full-scale output of VREFIN - 1 LSB. The contents of the serial input register are transferred to
the DAC register on the sixteenth falling edge of SCLK. See Figure 2.
Figure 32. Input Register Contents
Normally, the SYNC line is kept low for at least 16 falling edges of SCLK and the DAC is updated on the 16th
SCLK falling edge. However, if SYNC is brought high before the 16th falling edge, the data transfer to the shift
register is aborted and the write sequence is invalid. Under this condition, the DAC register is not updated and
there is no change in the mode of operation or in the DAC output voltages.
POWER-ON RESET
The power-on reset circuit controls the output voltages of both DACs during power-up. Upon application of
power, the DAC registers are filled with zeros and the output voltages are 0V. The outputs remain at 0V until a
valid write sequence is made to the DAC.
POWER-DOWN MODES
The DAC102S085 has four power-down modes, two of which are identical. In power-down mode, the supply
current drops to 20 µA at 3V and 30 µA at 5V. The DAC102S085 is set in power-down mode by setting OP1 and
OP0 to 11. Since this mode powers down both DACs, the first two bits of the shift register are used to select
different output terminations for the DAC outputs. Setting A1 and A0 to 00 or 11 causes the outputs to be tri-
stated (a high impedance state). While setting A1 and A0 to 01 or 10 causes the outputs to be terminated by 2.5
kΩor 100 kΩto ground respectively (see Table 1).
Copyright © 2006–2013, Texas Instruments Incorporated Submit Documentation Feedback 15
Product Folder Links: DAC102S085
DAC102S085
SNAS364E –MAY 2006–REVISED MARCH 2013
www.ti.com
Table 1. Power-Down Modes
A1 A0 OP1 OP0 Operating Mode
0 0 1 1 High-Z outputs
0 1 1 1 2.5 kΩto GND
1 0 1 1 100 kΩto GND
1 1 1 1 High-Z outputs
The bias generator, output amplifiers, resistor strings, and other linear circuitry are all shut down in any of the
power-down modes. However, the contents of the DAC registers are unaffected when in power-down. Each DAC
register maintains its value prior to the DAC102S085 being powered down unless it is changed during the write
sequence which instructed it to recover from power down. Minimum power consumption is achieved in the
power-down mode with SYNC and DIN idled low and SCLK disabled. The time to exit power-down (Wake-Up
Time) is typically tWU µsec as stated in the A.C. and Timing Characteristics.
APPLICATIONS INFORMATION
USING REFERENCES AS POWER SUPPLIES
While the simplicity of the DAC102S085 implies ease of use, it is important to recognize that the path from the
reference input (VREFIN) to the VOUTs will have essentially zero Power Supply Rejection Ratio (PSRR).
Therefore, it is necessary to provide a noise-free supply voltage to VREFIN. In order to utilize the full dynamic
range of the DAC102S085, the supply pin (VA) and VREFIN can be connected together and share the same supply
voltage. Since the DAC102S085 consumes very little power, a reference source may be used as the reference
input and/or the supply voltage. The advantages of using a reference source over a voltage regulator are
accuracy and stability. Some low noise regulators can also be used. Listed below are a few reference and power
supply options for the DAC102S085.
LM4130
The LM4130, with its 0.05% accuracy over temperature, is a good choice as a reference source for the
DAC102S085. The 4.096V version is useful if a 0 to 4.095V output range is desirable or acceptable. Bypassing
the LM4130 VIN pin with a 0.1µF capacitor and the VOUT pin with a 2.2µF capacitor will improve stability and
reduce output noise. The LM4130 comes in a space-saving 5-pin SOT23.
Figure 33. The LM4130 as a power supply
LM4050
Available with accuracy of 0.44%, the LM4050 shunt reference is also a good choice as a reference for the
DAC102S085. It is available in 4.096V and 5V versions and comes in a space-saving 3-pin SOT23.
16 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated
Product Folder Links: DAC102S085
LM4050-4.1
or
LM4050-5.0 VOUT = 0V to 5V
0.47 PF
Input
Voltage
RVZ
DAC102S085
DIN
SCLK
SYNC
VA VREFIN
0.1 PF
IZ
IDAC
DAC102S085
www.ti.com
SNAS364E –MAY 2006–REVISED MARCH 2013
Figure 34. The LM4050 as a power supply
The minimum resistor value in the circuit of Figure 34 must be chosen such that the maximum current through
the LM4050 does not exceed its 15 mA rating. The conditions for maximum current include the input voltage at
its maximum, the LM4050 voltage at its minimum, and the DAC102S085 drawing zero current. The maximum
resistor value must allow the LM4050 to draw more than its minimum current for regulation plus the maximum
DAC102S085 current in full operation. The conditions for minimum current include the input voltage at its
minimum, the LM4050 voltage at its maximum, the resistor value at its maximum due to tolerance, and the
DAC102S085 draws its maximum current. These conditions can be summarized as
R(min) = ( VIN(max) −VZ(min) ) /IZ(max) (3)
and R(max) = ( VIN(min) −VZ(max) ) / ( (IDAC(max) + IZ(min) )
where
• VZ(min) and VZ(max) are the nominal LM4050 output voltages ± the LM4050 output tolerance over
temperature
• IZ(max) is the maximum allowable current through the LM4050
• IZ(min) is the minimum current required by the LM4050 for proper regulation
• IDAC(max) is the maximum DAC102S085 supply current (4)
LP3985
The LP3985 is a low noise, ultra low dropout voltage regulator with a 3% accuracy over temperature. It is a good
choice for applications that do not require a precision reference for the DAC102S085. It comes in 3.0V, 3.3V and
5V versions, among others, and sports a low 30 µV noise specification at low frequencies. Since low frequency
noise is relatively difficult to filter, this specification could be important for some applications. The LP3985 comes
in a space-saving 5-pin SOT-23 and 5-bump DSBGA packages.
Figure 35. Using the LP3985 regulator
An input capacitance of 1.0µF without any ESR requirement is required at the LP3985 input, while a 1.0µF
ceramic capacitor with an ESR requirement of 5mΩto 500mΩis required at the output. Careful interpretation
and understanding of the capacitor specification is required to ensure correct device operation.
Copyright © 2006–2013, Texas Instruments Incorporated Submit Documentation Feedback 17
Product Folder Links: DAC102S085
DAC102S085
DIN
SCLK
SYNC VOUT
0.1 PF
+
10 PF+
-
+5V
R1
R2
-5V
+5V
±5V
10 pF
LP2980
1 PF
Input
Voltage
ON /OFF
VIN VOUT
VOUT = 0V to 5V
DAC102S085
DIN
SCLK
SYNC
VA VREFIN
0.1 PF
DAC102S085
SNAS364E –MAY 2006–REVISED MARCH 2013
www.ti.com
LP2980
The LP2980 is an ultra low dropout regulator with a 0.5% or 1.0% accuracy over temperature, depending upon
grade. It is available in 3.0V, 3.3V and 5V versions, among others.
Figure 36. Using the LP2980 regulator
Like any low dropout regulator, the LP2980 requires an output capacitor for loop stability. This output capacitor
must be at least 1.0µF over temperature, but values of 2.2µF or more will provide even better performance. The
ESR of this capacitor should be within the range specified in the LP2980 data sheet. Surface-mount solid
tantalum capacitors offer a good combination of small size and ESR. Ceramic capacitors are attractive due to
their small size but generally have ESR values that are too low for use with the LP2980. Aluminum electrolytic
capacitors are typically not a good choice due to their large size and have ESR values that may be too high at
low temperatures.
BIPOLAR OPERATION
The DAC102S085 is designed for single supply operation and thus has a unipolar output. However, a bipolar
output may be obtained with the circuit in Figure 37. This circuit will provide an output voltage range of ±5 Volts.
A rail-to-rail amplifier should be used if the amplifier supplies are limited to ±5V.
Figure 37. Bipolar Operation
The output voltage of this circuit for any code is found to be
VO= (VAx (D / 1024) x ((R1 + R2) / R1) - VAx R2 / R1) (5)
VO= (10 x D / 1024) - 5V
where
• D is the input code in decimal form (With VA= 5V and R1 = R2) (6)
A list of rail-to-rail amplifiers suitable for this application are indicated in Table 2.
Table 2. Some Rail-to-Rail Amplifiers
AMP PKGS Typ VOS Typ ISUPPLY
LMC7111 DIP-8, SOT23-5 0.9 mV 25 µA
LM7301 SO-8, SOT23-5 0.03 mV 620 µA
LM8261 SOT23-5 0.7 mV 1 mA
18 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated
Product Folder Links: DAC102S085
68HC11 DAC102S085
PC7
SCK
MOSI
SCLK
DIN
SYNC
80C51/80L51 DAC102S085
P3.3
TXD
RXD
SCLK
DIN
SYNC
ADSP-2101/
ADSP2103 DAC102S085
TFS
DT
SCLK
DIN
SCLK
SYNC
DAC102S085
www.ti.com
SNAS364E –MAY 2006–REVISED MARCH 2013
DSP/MICROPROCESSOR INTERFACING
Interfacing the DAC102S085 to microprocessors and DSPs is quite simple. The following guidelines are offered
to hasten the design process.
ADSP-2101/ADSP2103 Interfacing
Figure 38 shows a serial interface between the DAC102S085 and the ADSP-2101/ADSP2103. The DSP should
be set to operate in the SPORT Transmit Alternate Framing Mode. It is programmed through the SPORT control
register and should be configured for Internal Clock Operation, Active Low Framing and 16-bit Word Length.
Transmission is started by writing a word to the Tx register after the SPORT mode has been enabled.
Figure 38. ADSP-2101/2103 Interface
80C51/80L51 Interface
A serial interface between the DAC102S085 and the 80C51/80L51 microcontroller is shown in Figure 39. The
SYNC signal comes from a bit-programmable pin on the microcontroller. The example shown here uses port line
P3.3. This line is taken low when data is transmitted to the DAC102S085. Since the 80C51/80L51 transmits 8-bit
bytes, only eight falling clock edges occur in the transmit cycle. To load data into the DAC, the P3.3 line must be
left low after the first eight bits are transmitted. A second write cycle is initiated to transmit the second byte of
data, after which port line P3.3 is brought high. The 80C51/80L51 transmit routine must recognize that the
80C51/80L51 transmits data with the LSB first while the DAC102S085 requires data with the MSB first.
Figure 39. 80C51/80L51 Interface
68HC11 Interface
A serial interface between the DAC102S085 and the 68HC11 microcontroller is shown in Figure 40. The SYNC
line of the DAC102S085 is driven from a port line (PC7 in the figure), similar to the 80C51/80L51.
The 68HC11 should be configured with its CPOL bit as a zero and its CPHA bit as a one. This configuration
causes data on the MOSI output to be valid on the falling edge of SCLK. PC7 is taken low to transmit data to the
DAC. The 68HC11 transmits data in 8-bit bytes with eight falling clock edges. Data is transmitted with the MSB
first. PC7 must remain low after the first eight bits are transferred. A second write cycle is initiated to transmit the
second byte of data to the DAC, after which PC7 should be raised to end the write sequence.
Figure 40. 68HC11 Interface
Copyright © 2006–2013, Texas Instruments Incorporated Submit Documentation Feedback 19
Product Folder Links: DAC102S085
MICROWIRE
DEVICE DAC102S085
CS
SK
SO
SCLK
DIN
SYNC
DAC102S085
SNAS364E –MAY 2006–REVISED MARCH 2013
www.ti.com
Microwire Interface
Figure 41 shows an interface between a Microwire compatible device and the DAC102S085. Data is clocked out
on the rising edges of the SK signal. As a result, the SK of the Microwire device needs to be inverted before
driving the SCLK of the DAC102S085.
Figure 41. Microwire Interface
LAYOUT, GROUNDING, AND BYPASSING
For best accuracy and minimum noise, the printed circuit board containing the DAC102S085 should have
separate analog and digital areas. The areas are defined by the locations of the analog and digital power planes.
Both of these planes should be located in the same board layer. There should be a single ground plane. A single
ground plane is preferred if digital return current does not flow through the analog ground area. Frequently a
single ground plane design will utilize a "fencing" technique to prevent the mixing of analog and digital ground
current. Separate ground planes should only be utilized when the fencing technique is inadequate. The separate
ground planes must be connected in one place, preferably near the DAC102S085. Special care is required to
ensure that digital signals with fast edge rates do not pass over split ground planes. They must always have a
continuous return path below their traces.
The DAC102S085 power supply should be bypassed with a 10µF and a 0.1µF capacitor as close as possible to
the device with the 0.1µF right at the device supply pin. The 10µF capacitor should be a tantalum type and the
0.1µF capacitor should be a low ESL, low ESR type. The power supply for the DAC102S085 should only be
used for analog circuits.
Avoid crossover of analog and digital signals and keep the clock and data lines on the component side of the
board. The clock and data lines should have controlled impedances.
20 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated
Product Folder Links: DAC102S085
DAC102S085
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SNAS364E –MAY 2006–REVISED MARCH 2013
REVISION HISTORY
Changes from Revision D (March 2013) to Revision E Page
• Changed layout of National Data Sheet to TI format .......................................................................................................... 20
Copyright © 2006–2013, Texas Instruments Incorporated Submit Documentation Feedback 21
Product Folder Links: DAC102S085
PACKAGE OPTION ADDENDUM
www.ti.com 1-Nov-2013
Addendum-Page 1
PACKAGING INFORMATION
Orderable Device Status
(1)
Package Type Package
Drawing Pins Package
Qty Eco Plan
(2)
Lead/Ball Finish
(6)
MSL Peak Temp
(3)
Op Temp (°C) Device Marking
(4/5)
Samples
DAC102S085CIMM NRND VSSOP DGS 10 1000 TBD Call TI Call TI -40 to 105 X74C
DAC102S085CIMM/NOPB ACTIVE VSSOP DGS 10 1000 Green (RoHS
& no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 105 X74C
DAC102S085CIMMX/NOPB ACTIVE VSSOP DGS 10 3500 Green (RoHS
& no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 105 X74C
DAC102S085CISD/NOPB ACTIVE WSON DSC 10 1000 Green (RoHS
& no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 105 X75C
DAC102S085CISDX/NOPB ACTIVE WSON DSC 10 4500 Green (RoHS
& no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 105 X75C
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6) Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
PACKAGE OPTION ADDENDUM
www.ti.com 1-Nov-2013
Addendum-Page 2
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device Package
Type Package
Drawing Pins SPQ Reel
Diameter
(mm)
Reel
Width
W1 (mm)
A0
(mm) B0
(mm) K0
(mm) P1
(mm) W
(mm) Pin1
Quadrant
DAC102S085CIMM VSSOP DGS 10 1000 178.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1
DAC102S085CIMM/NOPB VSSOP DGS 10 1000 178.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1
DAC102S085CIMMX/NOP
BVSSOP DGS 10 3500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1
DAC102S085CISD/NOPB WSON DSC 10 1000 178.0 12.4 3.3 3.3 1.0 8.0 12.0 Q1
DAC102S085CISDX/NOP
BWSON DSC 10 4500 330.0 12.4 3.3 3.3 1.0 8.0 12.0 Q1
PACKAGE MATERIALS INFORMATION
www.ti.com 23-Sep-2013
Pack Materials-Page 1
*All dimensions are nominal
Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)
DAC102S085CIMM VSSOP DGS 10 1000 210.0 185.0 35.0
DAC102S085CIMM/NOPB VSSOP DGS 10 1000 210.0 185.0 35.0
DAC102S085CIMMX/NOP
BVSSOP DGS 10 3500 367.0 367.0 35.0
DAC102S085CISD/NOPB WSON DSC 10 1000 210.0 185.0 35.0
DAC102S085CISDX/NOP
BWSON DSC 10 4500 367.0 367.0 35.0
PACKAGE MATERIALS INFORMATION
www.ti.com 23-Sep-2013
Pack Materials-Page 2
MECHANICAL DATA
DSC0010A
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SDA10A (Rev A)
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