30 MHz to 2 GHz Quadrature Demodulator ADL5387 Data Sheet FUNCTIONAL BLOCK DIAGRAM Operating RF frequency 30 MHz to 2 GHz LO input at 2 x fLO 60 MHz to 4 GHz Input IP3: 31 dBm at 900 MHz Input IP2: 62 dBm at 900 MHz Input P1dB: 13 dBm at 900 MHz Noise figure (NF) 12.0 dB at 140 MHz 14.7 dB at 900 MHz Voltage conversion gain > 4 dB Quadrature demodulation accuracy Phase accuracy ~0.4 Amplitude balance ~0.05 dB Demodulation bandwidth ~240 MHz Baseband I/Q drive 2 V p-p into 200 Single 5 V supply 24 23 22 20 21 19 1 CMRF CMRF RFIP RFIN CMRF VPX VPB 18 VPA 2 COM 3 BIAS 4 VPL 5 VPL 6 VPL CML 7 VPB 17 QHI 16 DIVIDE-BY-2 PHASE SPLITTER QLO 15 IHI 14 ILO 13 LOIP LOIN CML CML COM 9 11 12 8 10 06764-001 FEATURES Figure 1. APPLICATIONS QAM/QPSK RF/IF demodulators W-CDMA/CDMA/CDMA2000/GSM Microwave point-to-(multi)point radios Broadband wireless and WiMAX Broadband CATVs GENERAL DESCRIPTION The ADL5387 is a broadband quadrature I/Q demodulator that covers an RF/IF input frequency range from 30 MHz to 2 GHz. With a NF = 13.2 dB, IP1dB = 12.7 dBm, and IIP3 = 32 dBm at 450 MHz, the ADL5387 demodulator offers outstanding dynamic range suitable for the demanding infrastructure direct-conversion requirements. The differential RF/IF inputs provide a wellbehaved broadband input impedance of 50 and are best driven from a 1:1 balun for optimum performance. The fully balanced design minimizes effects from second-order distortion. The leakage from the LO port to the RF port is <-70 dBc. Differential dc-offsets at the I and Q outputs are <10 mV. Both of these factors contribute to the excellent IIP2 specifications > 60 dBm. Ultrabroadband operation is achieved with a divide-by-2 method for local oscillator (LO) quadrature generation. Over a wide range of LO levels, excellent demodulation accuracy is achieved with amplitude and phase balances ~0.05 dB and ~0.4, respectively. The demodulated in-phase (I) and quadrature (Q) differential outputs are fully buffered and provide a voltage conversion gain of >4 dB. The buffered baseband outputs are capable of driving a 2 V p-p differential signal into 200 . The ADL5387 is fabricated using the Analog Devices, Inc., advanced silicon-germanium bipolar process and is available in a 24-lead exposed paddle LFCSP. Rev. B The ADL5387 operates off a single 4.75 V to 5.25 V supply. The supply current is adjustable with an external resistor from the BIAS pin to ground. Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 (c)2007-2013 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com ADL5387 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Mixers .......................................................................................... 15 Applications ....................................................................................... 1 Emitter Follower Buffers ........................................................... 15 Functional Block Diagram .............................................................. 1 Bias Circuit .................................................................................. 15 General Description ......................................................................... 1 Applications Information .............................................................. 16 Revision History ............................................................................... 2 Basic Connections ...................................................................... 16 Specifications..................................................................................... 3 Power Supply............................................................................... 16 Absolute Maximum Ratings............................................................ 5 Local Oscillator (LO) Input ...................................................... 16 ESD Caution .................................................................................. 5 RF Input ....................................................................................... 17 Pin Configuration and Function Descriptions ............................. 6 Baseband Outputs ...................................................................... 17 Typical Performance Characteristics ............................................. 7 Error Vector Magnitude (EVM) Performance ....................... 18 Distributions for fRF = 140 MHz ............................................... 11 Low IF Image Rejection............................................................. 19 Distributions for fRF = 450 MHz ............................................... 12 Example Baseband Interface ..................................................... 19 Distributions for fRF = 900 MHz ............................................... 13 Characterization Setups ................................................................. 22 Distributions for fRF = 1900 MHz ............................................. 14 Evaluation Board ............................................................................ 24 Circuit Description ......................................................................... 15 Outline Dimensions ....................................................................... 27 LO Interface................................................................................. 15 Ordering Guide .......................................................................... 27 V-to-I Converter ......................................................................... 15 REVISION HISTORY 10/13--Rev. A to Rev. B Added Figure 4, Figure 6, and Figure 8; Renumbered Sequentially ....................................................................................... 7 Moved Figure 9, Added Figure 10 .................................................. 8 Changes to Figure 25 ...................................................................... 11 Changes to Figure 31 ...................................................................... 12 Updated Outline Dimensions ....................................................... 27 Changes to Ordering Guide .......................................................... 27 5/13--Rev. 0 to Rev. A Changed Minimum Operating RF Frequency from 50 MHz to 30 MHz (Throughout) ..................................................................... 1 Changed Minimum LO Input at 2 x fLO from 100 MHz to 60 MHz (Throughout) ..................................................................... 1 Added Dynamic Performance @ RF = 30 MHz Parameters ...... 3 Changes to Local Oscillator (LO) Input Section ........................ 15 Changes to Table 4 .......................................................................... 24 Updated Outline Dimensions ....................................................... 26 Changes to Ordering Guide .......................................................... 26 10/07--Revision 0: Initial Version Rev. B | Page 2 of 28 Data Sheet ADL5387 SPECIFICATIONS VS = 5 V, TA = 25C, fRF = 900 MHz, fIF = 4.5 MHz, PLO = 0 dBm, BIAS pin open, ZO = 50 , unless otherwise noted, baseband outputs differentially loaded with 450 . Table 1. Parameter OPERATING CONDITIONS LO Frequency Range RF Frequency Range LO INPUT Input Return Loss LO Input Level I/Q BASEBAND OUTPUTS Voltage Conversion Gain Demodulation Bandwidth Quadrature Phase Error I/Q Amplitude Imbalance Output DC Offset (Differential) Output Common-Mode 0.1 dB Gain Flatness Output Swing Peak Output Current POWER SUPPLIES Voltage Current DYNAMIC PERFORMANCE at RF = 30 MHz Conversion Gain Input P1dB (IP1dB) Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) I/Q Magnitude Imbalance I/Q Phase Imbalance DYNAMIC PERFORMANCE at RF = 140 MHz Conversion Gain Input P1dB (IP1dB) Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO I/Q Magnitude Imbalance I/Q Phase Imbalance LO to I/Q Noise Figure Noise Figure under Blocking Conditions Condition Min External input = 2xLO frequency 0.06 0.03 Typ Max Unit 4 2 GHz GHz LOIP, LOIN -10 AC-coupled into LOIP with LOIN bypassed, measured at 2 GHz -6 QHI, QLO, IHI, ILO 450 differential load on I and Q outputs (at 900 MHz) 200 differential load on I and Q outputs (at 900 MHz) 1 V p-p signal 3 dB bandwidth at 900 MHz 0 dBm LO input Differential 200 load Each pin VPA, VPL, VPB, VPX 0 -5 dBm each input tone -5 dBm each input tone +6 dBm 4.3 dB 3.2 dB 240 0.4 0.1 5 VPOS - 2.8 40 2 12 MHz Degrees dB mV V MHz V p-p mA 4.75 BIAS pin open RBIAS = 4 k RFIP, RFIN, L1, L2 = 680 nH, C10, C11 = 0.01 F1 dB 180 157 5.25 V mA mA 4.5 12 69 31 0.1 0.3 dB dBm dBm dBm dB Degrees 4.7 13 67 31 -100 dB dBm dBm dBm dBm -95 0.05 0.2 -39 dBc dB Degrees dBm 12.0 14.4 dB dB RFIP, RFIN -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 , 1xLO appearing at the RF port LOIN, LOIP terminated in 50 RFIN, RFIP terminated in 50 , 1xLO appearing at the BB port With a -5 dBm interferer 5 MHz away Rev. B | Page 3 of 28 ADL5387 Parameter DYNAMIC PERFORMANCE at RF = 450 MHz Conversion Gain Input P1dB (IP1dB) Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO I/Q Magnitude Imbalance I/Q Phase Imbalance LO to I/Q Noise Figure DYNAMIC PERFORMANCE at RF = 900 MHz Conversion Gain Input P1dB (IP1dB) Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO I/Q Magnitude Imbalance I/Q Phase Imbalance LO to I/Q Noise Figure Noise Figure under Blocking Conditions DYNAMIC PERFORMANCE at RF = 1900 MHz Conversion Gain Input P1dB (IP1dB) Second-Order Input Intercept (IIP2) Third-Order Input Intercept (IIP3) LO to RF RF to LO I/Q Magnitude Imbalance I/Q Phase Imbalance LO to I/Q Noise Figure Noise Figure under Blocking Conditions 1 Data Sheet Condition Min -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 , 1xLO appearing at the RF port LOIN, LOIP terminated in 50 RFIN, RFIP terminated in 50 , 1xLO appearing at the BB port -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 , 1xLO appearing at the RF port LOIN, LOIP terminated in 50 RFIN, RFIP terminated in 50 , 1XLO appearing at the BB port With a -5 dBm interferer 5 MHz away -5 dBm each input tone -5 dBm each input tone RFIN, RFIP terminated in 50 , 1xLO appearing at the RF port LOIN, LOIP terminated in 50 RFIN, RFIP terminated in 50 , 1xLO appearing at the BB port With a -5 dBm interferer 5 MHz away See Figure 64 for locations of L1, L2, C10, and C11. Rev. B | Page 4 of 28 Typ Max Unit 4.4 12.7 69.2 32.8 -87 dB dBm dBm dBm dBm -90 0.05 0.6 -38 dBc dB Degrees dBm 13.2 dB 4.3 12.8 61.7 31.2 -79 dB dBm dBm dBm dBm -88 0.05 0.2 -41 dBc dB Degrees dBm 14.7 15.8 dB dB 3.8 12.8 59.8 27.4 -75 dB dBm dBm dBm dBm -70 0.05 0.3 -43 dBc dB Degrees dBm 16.5 18.7 dB dB Data Sheet ADL5387 ABSOLUTE MAXIMUM RATINGS ESD CAUTION Table 2. Parameter Supply Voltage VPOS1, VPOS2, VPOS3 LO Input Power RF/IF Input Power Internal Maximum Power Dissipation JA Maximum Junction Temperature Operating Temperature Range Storage Temperature Range Rating 5.5 V 13 dBm (re: 50 ) 15 dBm (re: 50 ) 1100 mW 54C/W 150C -40C to +85C -65C to +125C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. B | Page 5 of 28 ADL5387 Data Sheet PIN CONFIGURATION AND FUNCTION DESCRIPTIONS 24 23 22 21 20 19 1 CMRF CMRF RFIP RFIN CMRF VPX VPB 18 VPA 2 COM 3 BIAS VPB 17 QHI 16 ADL5387 VPL 5 VPL 6 VPL CML 7 TOP VIEW (Not to Scale) QLO 15 IHI 14 ILO 13 LOIP LOIN CML 8 9 10 CML COM 11 12 06764-002 4 Figure 2. Pin Configuration Table 3. Pin Function Descriptions Pin No. 1, 4 to 6, 17 to 19 2, 7, 10 to 12, 20, 23, 24 3 Mnemonic VPA, VPL, VPB, VPX 8, 9 LOIP, LOIN 13 to 16 ILO, IHI, QLO, QHI 21, 22 RFIN, RFIP COM, CML, CMRF BIAS EP Description Supply. Positive supply for LO, IF, biasing and baseband sections, respectively. These pins should be decoupled to board ground using appropriate sized capacitors. Ground. Connect to a low impedance ground plane. Bias Control. A resistor can be connected between BIAS and COM to reduce the mixer core current. The default setting for this pin is open. Local Oscillator. External LO input is at 2xLO frequency. A single-ended LO at 0 dBm can be applied through a 1000 pF capacitor to LOIP. LOIN should be ac-grounded, also using a 1000 pF. These inputs can also be driven differentially through a balun (recommended balun is M/A-COM ETC1-1-13). I-Channel and Q-Channel Mixer Baseband Outputs. These outputs have a 50 differential output impedance (25 per pin). The bias level on these pins is equal to VPOS - 2.8 V. Each output pair can swing 2 V p-p (differential) into a load of 200 . Output 3 dB bandwidth is 240 MHz. RF Input. A single-ended 50 signal can be applied to the RF inputs through a 1:1 balun (recommended balun is M/A-COM ETC1-1-13). Ground-referenced inductors must also be connected to RFIP and RFIN (recommended values = 120 nH). Exposed Paddle. Connect to a low impedance ground plane. Rev. B | Page 6 of 28 Data Sheet ADL5387 TYPICAL PERFORMANCE CHARACTERISTICS VS = 5 V, TA = 25C, LO drive level = 0 dBm, RBIAS = open, unless otherwise noted. 20 80 IIP2 70 INPUT P1dB 15 60 IIP2, IIP3 (dBm) 10 GAIN 50 40 IIP3 30 5 20 0 200 400 600 800 1000 1200 1400 1600 1800 2000 RF FREQUENCY (MHz) 10 20 06764-003 0 Figure 3. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs. RF Frequency 30 40 50 60 70 80 90 100 110 120 130 FREQUENCY (MHz) Figure 6. Input Third-Order Intercept (IIP3) and Input Second-Order Intercept Point (IIP2) vs. RF Frequency (Low Frequency Range) 2.0 20 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 1.5 15 MAGNITUDE ERROR (dB) GAIN (dB), IP1dB (dBm) TA = -40C TA = +25C TA = +85C 06764-106 GAIN (dB), IP1dB (dBm) TA = -40C TA = +25C TA = +85C INPUT P1dB 10 GAIN 5 1.0 0.5 0 -0.5 -1.0 40 50 60 70 80 90 100 110 120 130 FREQUENCY (MHz) -2.0 0 2.0 TA = +85C TA = +25C TA = -40C MAGNITUDE ERROR (dB) 1.5 INPUT IP2 50 40 30 20 0 200 -0.5 -1.0 -2.0 20 800 1000 1200 1400 1600 1800 2000 RF FREQUENCY (MHz) Figure 5. Input Third-Order Intercept (IIP3) and Input Second-Order Intercept Point (IIP2) vs. RF Frequency TA = -40C TA = +25C TA = +85C 0 400 600 1000 1200 1400 1600 1800 2000 0.5 -1.5 10 800 1.0 INPUT IP3 (I AND Q CHANNELS) 06764-004 IIP2, IIP3 (dBm) 60 600 Figure 7. I/Q Gain Mismatch vs. RF Frequency 80 70 400 RF FREQUENCY (MHz) Figure 4. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs. RF Frequency (Low Frequency Range) I CHANNEL Q CHANNEL 200 30 40 50 60 70 80 90 FREQUENCY (MHz) 100 110 120 130 06764-108 30 06764-104 0 20 06764-005 -1.5 Figure 8. I/Q Gain Mismatch vs. RF Frequency (Low Frequency Range) Rev. B | Page 7 of 28 ADL5387 19 TA = -40C TA = +25C TA = +85C 3 TA = -40C TA = +25C TA = +85C 17 NOISE FIGURE (dB) 2 1 0 -1 15 13 11 -2 600 800 1000 1200 1400 1600 1800 2000 RF FREQUENCY (MHz) 7 0 200 GAIN (dB), INPUT P1dB (dBm), NOISE FIGURE (dB) 1 0 -1 -2 -3 30 40 50 60 70 80 90 FREQUENCY (MHz) 100 110 120 130 06764-110 QUADRATURE PHASE ERROR (Degrees) 2 -4 20 20 80 INPUT IP2, Q CHANNEL 15 65 INPUT IP2, I CHANNEL INPUT P1dB 10 GAIN 5 35 INPUT IP3 0 -6 32 IIP3 (dBm) AND NOISE FIGURE (dB) -5 -10 -15 -20 -25 1000 BB FREQUENCY (MHz) Figure 11. Normalized I/Q Baseband Frequency Response 28 -4 -3 -2 -1 0 1 2 3 4 5 6 20 195 185 INPUT IP3 24 175 SUPPLY CURRENT 20 16 NOISE FIGURE 12 8 06764-006 BB RESPONSE (dB) 0 100 -5 TA = -40C TA = +25C TA = +85C NORMALIZED TO 1MHz 10 50 NOISE FIGURE Figure 13. Conversion Gain, Noise Figure, IIP3, IIP2, and IP1dB vs. LO Level, fRF = 140 MHz 5 1 1000 1200 1400 1600 1800 2000 LO LEVEL (dBm) Figure 10. I/Q Quadrature Phase Error vs. RF Frequency (Low Frequency Range) -30 800 Figure 12. Noise Figure vs. RF Frequency TA = -40C TA = +25C TA = +85C 3 600 RF FREQUENCY (MHz) Figure 9. I/Q Quadrature Phase Error vs. RF Frequency 4 400 INPUT IP2, INPUT IP3 (dBm) 400 06764-009 200 165 155 SUPPLY CURRENT (mA) 0 145 1 10 135 100 RBIAS (k) Figure 14. Noise Figure, IIP3, and Supply Current vs. RBIAS, fRF = 140 MHz Rev. B | Page 8 of 28 06764-010 -4 06764-007 9 -3 06764-008 QUADRATURE PHASE ERROR (Degrees) 4 Data Sheet Data Sheet ADL5387 15 RBIAS = 4k RBIAS = 1.4k -25 -20 -15 -10 -5 0 5 RF BLOCKER INPUT POWER (dBm) 450MHz: IIP2, I CHANNEL 450MHz: IIP2, Q CHANNEL 20 10 0 10 Figure 18. Conversion Gain, IP1dB, IIP2 I Channel, and IIP2 Q Channel vs. RBIAS 35 80 10 50 GAIN 5 35 IIP3 70 20 15 60 10 -4 -3 -2 -1 0 1 2 3 4 5 TA = -40C TA = +25C TA = +85C 6 LO LEVEL (dBm) 0 5 10 15 20 25 30 35 40 45 50 50 BB FREQUENCY (MHz) Figure 16. Conversion Gain, Noise Figure, IIP3, IIP2, and IP1dB vs. LO Level, fRF = 900 MHz Figure 19. IIIP3, IIP2, IP1dB vs. Baseband Frequency 32 0 TA = -40C TA = +25C TA = +85C 28 55 IP1dB 5 06764-012 20 -5 65 INPUT IP2, Q CHANNEL INPUT IP3 0 -6 75 INPUT IP2, I CHANNEL 25 IP1dB, IIP3 (dBm) INPUT P1dB INPUT IP2, INPUT IP3 (dBm) 30 65 INPUT IP2, Q CHANNEL 100 NOISE FIGURE 15 -10 FEEDTHROUGH (dBm) INPUT IP3 24 20 NOISE FIGURE 16 -20 -30 1xLO (INTERNAL) -40 -50 2xLO (EXTERNAL) -60 12 -70 8 1 10 RBIAS (k) Figure 17. IIP3 and Noise Figure vs. RBIAS, fRF = 900 MHz 100 -80 06764-013 IIP3 (dBm) AND NOISE FIGURE (dB) GAIN (dB), INPUT P1dB (dBm), NOISE FIGURE (dB) 450MHz: IP1dB 30 RBIAS (k) 80 INPUT IP2, I CHANNEL 140MHz: IIP2, Q CHANNEL 450MHz: GAIN 1 Figure 15. Noise Figure vs. Input Blocker Level, fRF = 900 MHz (RF Blocker 5 MHz Offset) 20 140MHz: IIP2, I CHANNEL 40 INPUT IP2, I AND Q CHANNELS (dBm) 0 -30 06764-011 5 140MHz: GAIN 140MHz: IP1dB 50 06764-015 10 60 0 200 400 600 800 1000 1200 1400 1600 1800 2000 INTERNAL 1xLO FREQUENCY (MHz) 06764-016 NOISE FIGURE (dB) RBIAS = 10k 70 06764-014 20 RBIAS = 100k 80 GAIN (dB), IP1dB, IIP2, I AND Q CHANNELS (dBm) 25 Figure 20. LO-to-BB Feedthrough vs. 1xLO Frequency (Internal LO Frequency) Rev. B | Page 9 of 28 Data Sheet 0 -20 -5 -40 LEAKAGE (dBc) -10 -15 -60 -80 -100 -20 0 200 400 600 800 1000 1200 1400 1600 1800 2000 RF FREQUENCY (MHz) -120 06764-017 -25 0 200 400 600 800 1000 1200 1400 1600 1800 2000 RF FREQUENCY (MHz) Figure 21. RF Port Return Loss vs. RF Frequency, Measured on Characterization Board through ETC1-1-13 Balun with 120 nH Bias Inductors 06764-019 RETURN LOSS (dB) ADL5387 Figure 23. RF-to-LO Leakage vs. RF Frequency -20 0 -30 -5 RETURN LOSS (dB) LO LEAKAGE (dBm) -40 -50 -60 1xLO -70 -10 -15 -20 -80 -25 -90 0 200 400 600 800 1000 1200 1400 1600 1800 2000 INTERNAL 1xLO FREQUENCY (MHz) Figure 22. LO-to-RF Leakage vs. Internal 1xLO Frequency -30 0 500 1000 1500 2000 2500 3000 3500 FREQUENCY (MHz) Figure 24. Single-Ended LO Port Return Loss vs. LO Frequency, LOIN AC-Coupled to Ground Rev. B | Page 10 of 28 4000 06764-020 -100 06764-018 2xLO Data Sheet ADL5387 DISTRIBUTIONS FOR fRF = 140 MHz 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 60 40 60 40 31 30 32 33 INPUT IP3 (dBm) 0 60 06764-121 29 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) PERCENTAGE (%) 80 60 40 20 60 40 20 13 12 14 15 0 10.5 06764-022 11 INPUT P1dB (dBm) 11.0 11.5 12.0 13.0 12.5 13.5 NOISE FIGURE (dB) Figure 26. IP1dB Distributions Figure 29. Noise Figure Distributions 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 80 60 40 20 60 40 20 -0.1 0 0.1 I/Q GAIN MISMATCH (dB) 0.2 06764-023 PERCENTAGE (%) 75 Figure 28. IIP2 Distributions for I Channel and Q Channel 100 0 -0.2 70 INPUT IP2 (dBm) Figure 25. IIP3 Distributions 0 10 65 06764-024 20 20 0 28 I CHANNEL Q CHANNEL 06764-025 PERCENTAGE (%) 80 Figure 27. I/Q Gain Mismatch Distributions 0 -1.0 -0.5 0 0.5 QUADRATURE PHASE ERROR (Degrees) Figure 30. I/Q Quadrature Error Distributions Rev. B | Page 11 of 28 1.0 06764-026 100 ADL5387 Data Sheet DISTRIBUTIONS FOR fRF = 450 MHz 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 60 40 60 40 32 33 34 35 INPUT IP3 (dBm) 0 60 06764-127 31 70 65 75 INPUT IP2 (dBm) Figure 34. IIP2 Distributions for I Channel and Q Channel Figure 31. IIP3 Distributions 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 60 40 60 40 20 20 12 13 14 15 INPUT P1dB (dBm) 0 12.0 06764-028 11 13.5 14.0 14.5 15.0 Figure 35. Noise Figure Distributions 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 80 60 40 60 40 20 20 -0.1 0 0.1 I/Q GAIN MISMATCH (dB) 0.2 06764-029 PERCENTAGE (%) 13.0 NOISE FIGURE (dB) Figure 32. IP1dB Distributions 0 -0.2 12.5 06764-031 PERCENTAGE (%) 80 0 10 06764-030 20 20 0 30 I CHANNEL Q CHANNEL 0 -1.0 -0.5 0 0.5 QUADRATURE PHASE ERROR (Degrees) Figure 36. I/Q Quadrature Error Distributions Figure 33. I/Q Gain Mismatch Distributions Rev. B | Page 12 of 28 1.0 06764-032 PERCENTAGE (%) 80 Data Sheet ADL5387 DISTRIBUTIONS FOR fRF = 900 MHz 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 60 40 40 20 32 31 34 33 35 INPUT IP3 (dBm) 0 55 06764-033 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) PERCENTAGE (%) 80 60 40 60 40 20 20 12 14 13 15 0 13.0 06764-034 11 INPUT P1dB (dBm) 13.5 14.0 14.5 15.0 15.5 16.0 NOISE FIGURE (dB) Figure 38. IP1dB Distributions Figure 41. Noise Figure Distributions 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 80 60 40 20 60 40 20 -0.1 0 0.1 I/Q GAIN MISMATCH (dB) 0.2 06764-035 PERCENTAGE (%) 75 Figure 40. IIP2 Distributions for I Channel and Q Channel 100 0 -0.2 70 65 INPUT IP2 (dBm) Figure 37. IIP3 Distributions 0 10 60 06764-037 0 30 60 06764-036 20 I CHANNEL Q CHANNEL Figure 39. I/Q Gain Mismatch Distributions 0 -1.0 -0.5 0 0.5 QUADRATURE PHASE ERROR (Degrees) Figure 42. I/Q Quadrature Error Distributions Rev. B | Page 13 of 28 1.0 06764-038 PERCENTAGE (%) 80 ADL5387 Data Sheet DISTRIBUTIONS FOR fRF = 1900 MHz 100 100 TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) PERCENTAGE (%) 80 60 40 60 40 TA = -40C TA = +25C TA = +85C 20 20 27 28 29 30 31 INPUT IP3 (dBm) 0 52 06764-039 54 56 66 68 TA = -40C TA = +25C TA = +85C 80 80 PERCENTAGE (%) 60 40 20 60 40 20 12 13 14 15 INPUT P1dB (dBm) 0 15.0 06764-040 11 15.5 16.0 16.5 17.0 17.5 18.0 NOISE FIGURE (dB) Figure 44. IP1dB Distributions 06764-043 PERCENTAGE (%) 64 100 TA = -40C TA = +25C TA = +85C Figure 47. Noise Figure Distributions 100 100 TA = -40C TA = +25C TA = +85C TA = -40C TA = +25C TA = +85C 80 PERCENTAGE (%) 80 60 40 20 60 40 20 -0.1 0 0.1 I/Q GAIN MISMATCH (dB) 0.2 06764-041 PERCENTAGE (%) 62 Figure 46. IIP2 Distributions for I Channel and Q Channel 100 0 -0.2 60 INPUT IP2 (dBm) Figure 43. IIP3 Distributions 0 10 58 Figure 45. I/Q Gain Mismatch Distributions 0 -1.0 -0.5 0 0.5 QUADRATURE PHASE ERROR (Degrees) Figure 48. I/Q Quadrature Error Distributions Rev. B | Page 14 of 28 1.0 06764-044 0 26 06764-042 I CHANNEL Q CHANNEL Data Sheet ADL5387 CIRCUIT DESCRIPTION The ADL5387 can be divided into five sections: the local oscillator (LO) interface, the RF voltage-to-current (V-to-I) converter, the mixers, the differential emitter follower outputs, and the bias circuit. A detailed block diagram of the device is shown in Figure 49. BIAS The ADL5387 has two double-balanced mixers: one for the in-phase channel (I channel) and one for the quadrature channel (Q channel). These mixers are based on the Gilbert cell design of four cross-connected transistors. The output currents from the two mixers are summed together in the resistive loads that then feed into the subsequent emitter follower buffers. ILO LOIP RFIN The differential RF input signal is applied to a resistively degenerated common base stage, which converts the differential input voltage to output currents. The output currents then modulate the two half-frequency LO carriers in the mixer stage. MIXERS IHI RFIP V-TO-I CONVERTER EMITTER FOLLOWER BUFFERS DIVIDE-BY-TWO QUADRATURE PHASE SPLITTER The output emitter followers drive the differential I and Q signals off-chip. The output impedance is set by on-chip 25 series resistors that yield a 50 differential output impedance for each baseband port. The fixed output impedance forms a voltage divider with the load impedance that reduces the effective gain. For example, a 500 differential load has 1 dB lower effective gain than a high (10 k) differential load impedance. LOIN QLO 06764-045 QHI Figure 49. Block Diagram The LO interface generates two LO signals at 90 of phase difference to drive two mixers in quadrature. RF signals are converted into currents by the V-to-I converters that feed into the two mixers. The differential I and Q outputs of the mixers are buffered via emitter followers. Reference currents to each section are generated by the bias circuit. A detailed description of each section follows. LO INTERFACE The LO interface consists of a buffer amplifier followed by a frequency divider that generate two carriers at half the input frequency and in quadrature with each other. Each carrier is then amplified and amplitude-limited to drive the doublebalanced mixers. BIAS CIRCUIT A band gap reference circuit generates the proportional-toabsolute temperature (PTAT) as well as temperature-independent reference currents used by different sections. The mixer current can be reduced via an external resistor between the BIAS pin and ground. When the BIAS pin is open, the mixer runs at maximum current and hence the greatest dynamic range. The mixer current can be reduced by placing a resistance to ground; therefore, reducing overall power consumption, noise figure, and IIP3. The effect on each of these parameters is shown in Figure 14, Figure 17, and Figure 18. Rev. B | Page 15 of 28 ADL5387 Data Sheet APPLICATIONS INFORMATION BASIC CONNECTIONS LO INPUT Figure 51 shows the basic connections schematic for the ADL5387. LOIN Figure 50. Single-Ended LO Drive The recommended LO drive level is between -6 dBm and +6 dBm. For operation below 50 MHz, a minimum LO drive level of 0 dBm should be used. The LO frequency at the input to the device should be twice that of the desired LO frequency at the mixer core. The applied LO frequency range is between 60 MHz and 4 GHz. LOCAL OSCILLATOR (LO) INPUT The LO port is driven in a single-ended manner. The LO signal must be ac-coupled via a 1000 pF capacitor directly into LOIP, and LOIN is ac-coupled to ground also using a 1000 pF capacitor. The LO port is designed for a broadband 50 match and therefore exhibits excellent return loss from 60 MHz to 4 GHz. The LO return loss can be seen in Figure 24. Figure 50 shows the LO input configuration. ETC1-1-13 RFC 120nH 120nH 23 22 21 20 19 CMRF CMRF RFIP RFIN CMRF VPX 1000pF 1000pF 24 1 VPA 9 1000pF The nominal voltage supply for the ADL5387 is 5 V and is applied to the VPA, VPB, VPL, and VPX pins. Ground should be connected to the COM, CML, and CMRF pins. Each of the supply pins should be decoupled using two capacitors; recommended capacitor values are 100 pF and 0.1 F. 0.1F LOIP 06764-047 POWER SUPPLY VPOS 8 1000pF VPOS VPB 18 100pF 100pF 2 COM 0.1F VPB 17 3 BIAS QHI 16 QHI ADL5387 5 VPL IHI 14 6 VPL ILO 13 LOIP LOIN CML CML COM 100pF CML 0.1F QLO 15 7 8 9 10 11 12 QLO IHI ILO 1000pF 1000pF LO Figure 51. Basic Connections Schematic for ADL5387 Rev. B | Page 16 of 28 06764-046 VPOS 4 VPL Data Sheet ADL5387 120nH 21 RFIN 1000pF ETC1-1-13 1000pF 22 RFIP RF INPUT 06764-048 120nH -10 -12 -14 -16 -18 -20 -22 -24 -28 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 FREQUENCY (GHz) 1.8 2.0 06764-049 -26 Figure 53. Differential RF Port Return Loss BASEBAND OUTPUTS The baseband outputs QHI, QLO, IHI, and ILO are fixed impedance ports. Each baseband pair has a 50 differential output impedance. The outputs can be presented with differential loads as low as 200 (with some degradation in linearity and gain) or high impedance differential loads (500 or greater impedance yields the same excellent linearity) that is typical of an ADC. The TCM9-1 9:1 balun converts the differential IF output to single-ended. When loaded with 50 , this balun presents a 450 load to the device. The typical maximum linear voltage swing for these outputs is 2 V p-p differential. The bias level on these pins is equal to VPOS - 2.8 V. The output 3 dB bandwidth is 240 MHz. Figure 54 shows the baseband output configuration. Figure 52. RF Input QHI 16 QHI QLO 15 QLO IHI 14 IHI ILO 13 ILO 06764-050 The RF inputs have a differential input impedance of approximately 50 . For optimum performance, the RF port should be driven differentially through a balun. The recommended balun is M/A-COM ETC1-1-13. The RF inputs to the device should be ac-coupled with 1000 pF capacitors. Ground-referenced choke inductors must also be connected to RFIP and RFIN (recommended value = 120 nH, Coilcraft 0402CS-R12XJL) for appropriate biasing. Several important aspects must be taken into account when selecting an appropriate choke inductor for this application. First, the inductor must be able to handle the approximately 40 mA of standing dc current being delivered from each of the RF input pins (RFIP, RFIN). (The suggested 0402 inductor has a 50 mA current rating). The purpose of the choke inductors is to provide a very low resistance dc path to ground and high ac impedance at the RF frequency so as not to affect the RF input impedance. A choke inductor that has a selfresonant frequency greater than the RF input frequency ensures that the choke is still looking inductive and therefore has a more predictable ac impedance (jL) at the RF frequency. Figure 52 shows the RF input configuration. The differential RF port return loss has been characterized as shown in Figure 53. S(1, 1) (dB) RF INPUT Figure 54. Baseband Output Configuration Rev. B | Page 17 of 28 ADL5387 Data Sheet ERROR VECTOR MAGNITUDE (EVM) PERFORMANCE Figure 56 shows the EVM performance of the ADL5387 when ac-coupled, with an IEEE 802.16e WiMAX signal. -10 -15 -25 -30 -35 -40 -45 -50 -50 -40 -30 -20 -10 0 10 20 INPUT POWER (dBm) Figure 56. RF = 750 MHz, IF = 0 Hz, EVM vs. Input Power for a 16 QAM 10 MHz Bandwidth Mobile WiMAX Signal (AC-Coupled Baseband Outputs) Figure 57 exhibits the zero IF EVM performance of a WCDMA signal over a wide RF input power range. 0 -5 0 -10 -5 -15 EVM (dB) -10 -15 -20 -25 -20 -30 -25 -35 -30 -40 -35 -45 -70 -40 -60 -50 -40 -30 -20 INPUT POWER (dBm) -10 0 10 06764-051 -50 -70 -60 -50 -40 -30 -20 INPUT POWER (dBm) -45 -10 0 10 06764-053 EVM (dB) -20 06764-052 The ADL5387 shows excellent EVM performance for various modulation schemes. Figure 55 shows typical EVM performance over input power range for a point-to-point application with 16 QAM modulation schemes and zero-IF baseband. The differential dc offsets on the ADL5387 are in the order of a few mV. However, ac coupling the baseband outputs with 10 F capacitors helps to eliminate dc offsets and enhances EVM performance. With a 10 MHz BW signal, 10 F ac coupling capacitors with the 500 differential load results in a high-pass corner frequency of ~64 Hz which absorbs an insignificant amount of modulated signal energy from the baseband signal. By using ac coupling capacitors at the baseband outputs, the dc offset effects, which can limit dynamic range at low input power levels, can be eliminated. 0 -5 EVM (dB) EVM is a measure used to quantify the performance of a digital radio transmitter or receiver. A signal received by a receiver would have all constellation points at the ideal locations; however, various imperfections in the implementation (such as carrier leakage, phase noise, and quadrature error) cause the actual constellation points to deviate from the ideal locations. Figure 57. RF = 1950 MHz, IF = 0 Hz, EVM vs. Input Power for a WCDMA (AC-Coupled Baseband Outputs) Figure 55. RF = 140 MHz, IF = 0 Hz, EVM vs. Input Power for a 16 QAM 10 Msym/s Signal (AC-Coupled Baseband Outputs) Rev. B | Page 18 of 28 Data Sheet ADL5387 COSLOt IF 0 IF -IF 0 +IF -90 0 +IF 0 +IF +90 LSB LO USB 0 0 +IF 06764-054 -IF SINLOt Figure 58. Illustration of the Image Problem LOW IF IMAGE REJECTION EXAMPLE BASEBAND INTERFACE The image rejection ratio is the ratio of the intermediate frequency (IF) signal level produced by the desired input frequency to that produced by the image frequency. The image rejection ratio is expressed in decibels. Appropriate image rejection is critical because the image power can be much higher than that of the desired signal, thereby plaguing the down conversion process. Figure 58 illustrates the image problem. If the upper sideband (lower sideband) is the desired band, a 90 shift to the Q channel (I channel) cancels the image at the lower sideband (upper sideband). In most direct conversion receiver designs, it is desirable to select a wanted carrier within a specified band. The desired channel can be demodulated by tuning the LO to the appropriate carrier frequency. If the desired RF band contains multiple carriers of interest, the adjacent carriers would also be down converted to a lower IF frequency. These adjacent carriers can be problematic if they are large relative to the wanted carrier as they can overdrive the baseband signal detection circuitry. As a result, it is often necessary to insert a filter to provide sufficient rejection of the adjacent carriers. Figure 59 shows the excellent image rejection capabilities of the ADL5387 for low IF applications, such as CDMA2000. The ADL5387 exhibits image rejection greater than 45 dB over the broad frequency range for an IF = 1.23 MHz. It is necessary to consider the overall source and load impedance presented by the ADL5387 and ADC input to design the filter network. The differential baseband output impedance of the ADL5387 is 50 . The ADL5387 is designed to drive a high impedance ADC input. It may be desirable to terminate the ADC input down to lower impedance by using a terminating resistor, such as 500 . The terminating resistor helps to better define the input impedance at the ADC input. The order and type of filter network depends on the desired high frequency rejection required, pass-band ripple, and group delay. Filter design tables provide outlines for various filter types and orders, illustrating the normalized inductor and capacitor values for a 1 Hz cutoff frequency and 1 load. After scaling the normalized prototype element values by the actual desired cut-off frequency and load impedance, the series reactance elements are halved to realize the final balanced filter network component values. -10 -20 -30 -40 -50 -60 -70 50 250 450 650 850 1050 1250 1450 1650 1850 RF INPUT FREQUENCY (MHz) 06764-055 IMAGE REJECTION AT 1.23MHz (dB) 0 Figure 59. Image Rejection vs. RF Input Frequency for a CDMA2000 Signal, IF = 1.23 MHz Rev. B | Page 19 of 28 ADL5387 Data Sheet The balanced configuration is realized as the 0.54 H inductor is split in half to realize the network shown in Figure 60. LN = 0.074H NORMALIZED SINGLE-ENDED CONFIGURATION VS CN 14.814F 0 -5 -10 -15 RL= 500 fC = 1Hz 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 FREQUENCY (MHz) 0.54H DENORMALIZED SINGLE-ENDED EQUIVALENT VS 5 -20 RS = 0.1 RL RS = 50 10 06764-157 RS = 50 Figure 61 and Figure 62 show the measured frequency response and group delay of the filter. MAGNITUDE RESPONSE (dB) As an example, a second-order, Butterworth, low-pass filter design is shown in Figure 60 where the differential load impedance is 500 , and the source impedance of the ADL5387 is 50 . The normalized series inductor value for the 10-to-1, load-tosource impedance ratio is 0.074 H, and the normalized shunt capacitor is 14.814 F. For a 10.9 MHz cutoff frequency, the single-ended equivalent circuit consists of a 0.54 H series inductor followed by a 433 pF shunt capacitor. Figure 61. Baseband Filter Response 433pF 900 RL= 500 800 fC = 10.9MHz 0.27H RL 2 = 250 RL = 250 2 Figure 60. Second-Order, Butterworth, Low-Pass Filter Design Example A complete design example is shown in Figure 63. A sixth-order Butterworth differential filter having a 1.9 MHz corner frequency interfaces the output of the ADL5387 to that of an ADC input. The 500 load resistor defines the input impedance of the ADC. The filter adheres to typical direct conversion WCDMA applications, where 1.92 MHz away from the carrier IF frequency, 1 dB of rejection is desired and 2.7 MHz away 10 dB of rejection is desired. Rev. B | Page 20 of 28 600 500 400 300 200 100 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 FREQUENCY (MHz) Figure 62. Baseband Filter Group Delay 1.8 06764-158 RS = 25 2 433pF DELAY (ns) BALANCED CONFIGURATION VS 700 0.27H 06764-056 RS = 25 2 Data Sheet ADL5387 ETC1-1-13 120nH 20 19 RFIP RFIN CMRF VPX 1 VPA 0.1F VPOS VPB 18 100pF 100pF CAC 10F 27H 27H 10H 27H 27H 10H 0.1F VPB 17 2 COM ADC INPUT 21 10H ADC INPUT 22 27H 500 23 27H 500 24 CMRF VPOS CMRF CAC 10F 68pF 1000pF 1000pF 91pF 120nH 270pF RFC QHI 16 3 BIAS ADL5387 VPOS QLO 15 5 VPL IHI 14 6 VPL ILO 13 CML COM 9 10 11 12 1000pF CAC 10F 1000pF 27H 27H 10H 06764-159 LO 68pF CML 8 91pF LOIN 7 CAC 10F 270pF LOIP 100pF CML 0.1F 4 VPL Figure 63. Sixth Order Low-Pass Butterworth Baseband Filter Schematic Rev. B | Page 21 of 28 ADL5387 Data Sheet CHARACTERIZATION SETUPS 10 MHz. For the case where a blocker was applied, the output blocker was at 15 MHz baseband frequency. Note that great care must be taken when measuring NF in the presence of a blocker. The RF blocker generator must be filtered to prevent its noise (which increases with increasing generator output power) from swamping the noise contribution of the ADL5387. At least 30 dB of attention at the RF and image frequencies is desired. For example, with a 2xLO of 1848 MHz applied to the ADL5387, the internal 1xLO is 924 MHz. To obtain a 15 MHz output blocker signal, the RF blocker generator is set to 939 MHz and the filters tuned such that there is at least 30 dB of attenuation from the generator at both the desired RF frequency (934 MHz) and the image RF frequency (914 MHz). Finally, the blocker must be removed from the output (by the 10 MHz low-pass filter) to prevent the blocker from swamping the analyzer. Figure 64 to Figure 66 show the general characterization bench setups used extensively for the ADL5387. The setup shown in Figure 66 was used to do the bulk of the testing and used sinusoidal signals on both the LO and RF inputs. An automated AgilentVEE program was used to control the equipment over the IEEE bus. This setup was used to measure gain, IP1dB, IIP2, IIP3, I/Q gain match, and quadrature error. The ADL5387 characterization board had a 9-to-1 impedance transformer on each of the differential baseband ports to do the differential-to-singleended conversion. The two setups shown in Figure 64 and Figure 65 were used for making NF measurements. Figure 64 shows the setup for measuring NF with no blocker signal applied while Figure 65 was used to measure NF in the presence of a blocker. For both setups, the noise was measured at a baseband frequency of SNS RF ADL5387 VPOS CHAR BOARD I LO INPUT 6dB PAD HP 6235A POWER SUPPLY R1 50 AGILENT N8974A NOISE FIGURE ANALYZER LOW-PASS FILTER IEEE GND Q FROM SNS PORT CONTROL OUTPUT AGILENT 8665B SIGNAL GENERATOR PC CONTROLLER Figure 64. General Noise Figure Measurement Setup Rev. B | Page 22 of 28 06764-057 IEEE Data Sheet ADL5387 BAND-REJECT TUNABLE FILTER BAND-PASS TUNABLE FILTER 6dB PAD R&S SMT03 SIGNAL GENERATOR RF GND ADL5387 6dB PAD VPOS CHAR BOARD LOW-PASS FILTER I LO 6dB PAD HP 6235A POWER SUPPLY R&S FSEA30 SPECTRUM ANALYZER R1 50 Q HP87405 LOW NOISE PREAMP 06764-058 BAND-PASS CAVITY FILTER AGILENT 8665B SIGNAL GENERATOR Figure 65. Measurement Setup for Noise Figure in the Presence of a Blocker 3dB PAD RF AMPLIFIER 3dB PAD IN RF OUT 3dB PAD IEEE VP GND AGILENT 11636A 3dB PAD R&S SMT-06 6dB PAD IEEE RF SWITCH MATRIX VPOS CHAR BOARD LO I 6dB PAD IEEE 6dB PAD AGILENT E3631 PWER SUPPLY RF INPUT AGILENT E8257D SIGNAL GENERATOR IEEE PC CONTROLLER IEEE R&S FSEA30 SPECTRUM ANALYZER Figure 66. General ADL5387 Characterization Setup Rev. B | Page 23 of 28 HP 8508A VECTOR VOLTMETER 06764-059 IEEE Q 6dB PAD ADL5387 IEEE RF GND INPUT CHANNELS A AND B R&S SMT-06 ADL5387 Data Sheet EVALUATION BOARD The ADL5387 evaluation board is available. The board can be used for single-ended or differential baseband analysis. The default configuration of the board is for single-ended baseband analysis. T1 RFC C10 24 23 22 21 20 19 CMRF RFIP RFIN CMRF VPX L1 CMRF VPOS R1 1 VPA C1 C11 L2 R8 R7 R6 C8 C2 2 COM VPB 17 3 BIAS QHI 16 C9 R2 R9 QLO 15 5 VPL IHI 14 6 VPL ILO 13 T2 R16 LOIP LOIN CML CML COM C4 CML 7 8 9 10 11 12 QLO R10 R11 I OUTPUT OR IHI R4 R5 T3 C13 C5 R13 C6 R17 C7 ILO R12 T4 06764-060 C3 4 VPL R15 C12 R3 Q OUTPUT OR QHI R14 ADL5387 VPOS VPOS VPB 18 LO Figure 67. Evaluation Board Schematic Rev. B | Page 24 of 28 Data Sheet ADL5387 Table 4. Evaluation Board Configuration Options Component VPOS, GND R1, R3, R6 C1, C2, C3, C4, C8, C9 C5, C6, C7, C10, C11 R4, R5, R9 to R16 L1, L2, R7, R8 T2, T3 C12, C13 R17 T1 R2 Function Power Supply and Ground Vector Pins. Power Supply Decoupling. Shorts or power supply decoupling resistors. The capacitors provide the required dc coupling up to 2 GHz. AC Coupling Capacitors. These capacitors provide the required ac coupling from 50 MHz to 2 GHz. For operation down to 30 MHz, C10 and C11 should be changed to 0.01 F. Single-Ended Baseband Output Path. This is the default configuration of the evaluation board. R14 to R16 and R4, R5, and R13 are populated for appropriate balun interface. R9, R10 and R11, R12 are not populated. Baseband outputs are taken from QHI and IHI. The user can reconfigure the board to use full differential baseband outputs. R9 to R12 provide a means to bypass the 9:1 TCM9-1 transformer to allow for differential baseband outputs. Access the differential baseband signals by populating R9 to R12 with 0 and not populating R4, R5, R13 to R16. This way the transformer does not need to be removed. The baseband outputs are taken from the SMAs of Q_HI, Q_LO, I_HI, and I_LO. Input Biasing. Inductance and resistance sets the input biasing of the common base input stage. Default value is 120 nH for operation above 50 MHz. For operation down to 30 MHz, L1 and L2 should be changed to 680 nH. IF Output Interface. TCM9-1 converts a differential high impedance IF output to a singleended output. When loaded with 50 , this balun presents a 450 load to the device. The center tap can be decoupled through a capacitor to ground. Decoupling Capacitors. C12 and C13 are the decoupling capacitors used to reject noise on the center tap of the TCM9-1. LO Input Interface. The LO is driven as a single-ended signal. Although, there is no performance change for a differential signal drive, the option is available by placing a transformer (T4, ETC1-1-13) on the LO input path. RF Input Interface. ETC1-1-13 is a 1:1 RF balun that converts the single-ended RF input to differential signal. RBIAS. Optional bias setting resistor. See the Bias Circuit section to see how to use this feature. Rev. B | Page 25 of 28 Default Condition Not Applicable R1, R3, R6 = 0 (0805) C2, C4, C8 = 100 pF (0402) C1, C3, C9 = 0.1 F (0603) C5, C6, C10, C11 = 1000 pF (0402), C7 = Open R4, R5, R13 to R16 = 0 (0402), R9 to R12 = Open L1, L2 = 120 nH (0402) R7, R8 = 0 (0402) T2, T3 = TCM9-1, 9:1 (Mini-Circuits) C12, C13 = 0.1 F (0402) R17 = 0 (0402) T1 = ETC1-1-13, 1:1 (M/A COM) R2 = Open Data Sheet 06764-166 06764-164 ADL5387 Figure 70. Evaluation Board Bottom Layer 06764-165 06764-167 Figure 68. Evaluation Board Top Layer Figure 71. Evaluation Board Bottom Layer Silkscreen Figure 69. Evaluation Board Top Layer Silkscreen Rev. B | Page 26 of 28 Data Sheet ADL5387 OUTLINE DIMENSIONS 4.10 4.00 SQ 3.90 0.60 MAX 2.50 REF 0.60 MAX 18 3.75 BSC SQ 1 0.50 BSC 2.45 2.30 SQ 2.15 EXPOSED PAD 6 13 TOP VIEW 1.00 0.85 0.80 12 MAX 0.80 MAX 0.65 TYP 0.30 0.23 0.18 SEATING PLANE 0.50 0.40 0.30 0.05 MAX 0.02 NOM COPLANARITY 0.08 0.20 REF 7 12 0.25 MIN BOTTOM VIEW FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET. 04-09-2012-A PIN 1 INDICATOR PIN 1 INDICATOR 24 19 COMPLIANT TO JEDEC STANDARDS MO-220-VGGD-2 Figure 72. 24-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 4 mm x 4 mm Body, Very Thin Quad (CP-24-2) Dimensions shown in millimeters ORDERING GUIDE Model 1 ADL5387ACPZ-R2 ADL5387ACPZ-R7 ADL5387ACPZ-WP ADL5387-EVALZ 1 Temperature Range -40C to +85C -40C to +85C -40C to +85C Package Description 24-Lead LFCSP_VQ 24-Lead LFCSP_VQ, 7" Tape and Reel 24-Lead LFCSP_VQ, Waffle Pack Evaluation Board Z = RoHS Compliant Part. Rev. B | Page 27 of 28 Package Option CP-24-2 CP-24-2 CP-24-2 Ordering Quantity 250 1,500 64 ADL5387 Data Sheet NOTES (c)2007-2013 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D06764-0-10/13(B) Rev. B | Page 28 of 28