PA241
PA241U 1
Product Innovation From
PA241
FEATURES
• RoHS COMPLIANT
• MONOLITHIC MOS TECHNOLOGY
• LOW COST
• HIGH VOLTAGE OPERATION—350V
• LOW QUIESCENT CURRENT TYP.—2.2mA
• NO SECOND BREAKDOWN
• HIGH OUTPUT CURRENT—120mA PEAK
• AVAILABLE IN DIE FORM—CPA241
APPLICATIONS
• PIEZO ELECTRIC POSITIONING
• ELECTROSTATIC TRANSDUCER & DEFLECTION
• DEFORMABLE MIRROR FOCUSING
• BIOCHEMISTRY STIMULATORS
• COMPUTER TO VACUUM TUBE INTERFACE
DESCRIPTION
The PA241 is a high voltage monolithic MOSFET operational
amplier which achieves performance features previously
found only in hybrid designs while increasing reliability. Inputs
are protected from excessive common mode and differential
mode voltages. The safe operating area (SOA) has no second
breakdown limitation and can be observed with all type loads
by choosing an appropriate current limiting resistor. External
compensation provides the user exibility in choosing optimum
gain and bandwidth for the application.
The PA241CE is packaged in a hermetically sealed 8-pin
TO-3 package. The metal case of the PA241CE is isolated in
excess of full supply voltage.
The PA241DF is packaged in a 24 pin PSOP (JEDEC MO-
166) package. The metal heat slug of the PA241DF is isolated
in excess of full supply voltage.
The PA241DW is packaged in Apex Precision Power’s her-
metic ceramic SIP package. The alumina ceramic isolates the
die in excess of full supply voltage.
EQUIVALENT SCHEMATIC
20R
PIEZO
TRANSDUCER
20R
Rn
20R
Cn
R
V
IN
–175
+175
–175
+175
R
CL
R
CL
47 47
10pF 10pF
A1
PA241
A2
PA241
LOW COST 660V p-p
PIEZO DRIVE
Two PA241 ampliers operated as a bridge driver for a piezo
transducer provides a low cost 660 volt total drive capability.
The RN CN network serves to raise the apparent gain of A2 at
high frequencies. If RN is set equal to R the ampliers can be
compensated identically and will have matching bandwidths.
EXTERNAL CONNECTIONS
RCL
1 4 5 6 732 8 9 10
CC
+IN-IN
NC NC -VS+VSILIM CC2 CC1 OUT
PA241DW
RCL
TOP VIEW
1
2
3
4
5
67
8
OUT
ILIM
–VS
+VS
CC1
–IN
+IN
CC2
CC
NOTE: PA241CE Recommended mounting torque is 4-7
in•lbs (.45 -.79 N•m)
CAUTION: The use of compressible, thermally conductive
insulators may void warranty.
PA241CE
8-PIN TO-3 24-PIN PSOP 10-PIN SIP
PACKAGE STYLE CE PACKAGE STYLE DF PACKAGE STYLE DW
ILIM
OUT
-IN
+IN
+VS
-VS
CC2
CC1
TYPICAL APPLICATION
Ref: APPLICATION NOTE 20: "Bridge Mode Operation of Power Ampliers"
CCRCL
NC
NC
NC
NC
-IN
NC
+IN
NC
NC
NC
NC
-VS
NC
NC
NC
OUT
NC
COMP
NC
COMP
NC
ILIM
NC
+VS
24
1
+
-
PA241DF
For CC values, see graph on page 4.
Note: CC must be rated for full supply
voltage.
High Voltage Power Operational Amplifier
PA241
Product Innovation From
Copyright © Cirrus Logic, Inc. 2009
(All Rights Reserved)
www.cirrus.com
DEC 2009
APEX − PA241UREVI
PA241
2 PA241U
Product Innovation From
ABSOLUTE MAXIMUM RATINGS PA241CE PA241DF
PA241CEA PA241DFA
SUPPLY VOLTAGE, +VS to –VS 350V 350V
OUTPUT CURRENT, continuous within SOA 60 mA 60 mA
OUTPUT CURRENT, peak 120 mA 120 mA
POWER DISSIPATION, continuous @ TC = 25°C 12W 12W
INPUT VOLTAGE, differential ±16 V ±16 V
INPUT VOLTAGE, common mode ±VS ±VS
TEMPERATURE, pin solder – 10 sec 300°C 220°C
TEMPERATURE, junction2 150°C 150°C
TEMPERATURE, storage –65 to +150°C –65 to +150°C
TEMPERATURE RANGE, powered (case) –40 to +125°C –40 to +125°C
CAUTION The PA241 is constructed from MOSFET transistors. ESD handling procedures must be observed.
PA241CE, PA241DF PA241CEA
PARAMETER TEST CONDITIONS1 MIN TYP MAX MIN TYP MAX UNITS
INPUT
OFFSET VOLTAGE, initial 25 40 15 30 mV
OFFSET VOLTAGE, vs. temperature3 25° to 85°C 100 250 * * µV/°C
OFFSET VOLTAGE, vs. temperature3 -25° to 25°C 270 500 * * µV/°C
OFFSET VOLTAGE, vs supply 3 * µV/V
OFFSET VOLTAGE, vs time 70 130 * * µV/kh
BIAS CURRENT, initial6 5/50 50/200
* * pA
BIAS CURRENT, vs supply 0.2/2 * pA/V
OFFSET CURRENT, initial6 2.5/50 50/200 * * pA
INPUT IMPEDANCE, DC 1011 *
INPUT CAPACITANCE 6 * pF
COMMON MODE, voltage range +VS–14 * V
COMMON MODE, voltage range -VS+12 * V
COMMON MODE REJECTION, DC VCM = ±90V DC 84 94 * * dB
NOISE, broad band 10kHz BW, RS = 1K 50 * µV RMS
NOISE, low frequency 1-10 Hz 125 * µV p-p
GAIN
OPEN LOOP at 15Hz RL = 5K 90 96 * * dB
BANDWIDTH, gain bandwidth product 3 * MHz
POWER BANDWIDTH 280V p-p 30 * kHz
OUTPUT
VOLTAGE SWING IO = 40mA ±VS–12 ±VS–10 ±VS–10 ±VS–8.5
V
CURRENT, peak4 120 * mA
CURRENT, continuous 60 * mA
SETTLING TIME to .1% 10V step, A V = –10 2 * µs
SLEW RATE CC = 3.3pF 30 * V/µs
RESISTANCE5, 1mA RCL = 0 150 * Ω
RESISTANCE5, 40 mA RCL = 0 5 * Ω
POWER SUPPLY
VOLTAGE ±50 ±150 ±175 * * * V
CURRENT, quiescent 2.2 2.5 * 2.3 mA
THERMAL
PA241CE RESIS
TANCE, AC junction to case F > 6
0Hz 5.4 6.5 * * °C/W
PA241DF RESIS
TANCE, AC junction to case F > 6
0Hz 6 7 * * °C/W
PA241CE RESIS
TANCE, DC junction to case F < 6
0Hz 9 10.4 * * °C/W
PA241DF RESIS
TANCE, DC junction to case F < 6
0Hz 9 11 * * °C/W
PA241CE RESISTANCE, junction to air Full temperature range 30 * °C/W
PA241DF RESISTANCE, junction to air7 Full temperature range 25 * °C/W
TEMPERATURE RANGE, case Meets full range spec's –25 +85 * * °C
SPECIFICATIONS
NOTES: * "A" specication is the same as the non "A" specication.
1. Unless otherwise noted TC = 25°C, CC = 6.8pF. DC input specications are ± value given. Power supply voltage is typical
rating.
2. Long term operation at the maximum junction temperature will result in reduced product life. Derate internal power dissipation
to achieve high MTTF. For guidance, refer to heatsink data sheet.
3. Sample tested by wafer to 95%.
4. Guaranteed but not tested.
5. The selected value of RCL must be added to the values given for total output resistance.
6. Specications separated by / indicate values for the PA241CE and PA241DF respectively.
7. Rating applies with solder connection of heatslug to a minimum 1 square inch foil area of the printed circuit board.
PA241
PA241U 3
Product Innovation From
CAUTION The PA241 is constructed from MOSFET transistors. ESD handling procedures must be observed.
ABSOLUTE MAXIMUM RATINGS PA241DW
PA241DWA
SUPPLY VOLTAGE, +VS to –VS 350V
OUTPUT CURRENT, continuous within SOA 60 mA
OUTPUT CURRENT, peak 120 mA
POWER DISSIPATION, continuous @ TC = 25°C 9W
INPUT VOLTAGE, differential ±16 V
INPUT VOLTAGE, common mode ±VS
TEMPERATURE, pin solder – 10 sec 220°C
TEMPERATURE, junction2 150°C
TEMPERATURE, storage –65 to +150°C
TEMPERATURE RANGE, powered (case) –40 to +125°C
PA241DW PA241DWA
PARAMETER TEST CONDITIONS1 MIN TYP MAX MIN TYP MAX UNITS
INPUT
OFFSET VOLTAGE, initial 25 40 15 30 mV
OFFSET VOLTAGE, vs. temperature3 25° to 85°C 100 250 * * µV/°C
OFFSET VOLTAGE, vs. temperature3 -25° to 25°C 270 500 * * µV/°C
OFFSET VOLTAGE, vs supply 3 * µV/V
OFFSET VOLTAGE, vs time 70 130 * µV/kh
BIAS CURRENT, initial 100 2000
* * pA
BIAS CURRENT, vs supply 15 50 * * pA/V
OFFSET CURRENT, initial 100 400 * * pA
INPUT IMPEDANCE, DC 1011 *
INPUT CAPACITANCE 6 * pF
COMMON MODE, voltage range +VS–14 * V
COMMON MODE, voltage range -VS+12 * V
COMMON MODE REJECTION, DC VCM = ±90V DC 84 94 * * dB
NOISE, broad band 10kHz BW, RS = 1K 50 * µV RMS
NOISE, low frequency 1-10 Hz 125 * µV p-p
GAIN
OPEN LOOP at 15Hz RL = 5K 90 96 * * dB
BANDWIDTH, gain bandwidth product 3 * MHz
POWER BANDWIDTH 280V p-p 30 * kHz
OUTPUT
VOLTAGE SWING IO = 40mA ±VS–12 ±VS–10 ±VS–10 ±VS–8.5
V
CURRENT, peak4 120 * mA
CURRENT, continuous 60 * mA
SETTLING TIME to .1% 10V step, A V = –10 2 * µs
SLEW RATE CC = 3.3pF 30 * V/µs
RESISTANCE5, 1mA RCL = 0 150 * Ω
RESISTANCE5, 40 mA RCL = 0 5 * Ω
POWER SUPPLY
VOLTAGE ±50 ±150 ±175 * * * V
CURRENT, quiescent 2.2 2.5 * 2.3 mA
THERMAL
PA241DW RESIS
TANCE, AC junction to case F > 6
0Hz 7 10 * * °C/W
PA241DW RESIS
TANCE, DC junction to case F < 6
0Hz 12 14 * * °C/W
PA241DW RESISTANCE, junction to air Full temperature range 55 * °C/W
TEMPERATURE RANGE, case Meets full range spec's –25 +85 * * °C
SPECIFICATIONS
NOTES: * "A" specication is the same as the non "A" specication.
1. Unless otherwise noted TC = 25°C, CC = 6.8pF. DC input specications are ± value given. Power supply voltage is typical
rating.
2. Long term operation at the maximum junction temperature will result in reduced product life. Derate internal power dissipation
to achieve high MTTF. For guidance, refer to heatsink data sheet.
3. Sample tested by wafer to 95%.
4. Guaranteed but not tested.
5. The selected value of RCL must be added to the values given for total output resistance.
PA241
4 PA241U
Product Innovation From
OUTPUT VOLTAGE SWING
0
2
4
6
8
10
12
OUTPUT CURRENT, I
O
(mA)
V
DROP
FROM V
S
, (V)
V
DROP
- @85°C
V
DROP
+ @85°C
V
DROP
- @25°C
V
DROP
+ @25°C
0 20 40 60 80 100 120
FREQUENCY, F (Hz)
POWER SUPPLY REJECTION
POWER SUPPLY REJECTION, PSR (dB)
10 100 1K 10K 100K
40
50
60
70
80
90
100
POSITIVE
NEGATIVE
100 1K
FREQUENCY, F (Hz)
0
80
120
COMMON MODE REJECTION
COMMON MODE REJECTION, CMR (dB)
20
60
100
10 10K 100K
40
QUIESCENT CURRENT
TOTAL SUPPLY VOLTAGE, (V)
NORMALIZED QUIESCENT CURRENT (%)
115
105
95
85
120
110
100
90
80
100 150 200 250 300 350
IQ (-25°C)
IQ (25°C)
IQ (85°C)
COMPENSATION CAPACITANCE, CC (pF)
SLEW RATE, (V/µs)
SLEW RATE
10 20 30 40 50 0
5
15
25
35
60 70
100 10K
FREQUENCY, F (Hz)
0.001
HARMONIC DISTORTION
DISTORTION, (%)
10
1K 100K
0.1
0.01
1 30V P-P
60V P-P
180V P-P
AV = 20
CC = 15pF
RL = 2K
FREQUENCY, F (Hz)
OUTPUT VOLTAGE, (VOUT)(p-p)
100K 1M 10K
10
100
1000
POWER RESPONSE
.75pF
6.8pF
15pF
33pF
68pF
1M 10M 100K 10K
-170
-160
-150
-140
-130
-120
-180
PHASE RESPONSE
FREQUENCY, F (Hz)
PHASE, Ф (°)
68pF
15pF
6.8pF
.75pF
-110
-100
-90
10K 1K 100 10
68pF
15pF
6.8pF
.75pF
100
80
60
40
20
0
-20
SMALL SIGNAL RESPONSE
OPEN LOOP GAIN, A (dB)
FREQUENCY, F (Hz)
10M 1M 100K
TC = 55°C
TC = 85°C
TC = 25°C
TC = 125°C
100
10
1
0.1
COMPENSATION, pF
100 10 1
GAIN
GAIN AND COMPENSATION
0.50
0.55
0.60
0.65
0.70
0.75
0.80
0.85
0.90
0.95
ILIMIT VS. TEMPERATURE
VBE (V)
-55 -35 -15 5 25 45 65 85 105 125
TEMPERATURE, (°C)
VBE+
VBE-
0 25 50 75 100 125
TEMPERATURE, T (°C)
0
3
6
POWER DERATING
INTERNAL POWER DISSIPATION, P(W)
15
9
12
PA241CE
PA241DF
T = T
A
T = T
C
T = T
A
T = T
C
PA241DW
PA241
PA241U 5
Product Innovation From
GENERAL
Please read Application Note 1 "General Operating Consid-
erations" which covers stability, power supplies, heat sinking,
mounting, current limit, SOA interpretation, and specication
interpretation. Visit www.Cirrus.com for design tools that help
automate tasks such as calculations for stability, internal power
dissipation, current limit, heat sink selection, Apex Precision
Power's complete Application Notes library, Technical Seminar
Workbook and Evaluation Kits.
PHASE COMPENSATION
Open loop gain and phase shift both increase with increas-
ing temperature. The PHASE COMPENSATION typical graph
shows closed loop gain and phase compensation capacitor
value relationships for four case temperatures. The curves are
based on achieving a phase margin of 50°. Calculate the high-
est case temperature for the application (maximum ambient
temperature and highest internal power dissipation) before
choosing the compensation. Keep in mind that when working
with small values of compensation, parasitics may play a large
role in performance of the nished circuit. The compensation
capacitor must be rated for at least the total voltage applied
to the amplier and should be a temperature stable type such
as NPO or COG.
OTHER STABILITY CONCERNS
There are two important concepts about closed loop gain
when choosing compensation. They stem from the fact that
while "gain" is the most commonly used term, β (the feedback
factor) is really what counts when designing for stability.
1. Gain must be calculated as a non-inverting circuit (equal
input and feedback resistors can provide a signal gain of
-1, but for calculating offset errors, noise, and stability, this
is a gain of 2).
2. Including a feedback capacitor changes the feedback factor
or gain of the circuit. Consider Rin=4.7k, Rf=47k for a gain
of 11. Compensation of 4.7 to 6.8pF would be reasonable.
Adding 33pF parallel to the 47k rolls off the circuit at 103kHz,
and at 2MHz has reduced gain from 11 to roughly 1.5 and
the circuit is likely to oscillate.
As a general rule the DC summing junction impedance
(parallel combination of the feedback resistor and all input
resistors) should be limited to 5k ohms or less. The amplier
input capacitance of about 6pF, plus capacitance of connecting
traces or wires and (if used) a socket will cause undesirable
circuit performance and even oscillation if these resistances
are too high. In circuits requiring high resistances, measure or
estimate the total sum point capacitance, multiply by Rin/Rf, and
parallel Rf with this value. Capacitors included for this purpose
are usually in the single digit pF range. This technique results
in equal feedback factor calculations for AC and DC cases. It
does not produce a roll off, but merely keeps β constant over
a wide frequency range. Paragraph 6 of Application Note 19
details suitable stability tests for the nished circuit.
CURRENT LIMIT
For proper operation, the current limit resistor, Rcl, must be
connected as shown in the external connection diagram. The
minimum value is 3.9 ohms, however for optimum reliability,
the resistor should be set as high as possible. The maximum
practical value is 110 ohms. Current limit values can be pre-
dicted as follows:
Ilimit = Vbe
Rcl
Where Vbe is shown in the CURRENT LIMIT typical
graph.
Note that +Vbe should be used to predict current through
the +Vs pin, -Vbe for current through the -Vs pin, and that they
vary with case temperature. Value of the current limit resistor
at a case temperature of 25° can be estimated as follows:
Rcl = 0.7
Ilimit
When the amplier is current limiting, there may be spurious
oscillation present during the current limited portion of the nega-
tive half cycle. The frequency of the oscillation is not predictable
and depends on the compensation, gain of the amplier, value
of the current limit resistor, and the load. The oscillation will
cease as the amplier comes out of current limit.
SAFE OPERATING AREA
The MOSFET output stage of the PA241 is not limited by
second breakdown considerations as in bipolar output stages.
However there are still three distinct limitations:
1. Voltage withstand capability of the transistors.
2. Current handling capability of the die metalization.
3. Temperature of the output MOSFETS.
These limitations can be seen in the SOA (see Safe Operat-
ing Area graphs). Note that each pulse capability line shows
a constant power level (unlike second breakdown limitations
where power varies with voltage stress). These lines are shown
for a case temperature of 25°C and correspond to thermal
resistances of 5.2°C/W for the PA241CE and DF and 10.4°C/W
for the PA241DW respectively. Pulse stress levels for other
case temperatures can be calculated in the same manner as
DC power levels at different temperatures. The output stage
is protected against transient yback by the parasitic diodes of
the output stage MOSFET structure. However, for protection
against sustained high energy yback external fast-recovery
diodes must be used.
HEATSINKING
The PA241DF package has a large exposed integrated
copper heatslug to which the monolithic amplier is directly
attached. The solder connection of the heatslug to a minimum
of 1 square inch foil area on the printed circuit board will result
in thermal performance of 25°C/W junction to air rating of the
PA241DF. Solder connection to an area of 1 to 2 square inches
is recommended. This may be adequate heatsinking but the
large number of variables involved suggest temperature mea-
surements be made on the top of the package. Do not allow
the temperature to exceed 85°C.
PA241
6 PA241U
Product Innovation From
SUPPLY TO OUTPUT DIFFERENTIAL, V
S
-V
O
(V)
10 20 30 50 100 200 300 500
OUTPUT CURRENT FROM +V
S
OR –V
S
, (mA)
2
3
4
5
10
20
30
40
50
100
DC, T
C
= 125°C
DC, T
C
= 85°C
DC
PULSE CURVES @ 10% DUTY CYCLE MAX
PA241CE and DF SOA
200mS
120
200
SUPPLY TO OUTPUT DIFFERENTIAL, V
S
-V
O
(V)
10 20 30 50 100 200 300 500
OUTPUT CURRENT FROM +V
S
OR –V
S
, (mA)
2
3
4
5
10
20
30
40
50
100
DC, T
C
= 125°C
DC, T
C
= 85°C
DC
PULSE CURVES @ 10% DUTY CYCLE MAX
PA241DW SOA
200mS
120
200
+Vs
-Vs
OUT
+Vs
-Vs
Z1
Z2
-IN
+IN
Q1 Q2
FIGURE 1
OVERVOLTAGE PROTECTION
Although the PA241 can withstand differential input voltages
up to 16V, in some applications additional external protection
may be needed. Differential inputs exceeding 16V will be clipped
by the protection circuitry. However, if more than a few milliamps
of current is available from the overload source, the protection
circuitry could be destroyed. For differential sources above
16V, adding series resistance limiting input current to 1mA will
prevent damage. Alternatively, 1N4148 signal diodes connected
anti-parallel across the input pins is usually sufficient. In more
demanding applications where bias current is important, diode
connected JFETs such as 2N4416 will be required. See Q1
and Q2 in Figure 1. In either case the differential input voltage
will be clamped to 0.7V. This is sufficient overdrive to produce
the maximum power bandwidth.
In the case of inverting circuits where the +IN pin is grounded,
the diodes mentioned above will also afford protection from
excessive common mode voltage. In the case of non-invert-
ing circuits, clamp diodes from each input to each supply will
provide protection. Note that these diodes will have substantial
reverse bias voltage under normal operation and diode leak-
age will produce errors.
Some applications will also need over-voltage protection
devices connected to the power supply rails. Unidirectional
zener diode transient suppressors are recommended. The
zeners clamp transients to voltages within the power supply
rating and also clamp power supply reversals to ground.
Whether the zeners are used or not the system power supply
should be evaluated for transient performance including power-
on overshoot and power-off polarity reversals as well as line
regulation. See Z1 and Z2 in Figure 1.
APPLICATION REFERENCES:
For additional technical information please refer to the fol-
lowing Application Notes:
AN1: General Operating Considerations
AN3: Bridge Circuit Drives
AN25: Driving Capacitive Loads
AN38: Loop Stability with Reactive Loads
PA241
PA241U 7
Product Innovation From
CONTACTING CIRRUS LOGIC SUPPORT
For all Apex Precision Power product questions and inquiries, call toll free 800-546-2739 in North America.
For inquiries via email, please contact apex.support@cirrus.com.
International customers can also request support by contacting their local Cirrus Logic Sales Representative.
To nd the one nearest to you, go to www.cirrus.com
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to change without notice and is provided "AS IS" without warranty of any kind (express or implied). Customers are advised to obtain the latest version of relevant
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copyrights, trademarks, trade secrets or other intellectual property rights. Cirrus owns the copyrights associated with the information contained herein and gives con-
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CUSTOMER OR CUSTOMER’S CUSTOMER USES OR PERMITS THE USE OF CIRRUS PRODUCTS IN CRITICAL APPLICATIONS, CUSTOMER AGREES,
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