400 MHz to 6 GHz
Quadrature Demodulator
Data Sheet
ADL5380
Rev. A Document Feedback
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FEATURES
Operating RF and LO frequency: 400 MHz to 6 GHz
Input IP3
30 dBm @ 900 MHz
28 dBm @1900 MHz
Input IP2: >65 dBm @ 900 MHz
Input P1dB (IP1dB): 11.6 dBm @ 900 MHz
Noise figure (NF)
10.9 dB @ 900 MHz
11.7 dB @ 1900 MHz
Voltage conversion gain: ~7 dB
Quadrature demodulation accuracy @ 900 MHz
Phase accuracy: ~0.2°
Amplitude balance: ~0.07 dB
Demodulation bandwidth: ~390 MHz
Baseband I/Q drive: 2 V p-p into 200 Ω
Single 5 V supply
APPLICATIONS
Cellular W-CDMA/GSM/ LT E
Microwave point-to-(multi)point radios
Broadband wireless and WiMAX
FUNCTIONAL BLOCK DIAGRAM
RFIN
RFIP
ENBL ADJ
QUADRATURE
PHASE SPLITTER
ADL5380
V2I
BIAS
LOIP
LOIN
IHI
ILO
QHI
QLO
07585-001
Figure 1.
GENERAL DESCRIPTION
The ADL5380 is a broadband quadrature I-Q demodulator that
covers an RF/IF input frequency range from 400 MHz to 6 GHz.
With a NF = 10.9 dB, IP1dB = 11.6 dBm, and IIP3 = 29.7 dBm @
900 MHz, the ADL5380 demodulator offers outstanding dynamic
range suitable for the demanding infrastructure direct-conversion
requirements. The differential RF inputs provide a well-behaved
broadband input impedance of 50 Ω and are best driven from a
1:1 balun for optimum performance.
Excellent demodulation accuracy is achieved with amplitude
and phase balances of ~0.07 dB and ~0.2°, respectively. The
demodulated in-phase (I) and quadrature (Q) differential outputs
are fully buffered and provide a voltage conversion gain of ~7 dB.
The buffered baseband outputs are capable of driving a 2 V p-p
differential signal into 200 Ω.
The fully balanced design minimizes effects from second-order
distortion. The leakage from the LO port to the RF port is
<−50 dBm. Differential dc offsets at the I and Q outputs are
typically <20 mV. Both of these factors contribute to the
excellent IIP2 specification, which is >65 dBm.
The ADL5380 operates off a single 4.75 V to 5.25 V supply. The
supply current is adjustable by placing an external resistor from
the ADJ pin to either the positive supply, VS, (to increase supply
current and improve IIP3) or to ground (which decreases supply
current at the expense of IIP3).
The ADL5380 is fabricated using the Analog Devices, Inc.,
advanced silicon-germanium bipolar process and is available
in a 24-lead exposed paddle LFCSP.
ADL5380 Data Sheet
Rev. A | Page 2 of 36
TABLE OF CONTENTS
Features .............................................................................................. 1
Applications ....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description ......................................................................... 1
Revision History ............................................................................... 2
Specifications ..................................................................................... 3
Absolute Maximum Ratings ............................................................ 5
ESD Caution .................................................................................. 5
Pin Configuration and Function Descriptions ............................. 6
Typical Performance Characteristics ............................................. 7
Low Band Operation .................................................................... 7
Midband Operation ................................................................... 11
High Band Operation ................................................................ 14
Distributions for fLO = 900 MHz ............................................... 17
Distributions for fLO = 1900 MHz ............................................. 18
Distributions for fLO = 2700 MHz ............................................. 19
Distributions for fLO = 3600 MHz ............................................. 20
Distributions for fLO = 5800 MHz ............................................. 21
Circuit Description ......................................................................... 22
LO Interface ................................................................................ 22
V-to-I Converter ......................................................................... 22
Mixers .......................................................................................... 22
Emitter Follower Buffers ........................................................... 22
Bias Circuit .................................................................................. 22
Applications Information .............................................................. 23
Basic Connections ...................................................................... 23
Power Supply ............................................................................... 23
Local Oscillator and RF Inputs ................................................. 24
Baseband Outputs ...................................................................... 25
Error Vector Magnitude (EVM) Performance ........................... 25
Low IF Image Rejection ............................................................. 26
Example Baseband Interface ..................................................... 27
Characterization Setups ................................................................. 31
Evaluation Board ............................................................................ 33
Thermal Grounding and Evaluation Board Layout ............... 35
Outline Dimensions ....................................................................... 36
Ordering Guide .......................................................................... 36
REVISION HISTORY
7/13—Rev. 0 to Rev. A
Changes to Table 2 ............................................................................. 5
Deleted Local Oscillator (LO) Input Section ............................... 23
Changed RF Input Section to Local Oscillator and RF Inputs
Section, Added Figure 78, Figure 79, and Figure 82,
Renumbered Sequentially ............................................................... 24
Added Figure 83 and Figure 84...................................................... 25
Changes to Evaluation Board Section and Figure 102 ............... 33
Changes to Table 5 and Figure 103 Caption ................................ 34
Deleted Figure 100, Figure 101, and Figure 102 .......................... 34
Updated Outline Dimensions ........................................................ 36
Changes to Ordering Guide ........................................................... 36
7/09—Revision 0: Initial Version
Data Sheet ADL5380
Rev. A | Page 3 of 36
SPECIFICATIONS
VS = 5 V, TA = 25°C, fLO = 900 MHz, fIF = 4.5 MHz, PLO = 0 dBm, ZO = 50 Ω, unless otherwise noted. Baseband outputs differentially
loaded with 450 Ω. Loss of the balun used to drive the RF port was de-embedded from these measurements.
Table 1.
Parameter Condition Min Typ Max Unit
OPERATING CONDITIONS
LO and RF Frequency Range 0.4 6 GHz
LO INPUT LOIP, LOIN
Input Return Loss LO driven differentially through a balun at 900 MHz −10 dB
LO Input Level −6 0 +6 dBm
I/Q BASEBAND OUTPUTS QHI, QLO, IHI, ILO
Voltage Conversion Gain 450 Ω differential load on I and Q outputs at 900 MHz 6.9 dB
200 Ω differential load on I and Q outputs at 900 MHz
dB
Demodulation Bandwidth 1 V p-p signal, 3 dB bandwidth 390 MHz
Quadrature Phase Error At 900 MHz 0.2 Degrees
I/Q Amplitude Imbalance 0.07 dB
Output DC Offset (Differential) 0 dBm LO input at 900 MHz ±10 mV
Output Common Mode Dependent on ADJ pin setting
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS) VS − 2.5 V
VADJ ~ 4.8 V (set by 200 Ω from ADJ pin to VS) VS − 2.8 V
VADJ ~ 2.4 V (ADJ pin open) VS − 1.2 V
0.1 dB Gain Flatness 37 MHz
Output Swing Differential 200 Ω load 2 V p-p
Peak Output Current Each pin 12 mA
POWER SUPPLIES VS = VCC1, VCC2, VCC3
Voltage 4.75 5.25 V
Current
1.5 kΩ from ADJ pin to V
S
; ENBL pin low
mA
1.5 kΩ from ADJ pin to VS; ENBL pin high 145 mA
ENABLE FUNCTION Pin ENBL
Off Isolation −70 dB
Turn-On Settling Time ENBL high to low 45 ns
Turn-Off Settling Time ENBL low to high 950 ns
ENBL High Level (Logic 1) 2.5 V
ENBL Low Level (Logic 0) 1.7 V
DYNAMIC PERFORMANCE at RF = 900 MHz VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
Conversion Gain 6.9 dB
Input P1dB 11.6 dBm
RF Input Return Loss
R F I P, RFIN driven differentially through a balun
dB
Second-Order Input Intercept (IIP2) −5 dBm each input tone 68 dBm
Third-Order Input Intercept (IIP3) −5 dBm each input tone 29.7 dBm
LO to RF RFIN, RFIP terminated in 50 Ω −52 dBm
RF to LO LOIN, LOIP terminated in 50 Ω −67 dBc
IQ Magnitude Imbalance 0.07 dB
IQ Phase Imbalance 0.2 Degrees
Noise Figure 10.9 dB
Noise Figure Under Blocking Conditions With a −5 dBm input interferer 5 MHz away 13.1 dB
ADL5380 Data Sheet
Rev. A | Page 4 of 36
Parameter Condition Min Typ Max Unit
DYNAMIC PERFORMANCE at RF = 1900 MHz VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
Conversion Gain 6.8 dB
Input P1dB 11.6 dBm
RF Input Return Loss R F I P, RFIN driven differentially through a balun −13 dB
Second-Order Input Intercept (IIP2) −5 dBm each input tone 61 dBm
Third-Order Input Intercept (IIP3) −5 dBm each input tone 27.8 dBm
LO to RF RFIN, RFIP terminated in 50 Ω −49 dBm
RF to LO LOIN, LOIP terminated in 50 Ω −77 dBc
IQ Magnitude Imbalance 0.07 dB
IQ Phase Imbalance
Degrees
Noise Figure 11.7 dB
Noise Figure Under Blocking Conditions With a −5 dBm input interferer 5 MHz away 14 dB
DYNAMIC PERFORMANCE at RF = 2700 MHz VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
Conversion Gain 7.4 dB
Input P1dB 11 dBm
RF Input Return Loss R F I P, RFIN driven differentially through a balun −10 dB
Second-Order Input Intercept (IIP2) −5 dBm each input tone 54 dBm
Third-Order Input Intercept (IIP3) −5 dBm each input tone 28 dBm
LO to RF
RFIN, RFIP terminated in 50 Ω
dBm
RF to LO LOIN, LOIP terminated in 50 Ω −73 dBc
IQ Magnitude Imbalance 0.07 dB
IQ Phase Imbalance 0.5 Degrees
Noise Figure 12.3 dB
DYNAMIC PERFORMANCE at RF = 3600 MHz VADJ ~ 4.8 V (set by200 Ω from ADJ pin to VS)
Conversion Gain 6.3 dB
Input P1dB 9.6 dBm
RF Input Return Loss R F I P, RFIN driven differentially through a balun −11 dB
Second-Order Input Intercept (IIP2) −5 dBm each input tone 48 dBm
Third-Order Input Intercept (IIP3) −5 dBm each input tone 21 dBm
LO to RF RFIN, RFIP terminated in 50 Ω −46 dBm
RF to LO LOIN, LOIP terminated in 50 Ω −72 dBc
IQ Magnitude Imbalance 0.14 dB
IQ Phase Imbalance
Degrees
Noise Figure 14.2 dB
Noise Figure Under Blocking Conditions With a −5 dBm input interferer 5 MHz away 16.2 dB
DYNAMIC PERFORMANCE at RF = 5800 MHz VADJ ~ 2.4 V (ADJ pin left open)
Conversion Gain 5.8 dB
Input P1dB 8.2 dBm
RF Input Return Loss R F I P, RFIN driven differentially through a balun −7.5 dB
Second-Order Input Intercept (IIP2) −5 dBm each input tone 44 dBm
Third-Order Input Intercept (IIP3) −5 dBm each input tone 20.6 dBm
LO to RF RFIN, RFIP terminated in 50 Ω −47 dBm
RF to LO LOIN, LOIP terminated in 50 Ω −62 dBc
IQ Magnitude Imbalance 0.07 dB
IQ Phase Imbalance −1.25 Degrees
Noise Figure 15.5 dB
Noise Figure Under Blocking Conditions
With a −5 dBm input interferer 5 MHz away
dB
Data Sheet ADL5380
Rev. A | Page 5 of 36
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter Rating
Supply Voltage: VCC1, VCC2, VCC3 5.5 V
LO Input Power 13 dBm (re: 50 Ω)
RF Input Power 15 dBm (re: 50 Ω)
Internal Maximum Power Dissipation 1370 mW
θJA1 53°C/W
θJC 2.5°C/W
Maximum Junction Temperature 150°C
Operating Temperature Range −40°C to +85°C
Storage Temperature Range −65°C to +125°C
1 Per JDEC standard JESD 51-2. For information on optimizing thermal
impedance, see the Thermal Grounding and Evaluation Board Layout
section.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ESD CAUTION
ADL5380 Data Sheet
Rev. A | Page 6 of 36
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
PIN 1
INDICATOR
NOTES
1. NC = NO CONNECT.
2. THE EXPOSED PAD S HOULD BE CO NNE CTED TO A
LOW IM P E DANCE THERMAL AND E LECTRI CAL
GROUND PLANE.
1
GND3 2GND1 3IHI 4ILO 5
GND1 6
VCC1
15 QLO
16 QHI
17 GND2
18 GND3
14 GND2
13 VCC2
7
ENBL 8
GND4 9
LOIP
1
1
GND4 2
1
NC
0
1
LOIN 1
2RFIN
2
2RFIP
3
2GND3
4
2VCC3
0
2GND3
9
1ADJ
ADL5380
TOP VIEW
(No t t o Scale)
07585-002
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No. Mnemonic Description
1, 2, 5, 8, 11, 14,
17, 18, 20, 23
GND1, GND2, GND3, GND4
Ground Connect.
3, 4, 15, 16 IHI, ILO, QLO, QHI I Channel and Q Channel Mixer Baseband Outputs. These outputs have a 50 Ω differential
output impedance (25 Ω per pin). Each output pair can swing 2 V p-p (differential) into a
load of 200 Ω. The output 3 dB bandwidth is ~400 MHz.
6, 13, 24 VCC1, VCC2, VCC3 Supply. Positive supply for LO, IF, biasing, and baseband sections. Decouple these pins to
the board ground using the appropriate-sized capacitors.
7 ENBL Enable Control. When pulled low, the part is fully enabled; when pulled high, the part is
partially powered down and the output is disabled.
9, 10 LOIP, LOIN Local Oscillator Input. Pins must be ac-coupled. A differential drive through a balun is
necessary to achieve optimal performance. Recommended balun is the Mini-Circuits
TC1-1-13 for lower frequencies, the Johanson Technology 3600 balun for midband
frequencies, and the Johanson Technology 5400 balun for high band frequencies.
Balun choice depends on the desired frequency range of operation.
12 NC Do not connect this pin.
19 ADJ A resistor to VS that optimizes third-order intercept. For operation <3 GHz, RADJ = 1.5 kΩ.
For operation from 3 GHz to 4 GHz, RADJ = 200 Ω. For operation >5 GHz, RADJ = open.
See the Circuit Description section for more details.
21, 22 RFIN, RFIP RF Input. A single-ended 50 Ω signal can be applied differentially to the RF inputs through
a 1:1 balun. Recommended balun is the Mini-Circuits TC1-1-13 for lower frequencies, the
Johanson Technology 3600 balun for midband frequencies, and the Johanson Technology
5400 balun for high band frequencies. Balun choice depends on the desired frequency
range of operation.
EP Exposed Paddle. Connect to a low impedance thermal and electrical ground plane.
Data Sheet ADL5380
Rev. A | Page 7 of 36
TYPICAL PERFORMANCE CHARACTERISTICS
VS = 5 V, TA = 25°C, LO drive level = 0 dBm, RF input balun loss is de-embedded, unless otherwise noted.
LOW BAND OPERATION
RF = 400 MHz to 3 GHz; Mini-Circuits TC1-1-13 balun on LO and RF inputs, 1.5 kΩ from the ADJ pin to VS.
2
6
12
16
4
10
8
14
18
400
600
800
1000
1200
1400
1600
1800
2200
2600
2000
2400
2800
3000
07585-003
LO F REQUENCY (MHz)
GAIN (dB), IP1dB (dBm)
TA = –40° C
TA = +25°C
TA = +85°C
GAIN
INP UT P1dB
Figure 3. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
400
600
800
1000
1200
1400
1600
1800
2200
2600
2000
2400
2800
3000
10
20
30
40
50
60
70
80 I CHANNE L
Q CHANNE L
07585-004
LO F REQUENCY (MHz)
IIP3, IIP2 (dBm)
T
A
= –40° C
T
A
= +25°C
T
A
= +85°C
INPUT IP2
INP UT IP3 (I AND Q CHANNELS)
Figure 4. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
–1.0
–0.8
–0.6
0
–0.2
–0.4
0.2
0.4
0.6
0.8
1.0
07585-005
GAIN MISM ATCH (dB)
TA = –40° C
TA = +25°C
TA = +85°C
400
600
800
1000
1200
1400
1600
1800
2200
2600
2000
2400
2800
3000
LO F REQUENCY (MHz)
Figure 5. IQ Gain Mismatch vs. LO Frequency
–8
–7
–6
–5
–4
–3
–2
–1
0
1
2
10 100 1000
07585-006
BASEBAND FREQUENCY ( M Hz )
BASEBAND RE S P ONSE (d B)
Figure 6. Normalized IQ Baseband Frequency Response
ADL5380 Data Sheet
Rev. A | Page 8 of 36
8
10
12
14
9
11
13
15
16
17
18
07585-007
LO F REQUENCY (MHz)
NOISE FIGURE (dB)
T
A
= –40° C
T
A
= +25°C
T
A
= +85°C
400
600
800
1000
1200
1400
1600
1800
2200
2600
2000
2400
2800
3000
Figure 7. Noise Figure vs. LO Frequency
–4
–3
–2
–1
0
1
2
3
4
400
600
800
1000
1200
1400
1600
1800
2000
2200
2400
2600
2800
3000
QUADRATURE PHASE E RROR (Degrees)
LO F REQUENCY (MHz)
T
A
= –40° C
T
A
= +25°C
T
A
= +85°C
07585-008
Figure 8. IQ Quadrature Phase Error vs. LO Frequency
25
30
35
40
45
50
55
60
65
70
75
0
2
4
6
8
10
12
14
16
18
20
–6 –5 –4 –3 –2 –1 0 1 2 3 4 5 6
IIP3, IIP2 ( dBm)
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
LO LEVEL (dBm)
IIP2, I CHANNE L
IIP2, Q CHANNE L
IP1dB
GAIN
IIP3
NOISE FIGURE
07585-009
Figure 9. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 900 MHz
160
180
200
220
240
260
280
300
0
5
10
15
20
25
30
35
1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5
SUPP LY CURRENT ( mA)
IIP3 (dBm) AND NOISE FIGURE ( dB)
V
ADJ
(V)
INPUT IP3
SUPPLY
CURRENT
NOISE FIGURE
T
A
= –40° C
T
A
= +25°C
T
A
= +85°C
07585-010
Figure 10. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 900 MHz
5
7
9
11
13
15
17
19
21
23
25
–30–25–20–15–10 –5 0 5
NOISE FIGURE (dB)
RF BLOCKER INPUT POWER (dBm)
920MHz
1920MHz
07585-011
Figure 11. Noise Figure vs. Input Blocker Level, fLO = 900 MHz, fLO = 1900 MHz
(RF Blocker 5 MHz Offset)
20
25
30
35
40
45
50
55
60
2
4
6
8
10
12
14
16
18
–6 –5 –4 –3 –2 –1 0 1 2 3 4 5 6
IIP3, IIP2 (dBm)
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
LO LEVEL (dBm)
GAIN
IIP3
IP1dB
NOISE FIGURE
IIP2, Q CHANNE L
IIP2, I CHANNE L
07585-012
Figure 12. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 2700 MHz
Data Sheet ADL5380
Rev. A | Page 9 of 36
0
5
10
15
20
25
30
35
1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5
IIP3 (dBm) AND NOISE FIGURE (dB)
V
ADJ
(V)
NOISE FIGURE
INPUT IP3
07585-013
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
Figure 13. IIP3 and Noise Figure vs. VADJ, fLO = 2700 MHz
0
10
20
30
40
50
60
70
80
1234
G
A
IN (dB), IP1dB (dBm), IIP2
I AND Q CHANNELS (dBm)
900MHz: GAIN
900MHz: IP1dB
900MHz: IIP2, I CHANNEL
900MHz: IIP2, Q CHANNEL
2700MHz: GAIN
2700MHz: IP1dB
2700MHz: IIP2, I CHANNEL
2700MHz: IIP2, Q CHANNEL
V
ADJ
(V)
07585-014
Figure 14. Conversion Gain, IP1dB, and IIP2 vs.
VADJ, fLO = 900 MHz, fLO = 2700 MHz
50
55
60
65
70
75
80
85
90
0
5
10
15
20
25
30
35
40
4.5 6.5 8.5 10.5 12.5 14.5 16.5 18.5
IIP2, I AND Q CHANNELS (dBm)
IP1dB, IIP3 (dBm)
BASEBAND FREQUENCY (MHz)
I CHANNEL
Q CHANNEL
IIP3
IIP2
IP1dB
TA = –40°C
TA = +25°C
TA = +85°C
07585-015
Figure 15. IP1dB, IIP3, and IIP2 vs. Baseband Frequency
–25
–20
–15
–10
–5
0
0.40.60.81.01.21.41.61.82.02.22.42.62.83.0
RETURN LOSS (dB)
RF FREQUENCY (GHz)
07585-016
Figure 16. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through TC1-1-13 Balun
–100
–90
–80
–70
–60
–50
–40
–30
–
20
LEAKAGE (
d
B
m
)
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
LO FREQUENCY (GHz)
07585-017
Figure 17. LO-to-RF Leakage vs. LO Frequency
–100
–90
–80
–70
–60
–50
–40
–30
–
20
LEAKAGE (dBc)
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
RF FREQUENCY (GHz)
07585-018
Figure 18. RF-to-LO Leakage vs. RF Frequency
ADL5380 Data Sheet
Rev. A | Page 10 of 36
–16
–14
–12
–10
–8
–6
–4
–2
0
RET URN LOSS ( dB)
0.4 0.6 0.8
1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
LO FREQ UE NCY ( GHz)
07585-019
Figure 19. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through TC1-1-13 Balun
Data Sheet ADL5380
Rev. A | Page 11 of 36
MIDBAND OPERATION
RF = 3 GHz to 4 GHz; Johanson Technology 3600BL14M050T balun on LO and RF inputs, 200 Ω from VADJ to VS.
4
5
6
7
8
9
10
11
12
13
14
3.03.13.23.33.43.53.63.73.83.94.0
GAIN (dB), IP1dB (dBm)
LO FREQUENCY (GHz)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
IP1dB
GAIN
07585-020
Figure 20. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
10
20
30
40
50
60
70
80
3.0 3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8 4.03.9
IIP3, IIP2 (dBm)
LO FREQUENCY (GHz)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
INPUT IP3 I AND Q CHANNELS
INPUT IP2 I CHANNEL
Q CHANNEL
07585-021
Figure 21. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
–1.0
–0.8
–0.6
–0.4
–0.2
0
0.2
0.4
0.6
0.8
1.0
3.0 3.2 3.4 3.6 3.8 4.0
GAIN MISMATCH (dB)
LO FREQUENCY (GHz)
0
7585-022
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
Figure 22. IQ Gain Mismatch vs. LO Frequency
10
15
20
25
30
35
40
45
50
55
60
0
2
4
6
8
10
12
14
16
18
20
–6–5–4–3–2–10123456
IIP3, IIP2 (dBm)
LO LEVEL (dBm)
IIP2, I CHANNEL
IIP2, Q CHANNEL
IP1dB
IIP3
GAIN
NOISE FIGURE
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
07585-023
Figure 23. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 3600 MHz
8
9
10
11
12
13
14
15
16
17
18
3.0 3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8 3.9 4.0
NOISE FIGURE (
d
B)
LO FREQUENCY (GHz)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-024
Figure 24. Noise Figure vs. LO Frequency
–4
–3
–2
–1
0
1
2
3
4
3.0 3.2 3.4 3.6 3.8 3.93.1 3.3 3.5 3.7 4.0
QUADRATURE PHASE ER
R
OR (Degrees)
LO FREQUENCY (GHz)
07585-025
TA = –40°C
TA = +25°C
TA = +85°C
Figure 25. IQ Quadrature Phase Error vs. LO Frequency
ADL5380 Data Sheet
Rev. A | Page 12 of 36
180
200
220
240
260
280
300
1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5
CURRENT ( mA)
IIP3 (dBm) AND NOISE FIGURE ( dB)
V
ADJ
(V)
SUPP LY CURRENT
NOISE FIGURE
INPUT IP3
0
5
10
15
20
25
30
T
A
= –40° C
T
A
= +25°C
T
A
= +85°C
07585-026
Figure 26. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 3600 MHz
11
13
15
17
19
21
23
25
–30 –25 –20 –15 –10 –5 05
NOISE FIGURE (dB)
RF POWEL LEVEL (dBm)
07585-027
Figure 27. Noise Figure vs. Input Blocker Level, fLO = 3600 MHz
(RF Blocker 5 MHz Offset)
–10
0
10
20
30
40
50
60
70
80
1 2 3 4
GAIN (dB), IP1dB (dBm), IIP2
I AND Q CHANNELS (dBm)
VADJ(V)
3600MHz: GAIN
3600MHz: IP1dB
3600MHz: IIP2, I CHANNEL
3600MHz: IIP2, Q CHANNEL
07585-028
Figure 28. Conversion Gain, IP1dB, and IIP2 vs. VADJ, fLO = 3600 MHz
–80
–70
–60
–50
–40
–30
–20
3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8 3.9 4.0
LE AKAGE (dBm)
LO FREQ UE NCY ( GHz)
07585-029
Figure 29. LO-to-RF Leakage vs. LO Frequency
–100
–90
–80
–70
–60
–50
–40
–30
–20
3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8 3.9 4.0
LE AKAGE (dBc)
RF FREQUENCY ( GHz)
07585-030
Figure 30. RF-to-LO Leakage vs. RF Frequency
–12
–10
–8
–6
–4
–2
0
3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8 3.9 4.0
RET URN LOSS ( dB)
RF FREQUENCY ( GHz)
07585-031
Figure 31. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through Johanson Technology 3600 Balun
Data Sheet ADL5380
Rev. A | Page 13 of 36
–30
–25
–20
–15
–10
–5
0
3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8 3.9 4.0
RET URN LOSS ( dB)
LO FREQ UE NCY ( GHz)
07585-032
Figure 32. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through Johanson Technology 3600 Balun
ADL5380 Data Sheet
Rev. A | Page 14 of 36
HIGH BAND OPERATION
RF = 5 GHz to 6 GHz; Johanson Technology 5400BL15B050E balun on LO and RF inputs, the ADJ pin is open.
2
3
4
5
6
7
8
9
10
11
12
5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
GAIN (dB), INPUT P1dB (dBm)
LO FREQUENCY (GHz)
GAIN
INPUT P1dB
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
0
7585-033
Figure 33. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
10
20
30
40
50
60
70
80
5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
IIP3, IIP2 (dBm)
LO FREQUENCY (GHz)
INPUT IP2
INPUT IP3 (I AND Q CHANNELS)
I CHANNEL
Q CHANNEL
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-034
Figure 34. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
–1.0
–0.8
–0.6
–0.4
–0.2
0
0.2
0.4
0.6
0.8
1.0
5.15.25.35.45.55.65.75.85.96.0
IQ AMPLITUDE MISMATCH (dB)
LO FREQUENCY (GHz)
07585-035
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
Figure 35. IQ Gain Mismatch vs. LO Frequency
10
15
20
25
30
35
40
45
50
55
60
0
2
4
6
8
10
12
14
16
18
20
–6 –5 –4 –3 –2 –1 0 1 2 3 4 5 6
IIP3, IIP2 (dBm)
LO LEVEL (dBm)
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
IIP2, Q CHANNEL
IIP2, I CHANNEL
IP1dB
GAIN
IIP3
NOISE FIGURE
07585-036
Figure 36. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 5800 MHz
8
9
10
11
12
13
14
15
16
17
18
19
20
5.0 5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
NOISE FIGURE (dB)
LO FREQUENCY (GHz)
T
A
= –40°C
T
A
= –25°C
T
A
= +85°C
07585-037
Figure 37. Noise Figure vs. LO Frequency
–4
–3
–2
–1
0
1
2
3
4
IQ PHASE MISM
A
TCH (Degrees)
LO FREQUENCY (GHz)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
07585-038
Figure 38. IQ Quadrature Phase Error vs. LO Frequency
Data Sheet ADL5380
Rev. A | Page 15 of 36
180
200
220
240
260
280
300
1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5
CURRENT ( mA)
IIP3 (dBm) AND NOISE FIGURE ( dB)
V
ADJ
(V)
NOISE FIGURE
0
5
10
15
20
25
30
T
A
= –40° C
T
A
= +25°C
T
A
= +85°C
INPUT IP3
SUPP LY CURRENT
07585-039
Figure 39. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 5800 MHz
0
5
10
15
20
25
–30 –25 –20 –15 –10 –5
NOISE FIGURE (dB)
RF POWER LEVEL (d Bm)
07585-040
Figure 40. Noise Figure vs. Input Blocker Level, fLO = 5800 MHz
(RF Blocker 5 MHz Offset)
0
10
20
30
40
50
60
1 2 3 4
GAIN (dB), IP1dB (dBm), IIP2
I AND Q CHANNEL (dBm)
VADJ (V)
5800MHz: GAIN
5800MHz: IP1dB
5800MHz: IIP2, I CHANNEL
5800MHz: IIP2, Q CHANNEL
07585-041
Figure 41. Conversion Gain, IP1dB, and IIP2 vs.
RBIAS, fLO = 5800 MHz
–100
–90
–80
–70
–60
–50
–40
–30
–20
5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
LEAKAGE (dBm)
LO FREQUENCY (GHz)
07585-042
Figure 42. LO-to-RF Leakage vs. LO Frequency
–20
–30
–40
–50
–60
–70
LE AKAGE (dBc)
–80
–90
–100 5.7
5.65.55.45.35.2
5.1 5.8 5.9 6.0
RF FREQUENCY ( M Hz )
07585-043
Figure 43. RF-to-LO Leakage vs. RF Frequency
RF FREQUENC Y (GHz)
–16
–14
–12
–10
–8
–6
–4
–2
0
RETURN LOSS (dB)
5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
07585-044
Figure 44. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through Johanson Technology 5400 Balun
ADL5380 Data Sheet
Rev. A | Page 16 of 36
–16
–14
–12
–10
–8
–6
–4
–2
–0
5.1 5.2 5.3 5.4 5.5 5.6 5.7 5.8 5.9 6.0
RET URN LOSS ( dB)
LO FREQ UE NCY ( GHz)
07585-045
Figure 45. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through Johanson Technology 5400 Balun
Data Sheet ADL5380
Rev. A | Page 17 of 36
DISTRIBUTIONS FOR fLO = 900 MHz
0
10
20
30
40
50
60
70
80
90
100
28 29 30 31 32 33 34
DISTRIBUTION PERCENTAGE (%)
INPUT IP3 (dBm)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-046
Figure 46. IIP3 Distributions
0
10
20
30
40
50
60
70
80
90
100
4567891011121314
DISTRIBUTION PERCENTAGE (
%
)
GAIN (dB), IP1dB (dBm)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
IP1dB
GAIN
07585-047
Figure 47. Gain and IP1dB Distributions
0
10
20
30
40
50
60
70
80
90
100
–0.3 –0.2 –0.1 0 0.1 0.2 0.3
DISTRIBUTION PERCENTAGE (%)
GAIN MISMATCH (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-048
Figure 48. IQ Gain Mismatch Distributions
0
10
20
30
40
50
60
70
80
90
100
45 50 55 60 65 70 75 80 85
DISTRIBUTION PERCENTAGE (
%
)
INPUT IP2 (dBm)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
I CHANNEL
Q CHANNEL
07585-049
Figure 49. IIP2 Distributions for I Channel and Q Channel
0
10
20
30
40
50
60
70
80
90
100
9.5 10.0 10.5 11.0 11.5 12.0 12.5
DISTRIBUTION PERCENTAGE (%)
NOISE FIGURE (dB)
TA = –40°C
TA = +25°C
TA = +85°C
07585-050
Figure 50. Noise Figure Distributions
0
10
20
30
40
50
60
70
80
90
100
–1.0 –0.8 –0.6 –0.4 –0.2 0 0.2 0.4 0.6 0.8 1.0
DISTRIBUTION PERCENTAGE (
%
)
QUADRATURE PHASE ERROR (Degrees)
TA = –40°C
TA = +25°C
TA = +85°C
07585-051
Figure 51. IQ Quadrature Phase Error Distributions
ADL5380 Data Sheet
Rev. A | Page 18 of 36
DISTRIBUTIONS FOR fLO = 1900 MHz
0
10
20
30
40
50
60
70
80
90
100
24 25 26 27 28 29 30 31 32
DISTRIBUTION PERCENTAGE (
%
)
INPUT IP3 (dBm)
TA = –40°C
TA = +25°C
TA = +85°C
07585-052
Figure 52. IIP3 Distributions
0
10
20
30
40
50
60
70
80
90
100
4567891011121314
DISTRIBUTION PERCENTAGE (
%
)
GAIN (dB), IP1dB (dBm)
TA = –40°C
TA = +25°C
TA = +85°C
IP1dB
GAIN
07585-053
Figure 53. Gain and IP1dB Distributions
0
10
20
30
40
50
60
70
80
90
100
–0.3 –0.2 –0.1 0 0.1 0.2 0.3
DISTRIBUTION PERCENTAGE (
%
)
GAIN MISMATCH (dB)
TA = –40°C
TA = +25°C
TA = +85°C
07585-054
Figure 54. IQ Gain Mismatch Distributions
0
10
20
30
40
50
60
70
80
90
100
45 50 55 60 65 70 75 80
DISTRIBUTION PERCENTAGE (%)
INPUT IP2 (dBm)
TA = –40°C
TA = +25°C
TA = +85°C
I CHANNEL
Q CHANNEL
07585-055
Figure 55. IIP2 Distributions for I Channel and Q Channel
0
10
20
30
40
50
60
70
80
90
100
10.5 11.0 11.5 12.0 12.5 13.0 13.5
DISTRIBUTION PERCENTAGE (%)
NOISE FIGURE (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-056
Figure 56. Noise Figure Distributions
0
10
20
30
40
50
60
70
80
90
100
–1.0 –0.8 –0.6 –0.4 –0.2 0 0.2 0.4 0.6 0.8 1.0
DISTRIBUTION PERCENTAGE (%)
QUADRATURE PHASE ERROR (Degrees)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
0
7585-057
Figure 57. IQ Quadrature Phase Error Distributions
Data Sheet ADL5380
Rev. A | Page 19 of 36
DISTRIBUTIONS FOR fLO = 2700 MHz
0
10
20
30
40
50
60
70
80
90
100
18 20 22 24 26 28 30 32 34 36
DISTRIBUTION PERCENTAGE (%)
INPUT IP3 (dBm)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
0
7585-058
Figure 58. IIP3 Distributions
0
10
20
30
40
50
60
70
80
90
100
4567891011121314
DISTRIBUTION PERCENTAGE (%)
GAIN (dB), IP1dB (dBm)
IP1dB
GAIN
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-059
Figure 59. Gain and IP1dB Distributions
0
10
20
30
40
50
60
70
80
90
100
–0.3 –0.2 –0.1 0 0.1 0.2 0.3
DISTRIBUTION PERCENTAGE (%)
GAIN MISMATCH (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-060
Figure 60. IQ Gain Mismatch Distributions
0
10
20
30
40
50
60
70
80
90
100
35 40 45 50 55 60 65 70 75
DISTRIBUTION PERCENTAGE (%)
INPUT IP2 (dBm)
I CHANNEL
Q CHANNEL
TA = –40°C
TA = +25°C
TA = +85°C
07585-061
Figure 61. IIP2 Distributions for I Channel and Q Channel
0
10
20
30
40
50
60
70
80
90
100
10.5 11.0 11.5 12.0 12.5 13.0 13.5 14.0
DISTRIBUTION PERCENTAGE (%)
NOISE FIGURE (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-062
Figure 62. Noise Figure Distributions
0
10
20
30
40
50
60
70
80
90
100
–2.0 –1.5 –1.0 –0.5 0 0.5 1.0 1.5 2.0
DISTRIBUTION PERCENTAGE (%)
QUADRATURE PHASE ERROR (Degrees)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-063
Figure 63. IQ Quadrature Phase Error Distributions
ADL5380 Data Sheet
Rev. A | Page 20 of 36
DISTRIBUTIONS FOR fLO = 3600 MHz
INPUT IP3 (dBm)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
0
10
20
30
40
50
60
70
80
90
100
DISTRIBUTION PERCENTAGE (%)
15 17 19 21 23 25 27 29 31 33
07585-064
Figure 64. IIP3 Distributions
0
10
20
30
40
50
60
70
80
90
100
4567891011121314
DISTRIBUTION PERCENTAGE (
%
)
GAIN (dB), IP1dB (dBm)
IP1dB
GAIN
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-065
Figure 65. Gain and IP1dB Distributions
0
10
20
30
40
50
60
70
80
90
100
–0.3 –0.2 –0.1 0 0.1 0.2 0.3
DISTRIBUTION PERCENTAGE (
%
)
GAIN MISMATCH (dB)
TA = –40°C
TA = +25°C
TA = +85°C
07585-066
Figure 66. IQ Gain Mismatch Distributions
0
10
20
30
40
50
60
70
80
90
100
35 40 45 50 55 60 65 70
DISTRIBUTION PERCENTAGE (
%
)
INPUT IP2 (dBm)
I CHANNEL
Q CHANNEL
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-067
Figure 67. IIP2 Distributions for I Channel and Q Channel
0
10
20
30
40
50
60
70
80
90
100
12.5 13.0 13.5 14.0 14.5 15.0 15.5 16.0
DISTRIBUTION PERCENTAGE (%)
NOISE FIGURE (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-068
Figure 68. Noise Figure Distributions
0
10
20
30
40
50
60
70
80
90
100
–0.5 0 0.5 1.0 1.5 2.0 2.5
DISTRIBUTION PERCENTAGE (
%
)
QUADRATURE PHASE ERROR (Degrees)
TA = –40°C
TA = +25°C
TA = +85°C
0
7585-069
Figure 69. IQ Quadrature Phase Error Distributions
Data Sheet ADL5380
Rev. A | Page 21 of 36
DISTRIBUTIONS FOR fLO = 5800 MHz
0
10
20
30
40
50
60
70
80
90
100
18 19 20 21 22 23 24
DISTRIBUTION PERCENTAGE (%)
INPUT IP3 (dBm)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-070
Figure 70. IIP3 Distributions
0
10
20
30
40
50
60
70
80
90
100
2345678910
GAIN (dB), IP1dB (dBm)
DISTRIBUTION PERCENTAGE (%)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
IP1dB
GAIN
07585-071
Figure 71. Gain and IP1dB Distributions
0
10
20
30
40
50
60
70
80
90
100
–0.3 –0.2 –0.1 0 0.1 0.2 0.3
DISTRIBUTION PERCENTAGE (
%
)
GAIN MISMATCH (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-072
Figure 72. IQ Gain Mismatch Distributions
0
10
20
30
40
50
60
70
80
90
100
30 35 40 45 50 55 60 65 70
DISTRIBUTION PERCENTAGE (%)
INPUT IP2 (dBm)
I CHANNEL
Q CHANNEL
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-073
Figure 73. IIP2 Distributions for I Channel and Q Channel
0
10
20
30
40
50
60
70
80
90
100
13.0 13.5 14.0 14.5 15.0 15.5 16.0 16.5 17.0 17.5 18.0
DISTRIBUTION PERCENTAGE (
%
)
NOISE FIGURE (dB)
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-074
Figure 74. Noise Figure Distributions
0
10
20
30
40
50
60
70
80
90
100
DISTRIBUTION PERCENTAGE (%)
QUADRATURE PHASE ERROR (Degrees)
–3 –2 –1 0 1 2 3
T
A
= –40°C
T
A
= +25°C
T
A
= +85°C
07585-075
Figure 75. IQ Quadrature Phase Error Distributions
ADL5380 Data Sheet
Rev. A | Page 22 of 36
CIRCUIT DESCRIPTION
The ADL5380 can be divided into five sections: the local
oscillator (LO) interface, the RF voltage-to-current (V-to-I)
converter, the mixers, the differential emitter follower outputs,
and the bias circuit. A detailed block diagram of the device is
shown in Figure 76.
RFIN
RFIP
ENBL ADJ
QUADRATURE
PHASE SPLITTER
ADL5380
V2I
BIAS
LOIP
LOIN
IHI
ILO
QHI
QLO
07585-076
Figure 76. Block Diagram
The LO interface generates two LO signals at 90° of phase
difference to drive two mixers in quadrature. RF signals are
converted into currents by the V-to-I converters that feed into
the two mixers. The differential I and Q outputs of the mixers
are buffered via emitter followers. Reference currents to each
section are generated by the bias circuit. A detailed description
of each section follows.
LO INTERFACE
The LO interface consists of a polyphase quadrature splitter
followed by a limiting amplifier. The LO input impedance is set
by the polyphase, which splits the LO signal into two differential
signals in quadrature. The LO input impedance is nominally
50 Ω. Each quadrature LO signal then passes through a limiting
amplifier that provides the mixer with a limited drive signal. For
optimal performance, the LO inputs must be driven differentially.
V-TO-I CONVERTER
The differential RF input signal is applied to a V-to-I converter
that converts the differential input voltage to output currents.
The V-to-I converter provides a differential 50 Ω input impedance.
The V-to-I bias current can be adjusted up or down using the
ADJ pin (Pin 19). Adjusting the current up improves IIP3 and
IP1dB but degrades SSB NF. Adjusting the current down improves
SSB NF but degrades IIP3 and IP1dB. The current adjustment
can be made by connecting a resistor from the ADJ pin (Pin 19)
to VS to increase the bias current or to ground to decrease the
bias current. Table 4 approximately dictates the relationship
between the resistor used (RADJ), the resulting ADJ pin voltage,
and the resulting baseband common-mode output voltage.
Table 4. ADJ Pin Resistor Values and Approximate ADJ Pin
Voltages
RADJ ~VADJ (V)
~ Baseband Common-
Mode Output (V)
200 Ω to VS 4.8 2.2
600 Ω to VS 4.5 2.3
1.54 kΩ to VS 4 2.5
3.8 kΩ to VS 3.5 2.7
10 kΩ to VS 3 3
Open 2.5 3.2
9 kΩ to GND 2 3.4
3.5 kΩ to GND 1.5 3.6
1.5 kΩ to GND 1 3.8
MIXERS
The ADL5380 has two double-balanced mixers: one for the in-
phase channel (I channel) and one for the quadrature channel
(Q channel). These mixers are based on the Gilbert cell design
of four cross-connected transistors. The output currents from
the two mixers are summed together in the resistive loads that
then feed into the subsequent emitter follower buffers.
EMITTER FOLLOWER BUFFERS
The output emitter followers drive the differential I and Q signals
off chip. The output impedance is set by on-chip 25 Ω series
resistors that yield a 50 Ω differential output impedance for
each baseband port. The fixed output impedance forms a
voltage divider with the load impedance that reduces the effective
gain. For example, a 500 Ω differential load has 1 dB lower
effective gain than a high (10 kΩ) differential load impedance.
BIAS CIRCUIT
A band gap reference circuit generates the reference currents
used by different sections. The bias circuit can be enabled and
partially disabled using ENBL (Pin 7). If ENBL is grounded or
left open, the part is fully enabled. Pulling ENBL high shuts off
certain sections of the bias circuitry, reducing the standing
power to about half of its fully enabled consumption and
disabling the outputs.
Data Sheet ADL5380
Rev. A | Page 23 of 36
APPLICATIONS INFORMATION
BASIC CONNECTIONS
Figure 77 shows the basic connections schematic for the ADL5380.
POWER SUPPLY
The nominal voltage supply for the ADL5380 is 5 V and is
applied to the VCC1, VCC2, and VCC3 pins. Connect ground
to the GND1, GND2, GND3, and GND4 pins. Solder the exposed
paddle on the underside of the package to a low thermal and
electrical impedance ground plane. If the ground plane spans
multiple layers on the circuit board, these layers should be stitched
together with nine vias under the exposed paddle. The AN-772
Application Note discusses the thermal and electrical grounding
of the LFCSP in detail. Decouple each of the supply pins using
two capacitors; recommended capacitor values are 100 pF and 0.1 µF.
LO_SE
1
ADL5380
VCC3
GND3
RFIP
RFIN
GND3
ADJ
ENBL
GND4
LOIP
LOIN
GND4
NC
24 23 22 21 20 19
7 8 9 10 11 12
2
3
4
5
6
GND3
GND1
IHI
ILO
GND1
VCC1
18
17
16
15
14
13
GND3
GND2
QHI
QLO
GND2
VCC2
0.1µF 100pF
VS
ILO
IHI
QHI
QLO
RFIN
VS
VS
VS
0.1µF 100pF
100pF 100pF
100pF 0.1µF
BALUN
BALUN
100pF 100pF
RADJ
07585-078
Figure 77. Basic Connections Schematic
ADL5380 Data Sheet
Rev. A | Page 24 of 36
LOCAL OSCILLATOR AND RF INPUTS
The RF and LO inputs have a differential input impedance of
approximately 50 Ω as shown in Figure 78. Figure 79 shows the
return loss. For optimum performance, both the LO and RF ports
should be ac coupled and driven differentially through a balun as
shown in Figure 80 and Figure 81. The user has many different
types of balun to choose from and from a variety of manufacturers.
For the data presented in this datasheet all measurements were
gathered with the baluns listed below. For applications that are
band specific, the recommended baluns are:
• Up to 3 GHz is the Mini-Circuits TC1-1-13.
• From 3 GHz to 4 GHz is the Johanson Technology
3600BL14M050.
• From 4.9 GHz to 6 GHz is the Johanson Technology
5400BL15B050.
For wideband applications covering the entire 400 MHz to 6 GHz
range of the ADL5380, the recommended balun is the TCM1-
63AX+ from Mini-Circuits. This wide and maximally flat balun
allows coverage of the entire frequency range with one component.
The recommended drive level for the LO port is between −6 dBm
and +6 dBm.
120
100
80
60
40
20
0
2.0
–2.0
–1.5
–1.0
–0.5
0
0.5
1.0
1.5
400 1400 2400 3400 4400 5400 6400
07585-178
PARAL LEL RIN (Ω)
PARAL LEL CAPACITANCE ( pF)
RF FREQUENCY ( M Hz )
RESISTANCE
CAPACITANCE
Figure 78. Differential Input Impedance of the RF Port
00.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
–28
–26
–24
–22
–20
–18
–16
–14
–12
–10
–30
–8
RF FREQUENCY ( GHz)
DIFFERENTIAL RETURN LOSS RF PORT (dB)
07585-080
Figure 79. Differential RF Port Return Loss
LO INPUT
BALUN
LOIP
LOIN
100pF
9
100pF
10
07585-077
Figure 80. Differential LO Drive
RF I NP UT
RFIN
BALUN
RFIP
100pF
100pF
21
22
07585-079
Figure 81. RF Input
Alternatively, if the single-ended drive of both the LO and RF ports
is the desired mode of operation, degradations in IIP2 will be
observed because of the lack of common mode rejection. The
degradation in IIP2 is more prevalent at high frequencies, specifically
frequencies greater than 1600 MHz. At low frequencies, the
ADL5380 has inherent common mode rejection offering superior
IIP2 performance in the 70 dBm range. As shown in Figure 82
and Figure 83, in single-ended mode, the largest performance
impact is seen in IIP2 while minimal performance degradation
is observed in IIP3.
100
90
80
70
60
50
40
30
20
10
0
400 54004400340024001400
07585-179
IIP2 (dBm)
FREQUENCY (MHz)
RF AND LO PORTS DIFFERENITAL DRIVE:
TCM1-63AX+
RF AND LO PO RTS SI NGLE-E NDE D DRIVE
Figure 82. IIP2 vs. Frequency Comparison for Single-Ended and Differential
Drive of the RF and LO Ports
Data Sheet ADL5380
Rev. A | Page 25 of 36
40
35
30
25
20
15
10
5
0
400 54004400340024001400
07585-180
IIP3 (dBm)
FREQUENCY (MHz)
RF AND LO PORTS DIFFERENITAL
DRIVE: TCM1-63AX+
RF AND LO PORTS SINGLE-ENDED DRIVE
Figure 83. IIP3 vs. Frequency Comparison for Single-Ended and Differential
Drive of the RF and LO Ports
To configure the ADL5380 for single-ended drive, terminate the
unused input with a 100 pF capacitor to GND while driving the
alternative input. The single-ended input impedance is 25  or
half the differential impedance. As a result of this, ensure that
there is proper impedance matching when interfacing with the
ADL5380 in single-ended mode for maximum transfer of
power. Figure 84, shows an example single ended configuration
when using a signal source with a 50  source impedance.
RFIP
RFIN
0°
90°
IHI
ILO
LOIP
LOIN
QHI
QLO
100pF 100pF
25Ω25Ω
07585-181
Figure 84. Single-Ended Configuration
BASEBAND OUTPUTS
The baseband outputs QHI, QLO, IHI, and ILO are fixed
impedance ports. Each baseband pair has a 50 Ω differential
output impedance. The outputs can be presented with differential
loads as low as 200 Ω (with some degradation in gain) or high
impedance differential loads (500 Ω or greater impedance yields
the same excellent linearity) that is typical of an ADC. The TCM9-1
9:1 balun converts the differential IF output to a single-ended
output. When loaded with 50 Ω, this balun presents a 450 Ω
load to the device. The typical maximum linear voltage swing for
these outputs is 2 V p-p differential. The output 3 dB bandwidth
is 390 MHz. Figure 85 shows the baseband output configuration.
07585-081
16
15
3
4
IHI
ILO
QHI
QLO
ADL5380
Figure 85. Baseband Output Configuration
ERROR VECTOR MAGNITUDE (EVM) PERFORMANCE
EVM is a measure used to quantify the performance of a digital
radio transmitter or receiver. A signal received by a receiver has all
constellation points at their ideal locations; however, various
imperfections in the implementation (such as magnitude
imbalance, noise floor, and phase imbalance) cause the actual
constellation points to deviate from their ideal locations.
In general, a demodulator exhibits three distinct EVM
limitations vs. received input signal power. At strong signal
levels, the distortion components falling in-band due to non-
linearities in the device cause strong degradation to EVM
as signal levels increase. At medium signal levels, where the
demodulator behaves in a linear manner and the signal is well
above any notable noise contributions, the EVM has a tendency to
reach an optimum level determined dominantly by the quadrature
accuracy of the demodulator and the precision of the test equipment.
As signal levels decrease, such that noise is a major contribution,
the EVM performance vs. the signal level exhibits a decibel-for-
decibel degradation with decreasing signal level. At lower signal
levels, where noise proves to be the dominant limitation, the
decibel EVM proves to be directly proportional to the SNR.
The ADL5380 shows excellent EVM performance for various
modulation schemes. Figure 86 shows the EVM performance of
the ADL5380 with a 16 QAM, 200 kHz low IF.
–50
–45
–40
–35
–30
–25
–20
–15
–10
–5
0
–90 –70 –50 –30 –10 10
EVM (dB)
RF INPUT POWER (dBm)
07585-082
Figure 86. EVM, RF = 900 MHz, IF = 200 kHz vs.
RF Input Power for a 16 QAM 160ksym/s Signal
ADL5380 Data Sheet
Rev. A | Page 26 of 36
Figure 87 shows the zero-IF EVM performance of a 10 MHz
IEEE 802.16e WiMAX signal through the ADL5380. The
differential dc offsets on the ADL5380 are in the order of a few
millivolts. However, ac coupling the baseband outputs with 10 µF
capacitors eliminates dc offsets and enhances EVM performance.
With a 10 MHz BW signal, 10 µF ac coupling capacitors with
the 500 Ω differential load results in a high-pass corner frequency
of ~64 Hz, which absorbs an insignificant amount of modulated
signal energy from the baseband signal. By using ac coupling
capacitors at the baseband outputs, the dc offset effects, which
can limit dynamic range at low input power levels, can be
eliminated.
–60
–50
–40
–30
–20
–10
0
–75 –65 –55 –45 –35 –25 –15 –5 5
EVM (dB)
RF INPUT POWER ( dBm)
5.8GHz
3.5GHz
2.6GHz
07585-083
Figure 87. EVM, RF = 2.6 GHz, RF = 3.5 GHz, and RF = 5.8 GHz, IF = 0 Hz vs.
RF Input Power for a 16 QAM 10 MHz Bandwidth Mobile WiMAX Signal
(AC-Coupled Baseband Outputs)
Figure 88 exhibits multiple W-CDMA low-IF EVM performance
curves over a wide RF input power range into the ADL5380. In
the case of zero-IF, the noise contribution by the vector signal
analyzer becomes predominant at lower power levels, making it
difficult to measure SNR accurately.
–45
–40
–35
–30
–25
–20
–15
–10
–80 –70 –60 –50 –40 –30 –20 –10 010
EVM (dB)
RF INPUT POWER ( dBm)
0Hz I F
5MHz LOW-IF
7.5MHz LOW-IF
2.5MHz LOW-IF
07585-084
Figure 88. EVM, RF = 1900 MHz, IF = 0 Hz, IF = 2.5 MHz, IF = 5 MHz, and IF =
7.5 MHz vs. RF Input Power for a W-CDMA Signal (AC-Coupled Baseband Outputs)
LOW IF IMAGE REJECTION
The image rejection ratio is the ratio of the intermediate frequency
(IF) signal level produced by the desired input frequency to that
produced by the image frequency. The image rejection ratio is
expressed in decibels. Appropriate image rejection is critical
because the image power can be much higher than that of the
desired signal, thereby plaguing the down-conversion process.
Figure 89 illustrates the image problem. If the upper sideband
(lower sideband) is the desired band, a 90° shift to the Q channel
(I channel) cancels the image at the lower sideband (upper sideband).
Phase and gain balance between I and Q channels are critical
for high levels of image rejection.
0°
0°
SIN
ωLOt
COS
ωLOt
ωIF ωIF
ωLSB ωUSB
–
ωIF
0 +
ωIF
0 +
ωIF
0 +
ωIF
–
ωIF
0 +
ωIF
ωLO
–90°
+90°
07585-085
Figure 89. Illustration of the Image Problem
Data Sheet ADL5380
Rev. A | Page 27 of 36
Figure 90 and Figure 91 show the excellent image rejection
capabilities of the ADL5380 for low IF applications, such as
W-CDMA. The ADL5380 exhibits image rejection greater than
45 dB over a broad frequency range.
50
30
40
60
0
10
20
400 800 1200 1600 2000 2400 2800 3200 3600 4000
IMAGE REJECTION (dB)
RF FREQUENCY (MHz)
2.5MHz LOW IF
5MHz LOW IF
7MHz LOW IF
07585-103
Figure 90. Low Band and Midband Image Rejection vs. RF Frequency for a
W-CDMA Signal, IF = 2.5 MHz, 5 MHz, and 7.5 MHz
50
30
40
60
0
10
20
5000 5200 5400 5600 5800 6000
IMAGE REJECTION (dB)
RF FREQUENCY (MHz)
2.5MHz LOW IF
5MHz LOW IF
7MHz LOW IF
07585-104
Figure 91. High Band Image Rejection vs. RF Frequency for a W-CDMA Signal,
IF = 2.5 MHz, 5 MHz, and 7.5 MHz
EXAMPLE BASEBAND INTERFACE
In most direct-conversion receiver designs, it is desirable to
select a wanted carrier within a specified band. The desired
channel can be demodulated by tuning the LO to the appropriate
carrier frequency. If the desired RF band contains multiple
carriers of interest, the adjacent carriers are also down converted to
a lower IF frequency. These adjacent carriers can be problematic if
they are large relative to the wanted carrier because they can
overdrive the baseband signal detection circuitry. As a result, it
is often necessary to insert a filter to provide sufficient rejection
of the adjacent carriers.
It is necessary to consider the overall source and load impedance
presented by the ADL5380 and ADC input when designing the
filter network. The differential baseband output impedance of
the ADL5380 is 50 Ω. The ADL5380 is designed to drive a high
impedance ADC input. It may be desirable to terminate the
ADC input down to lower impedance by using a terminating
resistor, such as 500 Ω. The terminating resistor helps to better
define the input impedance at the ADC input at the cost of a
slightly reduced gain (see the Circuit Description section for
details on the emitter-follower output loading effects).
The order and type of filter network depends on the desired high
frequency rejection required, pass-band ripple, and group delay.
Filter design tables provide outlines for various filter types and
orders, illustrating the normalized inductor and capacitor values
for a 1 Hz cutoff frequency and 1 Ω load. After scaling the
normalized prototype element values by the actual desired
cut-off frequency and load impedance, the series reactance
elements are halved to realize the final balanced filter network
component values.
As an example, a second-order Butterworth, low-pass filter design
is shown in Figure 92 where the differential load impedance is
500 Ω and the source impedance of the ADL5380 is 50 Ω. The
normalized series inductor value for the 10-to-1, load-to-source
impedance ratio is 0.074 H, and the normalized shunt capacitor
is 14.814 F. For a 10.9 MHz cutoff frequency, the single-ended
equivalent circuit consists of a 0.54 μH series inductor followed
by a 433 pF shunt capacitor.
The balanced configuration is realized as the 0.54 μH inductor
is split in half to realize the network shown in Figure 92.
V
S
R
S
2
R
S
R
L
R
S
2
R
L
2
R
L
2
433pF
V
S
R
S
= 50Ω
R
L
= 500Ω
0.54µH
0.27µH
0.27µH
433pF
BALANCED
CONFIGURATION
DENORMALIZED
SINGLE-ENDED
EQUIVALENT
V
S
R
S
= 50
Ω
= 0.1
R
L
= 500Ω
L
N
= 0.074H
C
N
14.814F
NORMALIZED
SINGLE-ENDED
CONFIGURATION
= 25Ω
= 25Ω
= 250Ω
= 250Ω
f
C
= 10.9MHz
f
C
= 1Hz
0
7585-087
Figure 92. Second-Order Butterworth, Low-Pass Filter Design Example
ADL5380 Data Sheet
Rev. A | Page 28 of 36
A complete design example is shown in Figure 95. A sixth-order
Butterworth differential filter having a 1.9 MHz corner frequency
interfaces the output of the ADL5380 to that of an ADC input.
The 500 Ω load resistor defines the input impedance of the
ADC. The filter adheres to typical direct conversion W-CDMA
applications where, 1.92 MHz away from the carrier IF frequency,
1 dB of rejection is desired, and, 2.7 MHz away from the carrier IF
frequency, 10 dB of rejection is desired.
Figure 93 and Figure 94 show the measured frequency response
and group delay of the filter.
10
5
–20
–15
–10
–5
0
03.53.02.52.01.51.00.5
MAGNITUDE RESPONSE (dB)
FREQUENCY (MHz)
07585-088
Figure 93. Sixth-Order Baseband Filter Response
900
800
700
600
500
400
300
200
100 00.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8
DEL AY ( ns)
FREQUENCY (MHz)
07585-089
Figure 94. Sixth-Order Baseband Filter Group Delay
Data Sheet ADL5380
Rev. A | Page 29 of 36
270pF
100pF
68pF
500Ω
C
AC
10µF
C
AC
10µF
27µH
27µH
10µH
27µH
27µH
10µH
C
AC
10µF
C
AC
10µF
27µH
27µH
10µH
27µH
27µH
10µH
270pF
100pF
68pF
500Ω
ADC INPUTADC INPUT
LO_SE
BALUN
ADL5380
0.1µF 100pF
RFIN
V
S
V
S
V
S
V
S
0.1µF 100pF
100pF 100pF
100pF 0.1µF
BALUN
100pF 100pF
1
VCC3
GND3
RFIP
RFIN
GND3
ADJ
ENBL
GND4
LOIP
LOIN
GND4
NC
24 23 22 21 20 19
7 8 9 10 11 12
2
3
4
5
6
GND3
GND1
IHI
ILO
GND1
VCC1
18
17
16
15
14
13
GND3
GND2
QHI
QLO
GND2
VCC2
07585-090
Figure 95. Sixth-Order Low-Pass Butterworth, Baseband Filter Schematic
ADL5380 Data Sheet
Rev. A | Page 30 of 36
As the load impedance of the filter increases, the filter design
becomes more challenging in terms of meeting the required
rejection and pass band specifications. In the previous W-CDMA
example, the 500 Ω load impedance resulted in the design of a
sixth-order filter that has relatively large inductor values and small
capacitor values. If the load impedance is 200 Ω, the filter design
becomes much more manageable. Figure 96 shows a fourth-order
filter designed for a 10 MHz wide LTE signal. As shown in Figure 96,
the resultant inductor and capacitor values become much more
practical with a 200 Ω load.
2.2µH
2.2µH
100pF
1.5µH
1.5µH
22pF
200Ω
50Ω
07585-091
Figure 96. Fourth-Order Low-Pass LTE Filter Schematic
Figure 97 and Figure 98 illustrate the magnitude response and
group delay response of the fourth-order filter, respectively.
–35
–25
–15
–5
–30
–20
–10
0
–40
5
FREQUENCY (MHz)
FREQUENCY RESPONSE (dB)
403530252015105
0
07585-092
Figure 97. Fourth-Order Low-Pass LTE Filter Magnitude Response
510 15 20 25 30 35 40
0
10
20
30
40
50
0
60
FREQUENCY (MHz)
GROUP DELAY ( ns)
07585-093
Figure 98. Fourth-Order Low-Pass LTE Filter Group Delay Response
Data Sheet ADL5380
Rev. A | Page 31 of 36
CHARACTERIZATION SETUPS
Figure 99 to Figure 101 show the general characterization bench
setups used extensively for the ADL5380. The setup shown in
Figure 101 was used to do the bulk of the testing and used
sinusoidal signals on both the LO and RF inputs. An automated
Agilent VEE program was used to control the equipment over
the
IEEE bus. This setup was used to measure gain, IP1dB, IIP2,
IIP3, I/Q gain match, and quadrature error. The ADL5380
characterization board had a 9-to-1 impedance transformer on
each of the differential baseband ports to do the differential-to-
single-ended conversion, which presented a 450 Ω differential load
to each baseband port, when interfaced with 50 Ω test equipment.
For all measurements of the ADL5380, the loss of the RF input
balun was de-embedded. Due to the wideband nature of the
ADL5380, three different board configurations had to be used to
characterize the product. For low band characterization (400 MHz
to 3 GHz), the Mini-Circuits TC1-1-13 balun was used on the
RF and LO inputs to create differential signals at the device pins.
For midband characterization (3 GHz to 4 GHz), the Johanson
Tec hnol og y 3600BL14M050T was used, and for high band
characterization (5 GHz to 6 GHz), the Johanson Technology
5400BL15B050E balun was used.
The two setups shown in Figure 99 and Figure 100 were used
for making NF measurements. Figure 99 shows the setup for
measuring NF with no blocker signal applied while Figure 100
was used to measure NF in the presence of a blocker. For both
setups, the noise was measured at a baseband frequency of
10 MHz. For the case where a blocker was applied, the output
blocker was at a 15 MHz baseband frequency. Note that great
care must be taken when measuring NF in the presence of a
blocker. The RF blocker generator must be filtered to prevent
its noise (which increases with increasing generator output power)
from swamping the noise contribution of the ADL5380. At least
30 dB of attention at the RF and image frequencies is desired.
For example, assume a 915 MHz signal applied to the LO inputs of
the ADL5380. To obtain a 15 MHz output blocker signal, the RF
blocker generator is set to 930 MHz and the filters tuned such
that there is at least 30 dB of attenuation from the generator at
both the desired RF frequency (925 MHz) and the image RF
frequency (905 MHz). Finally, the blocker must be removed
from the output (by the 10 MHz low-pass filter) to prevent
the blocker from swamping the analyzer.
HP 6235A
POWER SUPPLY
AGILENT 8665B
SIGNAL GENERATOR
IEEE
IEEE
PC CONTROLLER
CONTROL
SNS
OUTPUT AGI LENT N8974A
NOISE FIGURE ANALYZER
6dB P AD
ADL5380
CHAR BOARD
RF
LO
Q
I
GND
V
POS
LOW-PASS
FILTER
INPUT
R1
50Ω
FROM SNS PORT
07585-095
Figure 99. General Noise Figure Measurement Setup
ADL5380 Data Sheet
Rev. A | Page 32 of 36
R&S F S E A30
SPE CTRUM ANALYZER
HP 6235A
POWER SUPPLY
AGILENT 8665B
SIGNAL GENERATOR
LOW-PASS
FILTER
R&S SM T03
SIGNAL GENERATOR
ADL5380
CHAR BOARD
RF
LO
Q
I
GND
V
POS
6dB P AD
6dB P AD
6dB P AD
R1
50Ω
BAND-PASS
CAVITY FILTER
BAND-PASS
TUNABLE FILTER BAND-REJECT
TUNABLE FILTER
HP 87405
LOW NOISE
PREAMP
07585-096
Figure 100. Measurement Setup for Noise Figure in the Presence of a Blocker
R&S F S E A30
SPE CTRUM ANALYZER HP 8508A
VECTOR VOLT MET ER
R&S SM T06
AGILENT E 3631
POWER SUPPLY
AGILENT E 8257D
SIGNAL GENERATOR
PC CONTROLLER
R&S SM T06
IEEE IEEE IEEE IEEE
IEEE IEEE
ADL5380
CHAR BOARD
RF
LO
Q
I
GND
VPOS
6dB P AD
6dB P AD
6dB P AD
6dB P AD
SWITCH
MATRIX
RF
AMPLIFIER
VP GND
OUTIN 3dB P AD
3dB P AD
3dB P AD
3dB P AD
RF
RF
AGILENT
11636A
INP UT CHANNELS
A AND B
RF
INPUT
IEEE
07585-097
Figure 101. General Characterization Setup
Data Sheet ADL5380
Rev. A | Page 33 of 36
EVALUATION BOARD
The ADL5380 evaluation board is available. The evaluation board
is populated with the wide band TCM1-63AX+ transformer
from Mini-Circuits. This transformer covers the entire
frequency range of the ADL5380 from 400 MHz to 6 GHZ.
The board can be used for single-ended or differential baseband
analysis. The default configuration of the board is for single-ended
baseband analysis.
C5x C12x
C9x C6x
VPOS
LO_SE
C3xC2x
T3x
T1x
ADL5380
VCC3
GND3
RFIP
RFIN
GND3
ADJ
ENBL
GND4
LOIP
LOIN
GND4
NC
GND3
GND1
IHI
ILO
GND1
VCC1
GND3
GND2
QHI
QLO
GND2
VCC2
R10x
T2x
R14x
R13x
R18x
C11x C8x
VPOS VPOS
VPOS
R19x
R5x
R17x R16x
R15x
R4x
C16x R7x
T4x R6x
P1x
VPOS
VPOS
R11x R1xR9x
C1x C4x
C7x C10x
R12x
C15x
R3x
R2x
R23x
LONx
LOPx
INx
IPx QPx
QNx
RFx
1
24 23 22 21 20 19
7 8 9 10 11 12
2
3
4
5
6
18
17
16
15
14
13
07585-098
Figure 102. Evaluation Board Schematic
ADL5380 Data Sheet
Rev. A | Page 34 of 36
Table 5. Evaluation Board Configuration Options
Component Description Default Condition
VPOSx, GNDx Power Supply and Ground Vector Pins. Not applicable
R10x, R12x,
R19x
Power Supply Decoupling. Shorts or power supply decoupling resistors. R10x, R12x, R19x = 0 Ω (0603)
C6x to C11x The capacitors provide the required dc coupling up to 6 GHz. C6x, C7x, C8x = 100 pF (0402),
C9x, C10x, C11x = 0.1 µF (0603)
P1x, R11x,
R9x, R1x
Device Enable. When connected to VS, the device is active. P1x, R9x = DNI, R1x = DNI,
R11x = 0 Ω
R23x Adjust Pin. The resistor value here sets the bias voltage at this pin and optimizes
third-order distortion.
R23x = 1.5 kΩ (0603)
C1x to C5x,
C12x
AC Coupling Capacitors. These capacitors provide the required ac coupling
from 400 MHz to 4 GHz.
C1x, C4x = DNI,
C2x, C3x, C5x, C12x = 100 pF (0402)
R2x to R7x,
R13x to R18x
Single-Ended Baseband Output Path. This is the default configuration of the
evaluation board. R13x to R18x are populated for appropriate balun interface.
R2x to R5x are not populated. Baseband outputs are taken from QHI and IHI. The
user can reconfigure the board to use full differential baseband outputs. R2x to R5x
provide a means to bypass the 9:1 TCM9-1 transformer to allow for differential base-
band outputs. Access the differential baseband signals by populating R2x to R5x
with 0 Ω and not populating R13x to R18x. This way the transformer does not need
to be removed. The baseband outputs are taken from the SMAs of QHI, QLO, IHI,
and ILO. R6x and R7x are provisions for applying a specific differential load across
the baseband outputs
R2x to R7x = open,
R13x to R18x = 0 Ω (0402)
T2x, T4x IF Output Interface. TCM9-1 converts a differential high impedance IF output to
a single-ended output. When loaded with 50 Ω, this balun presents a 450 Ω load
to the device. The center tap can be decoupled through a capacitor to ground.
T2x, T4x = TCM9-1, 9:1 (Mini-Circuits)
C15x, C16x Decoupling Capacitors. C15x and C16x are the decoupling capacitors used to reject
noise on the center tap of the TCM9-1.
C15x, C16x = 0.1 µF (0402)
T1x LO Input Interface. A 1:1 RF balun that converts the single-ended RF input to
differential signal is used.
TCM1-63AX+
T3x RF Input Interface. A 1:1 RF balun that converts the single-ended RF input to
differential signal is used.
TCM1-63AX+
07585-099
Figure 103. Evaluation Board Top Layer
Data Sheet ADL5380
Rev. A | Page 35 of 36
THERMAL GROUNDING AND EVALUATION
BOARD LAYOUT
The package for the ADL5380 features an exposed paddle on the
underside that should be well soldered to a low thermal and
electrical impedance ground plane. This paddle is typically
soldered to an exposed opening in the solder mask on the
evaluation board. Figure 104 illustrates the dimensions used in
the layout of the ADL5380 footprint on the ADL5380 evaluation
board (1 mil = 0.0254 mm).
Notice the use of nine via holes on the exposed paddle. These
ground vias should be connected to all other ground layers on
the evaluation board to maximize heat dissipation from the
device package.
07585-105
82 mil.
12 mil.
12 mil.
23 mil.
133.8 mil.
98.4 mil.
19.7 mil.
25 mil.
Figure 104. Dimensions for Evaluation Board Layout for the ADL5380 Package
Under these conditions, the thermal impedance of the ADL5380
was measured to be approximately 30°C/W in still air.
ADL5380 Data Sheet
Rev. A | Page 36 of 36
OUTLINE DIMENSIONS
COMPLIANT
TO
JEDEC S TANDARDS MO- 220- V GGD-8
04-11-2012-A
1
0.50
BSC
PI N 1
INDICATOR
2.50 RE F
0.50
0.40
0.30
TOP VIEW
12° M AX 0.80 MAX
0.65 TYP
SEATING
PLANE COPLANARITY
0.08
1.00
0.85
0.80
0.30
0.23
0.18
0.05 M AX
0.02 NOM
0.20 RE F
0.25 M IN
2.65
2.50 S Q
2.35
24
7
19
12
13
18
6
0.60 M AX
0.60 M AX
PI N 1
INDICATOR
4.10
4.00 S Q
3.90
3.75 BS C
SQ
EXPOSED
PAD
FOR PROPE R CONNECTION OF
THE EXPOSED PAD, REFER TO
THE P IN CONFIGURAT ION AND
FUNCTION DE S CRIPTIONS
SECTION OF THIS DATA SHEET.
BOTTOM VIEW
Figure 105. 24-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
4 mm × 4 mm Body, Very Thin Quad
(CP-24-3)
Dimensions shown in millimeters
ORDERING GUIDE
Model1 Temperature Range Package Description PackageOption Ordering Quantity
ADL5380ACPZ-R7 –40°C to +85°C 24-Lead LFCSP_VQ CP-24-3 1,500, 7” Tape and Reel
ADL5380ACPZ-WP –40°C to +85°C 24-Lead LFCSP_VQ CP-24-3 64, Waffle Pack
ADL5380-EVALZ 1
1 Z = RoHS Compliant Part.
©2009–2013 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D07585-0-7/13(A)