LTC3201
1
3201f
APPLICATIO S
U
TYPICAL APPLICATIO
U
FEATURES
DESCRIPTIO
U
The LTC
®
3201 is an ultralow noise, constant frequency,
charge pump DC/DC converter specifically designed for
powering white LEDs. The part produces a low noise
boosted supply capable of supplying 100mA of output
current. LED current is regulated for accurate and stable
backlighting. A 3-bit DAC provides output current adjust
for brightness control.
Low external parts count (one small flying capacitor and
three small bypass capacitors) and small MSOP-10 pack-
age size make the LTC3201 ideally suited for space con-
strained applications. An input noise filter further reduces
input noise, thus enabling direct connection to the battery.
High switching frequency enables the use of small external
capacitors.
The LTC3201 contains overtemperature protection and
can survive an indefinite output short to GND. Internal
soft-start circuitry also prevents excessive inrush current
on start-up. A low current shutdown feature disconnects
the load from V
IN
and reduces quiescent current to less
than 1µA.
■
White LED Backlighting
■
Programmable Boost Current Source
■
Input Noise Filter Minimizes Supply Noise
■
Constant Frequency Operation
■
3-Bit LED Current Control
■
No Inductors
■
Low Shutdown Current: I
IN
< 1µA
■
Output Current: 100mA
■
V
IN
Range: 2.7V to 4.5V
■
1.8MHz Switching Frequency
■
Soft-Start Limits Inrush Current at Turn-On
■
Short-Circuit and Overtemperature Protected
■
Available in 10-Pin MSOP Package
100mA Ultralow Noise
Charge Pump LED Supply
with Output Current Adjust
Ultralow Noise White LED Driver
with Adjustable Current Control Input Current Ripple
, LTC and LT are registered trademarks of Linear Technology Corporation.
LTC3201
V
IN
CM CP
V
OUT
D0-D2
FILTER
GND FB
1µF
1µF
0.22µF
0.22µF
56Ω56Ω56Ω
UP TO
6-WHITE LEDs
Li ION
LED
CURRENT
ADJUST
3
3201 TA01a
+
• • •
3201 TA01b
50mA/DIV
IOUT = 100mA
IIN = 205mA
VIN = 3.6V
100ns/DIV
LTC3201
2
3201f
ABSOLUTE AXI U RATI GS
W
WW
U
PACKAGE/ORDER I FOR ATIO
UUW
(Note 1)
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 3.6V, CFILTER = CFLY = 0.22µF, CIN = COUT = 1µF,
tMIN to tMAX unless otherwise noted.
V
IN
, V
FILTER
, V
OUT
, CP, CM to GND ..............–0.3V to 6V
D0, D1, D2, FB to GND ................. –0.3V to (V
IN
+ 0.3V)
V
OUT
Short-Circuit Duration............................. Indefinite
I
OUT ......................................................................................
150mA
Operating Temperature Range (Note 2) ...–40°C to 85°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec)..................300°C
ORDER PART
NUMBER
MS PART
MARKING
T
JMAX
= 150°C
θ
JA
= 130°C/W (1 LAYER BOARD)
θ
JA
= 100°C/W (4 LAYER BOARD)
Consult LTC Marketing for parts specified with wider operating temperature ranges.
LTC3201EMS
PARAMETER CONDITIONS MIN TYP MAX UNITS
V
IN
Operating Voltage ●2.7 4.5 V
V
IN
Operating Current I
OUT
= 0mA ●4 6.5 mA
V
IN
Shutdown Current D0, D1, D2 = 0V, V
OUT
= 0V ●1µA
Open-Loop Output Impedance I
OUT
= 100mA 8 Ω
Input Current Ripple I
IN
= 200mA 30 mA
P-P
Output Ripple I
OUT
= 100mA, C
OUT
= 1µF30mV
P-P
V
FB
Regulation Voltage D0 = D1 = D2 = V
IN
●0.57 0.63 0.66 V
V
FB
DAC Step Size 90 mV
Switching Frequency Oscillator Free Running 1.4 1.8 MHz
D0 to D2 Input Threshold ●0.4 1.1 V
D0 to D2 Input Current ●–1 1 µA
V
OUT
Short-Circuit Current V
OUT
= 0V 150 mA
V
OUT
Turn-On Time I
OUT
= 0mA 1 ms
LTVB
1
2
3
4
5
V
OUT
CP
FILTER
CM
GND
10
9
8
7
6
FB
V
IN
D2
D1
D0
TOP VIEW
MS PACKAGE
10-LEAD PLASTIC MSOP
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
Note 2: The LTC3201E is guaranteed to meet performance specifications
from 0°C to 70°C. Specifications over the –40°C to 85°C operating
temperature range are assured by design, characterization and correlation
with statistical process controls.
LTC3201
3
3201f
TYPICAL PERFOR A CE CHARACTERISTICS
UW
SUPPLY VOLTAGE (V)
2.7
0.640
0.635
0.630
0.625
0.620
0.615
0.610
0.605 3.6 4.2
3201 G01
3.0 3.3 3.9 4.5
FEEDBACK VOLTAGE (V)
C
FLY
= C
FILTER
= O.22µF
C
IN
= C
OUT
= 1µFT
A
= 85°C
T
A
= –40°C
T
A
= 25°C
LOAD CURRENT (mA)
0
4.15
4.10
4.05
4.00
3.95
3.90
3.85
3.80
3201 G02
20 40 60 80 100 120 140 160 180 200
OUTPUT VOLTAGE (V)
C
FLY
= C
FILTER
= O.22µF
C
IN
= C
OUT
= 1µF
T
A
= 25°C
V
IN
= 4.5V
V
IN
= 3.2V
V
IN
= 2.7V
SUPPLY VOLTAGE (V)
2.7
OSCILLATOR FREQUENCY (MHz)
2.2
2.0
1.8
1.6
1.4
1.2 3.3 3.9 4.2
3201 G03
3.0 3.6 4.5
C
FLY
= C
FILTER
= O.22µF
C
IN
= C
OUT
= 1µF
V
OUT
= 4V
T
A
= 85°C
T
A
= –40°C
T
A
= 25°C
SUPPLY VOLTAGE (V)
2.7
SHORT-CIRCUIT CURRENT (mA)
250
200
150
100
50
03.3 3.9 4.2
3201 G04
3.0 3.6 4.5
CFLY = CFILTER = O.22µF
CIN = COUT = 1µF
TA = 25°C
FEEDBACK VOLTAGE (V)
0.620
0.615
0.610
0.605
0.600
0.595
0.590
C
FLY
= C
FILTER
= O.22µF
C
IN
= C
OUT
= 1µF
T
A
= 25°C
SUPPLY VOLTAGE (V)
2.7 3.3 3.9 4.2
3201 G05
3.0 3.6 4.5
Feedback Voltage vs Supply
Voltage
Oscillator Frequency vs Supply
Voltage
Feedback Voltage
vs Supply Voltage
IOUT = 100mA, VOUT = 4V
Output Voltage vs Load Current
Short-Circuit Current vs Supply
Voltage Feedback Voltage vs I
OUT
I
OUT
(mA)
0
V
FB
(V)
0.64
0.62
0.60
0.58
0.56
0.54
0.52
0.50 20
3201 G06
40 60 80 100 120 140 160180 200 220
C
FLY
= C
FILTER
= 0.22µF
C
IN
= C
OUT
= 1µF
T
A
= 25°C
V
IN
= 3.6V
LTC3201
4
3201f
UU
U
PI FU CTIO S
V
OUT
(Pin 1): Charge Pump Output. Bypass with a 1µF
ceramic capacitor to GND.
CP (Pin 2): Flying Capacitor Positive Terminal.
FILTER (Pin 3): Input Noise Filter Terminal. Bypass with a
0.22µF high resonant frequency ceramic capacitor to
GND. Place filter capacitor less than 1/8" from device.
CM (Pin 4): Flying Capacitor Negative Terminal.
GND (Pin 5): Ground. Connect to a ground plane for best
performance.
D0 (Pin 6): Current Control DAC LSB Input.
D1 (Pin 7): Current Control DAC Bit 1 Input.
D2 (Pin 8): Current Control DAC MSB Input. Inputs D0 to
D2 program a 3-bit DAC output which is used as the
internal reference voltage. The DAC output reference volt-
age is used to regulate amount of current flowing through
the LEDs. An internal control loop adjusts the charge
pump output such that the voltage drop across an external
sense resistor connected from FB to GND equals the
internal DAC output reference voltage. See Truth Table in
Applications Information section for internal reference
settings vs DAC code. When D0 to D2 are low, the part
enters a low current shutdown mode and the load is
disconnected from V
IN
.
V
IN
(Pin 9): Input Voltage. V
IN
may be between 2.7V and
4.5V. Bypass V
IN
with a 1µF low ESR capacitor to ground.
FB (Pin 10): Charge Pump Feedback Input. This pin acts
as a sense pin for I
OUT
. Connect a sense resistor between
FB and GND to set the output current. I
OUT
will be adjusted
until V
FB
= internal DAC output reference.
SI PLIFIED
W
BLOCK DIAGRA
W
–
+
3201 BD
CHARGE
PUMP
3-BIT
DAC
LPF
3
1
10
9
5
2
4
8
7
6
SOFT-START
AND
SWITCH CONTROL
1.8MHz
OSCILLATOR
GND
FILTER
V
IN
V
OUT
FB
CP
CM
D1
D2
D0
1.2V
LTC3201
5
3201f
APPLICATIO S I FOR ATIO
WUUU
Operation (Refer to Simplified Block Diagram)
The LTC3201 is a switched capacitor boost charge pump
especially designed to drive white LEDs in backlighting
applications. The LTC3201’s internal regulation loop
maintains constant LED output current by monitoring the
voltage at the FB pin. The device has a novel internal filter
that, along with an external 0.22µF capacitor, significantly
reduces input current ripple. An internal 7-state DAC
allows the user to lower the regulation voltage at the FB
pin, thus lowering the LED current. To regulate the output
current, the user places a sense resistor between FB and
GND. The white LED is then placed between V
OUT
and FB.
The value at the FB pin is then compared to the output of
the DAC. The charge pump output voltage is then changed
to equalize the DAC output and the FB pin. The value of the
sense resistor determines the maximum value of the
output current.
When the charge pump is enabled, a two-phase
nonoverlapping clock activates the charge pump switches.
The flying capacitor is charged to V
IN
on phase one of the
clock. On phase two of the clock, it is stacked in series with
V
IN
and connected to V
OUT
. This sequence of charging and
discharging the flying capacitor continues at a free run-
ning frequency of 1.8MHz (typ) until the FB pin voltage
reaches the value of the DAC.
In shutdown mode all circuitry is turned off and the
LTC3201 draws only leakage current (<1µA) from the V
IN
supply. Furthermore, V
OUT
is disconnected from V
IN
. The
LTC3201 is in shutdown when a logic low is applied to all
three D0:D2 pins. Note that if V
OUT
floats to >1.5V,
shutdown current will increase to 10µA max. In normal
operation, the quiescent supply current of the LTC3201
will be slightly higher if any of the D0:D2 pins is driven high
with a signal that is below V
IN
than if it is driven all the way
to V
IN
. Since the D0:D2 pins are high impedance CMOS
inputs, they should never be allowed to float.
Input Current Ripple
The LTC3201 is designed to minimize the current ripple at
V
IN
. Typical charge pump boost converters draw large
amounts of current from V
IN
during both phase 1 and
phase 2 of the clocking. If there is a large nonoverlap time
between the two phases, the current being drawn from V
IN
can go down to zero during this time. At the full load of
100mA at the output, this means that the input could
potentially go from 200mA down to 0mA during the
nonoverlap time. The LTC3201 mitigates this problem by
minimizing the nonoverlap time, using a high (1.8MHz)
frequency clock, and employing a novel noise FILTER
network. The noise filter consists of internal circuitry plus
external capacitors at the FILTER and V
IN
pins. The filter
capacitor serves to cancel the higher frequency compo-
nents of the noise, while the V
IN
capacitor cancels out the
lower frequency components. The recommended values
are 0.22µF for the FILTER capacitor and 1µF for the V
IN
capacitor. Note that these capacitors must be of the highest
possible resonant frequencies. See Layout Considerations.
3-Bit DAC for Output Current Control
Digital pins D0, D1, D2 are used to control the output
current level. D0 = D1 = D2 = V
IN
allows the user to program
an output LED current that is equal to 0.63V/R
SENSE
, where
R
SENSE
is the resistor connected to any single LED and
connected between FB and ground. Due to the finite
transconductance of the regulation loop, for a given diode
setting, the voltage at the FB Pin will decrease as output
current increases. All LEDs subsequently connected in
parallel should then have similar currents. The mismatch-
ing of the LED V
F
and the mismatching of the
sense
resistors will cause a differential current error between
LEDs connected to the same output. Once the
sense
resistor is selected, the user can then control the voltage
applied across that resistor by changing the digital values
at D0:D2. This in turn controls the current into the LED.
Note that there are only 7 available current states. The 8th
is reserved to shutdown. This is the all 0s code. Refer to
Table below.
D0 D1 D2 FB
HIGH HIGH HIGH 0.63V
HIGH HIGH LOW 0.54V
HIGH LOW HIGH 0.45V
HIGH LOW LOW 0.36V
LOW HIGH HIGH 0.27V
LOW HIGH LOW 0.18V
LOW LOW HIGH 0.09V
LOW LOW LOW Shutdown
LTC3201
6
3201f
Power Efficiency
The power efficiency (η) of the LTC3201 is similar to that
of a linear regulator with an effective input voltage of twice
the actual input voltage. This occurs because the input
current for a voltage doubling charge pump is approxi-
mately twice the output current. In an ideal regulator the
power efficiency would be given by:
η= = =
P
P
VI
VI
V
V
OUT
IN
OUT OUT
IN OUT
OUT
IN
•
•2 2
At moderate to high output power the switching losses
and quiescent current of LTC3201 are relatively low. Due
to the high clocking frequency, however, the current used
for charging and discharging the switches starts to reduce
efficiency. Furthermore, due to the low V
F
of the LEDs,
power delivered will remain low.
Short-Circuit/Thermal Protection
The LTC3201 has short-circuit current limiting as well as
overtemperature protection. During short-circuit condi-
tions, the output current is limited to typically 150mA.
On-chip thermal shutdown circuitry disables the charge
pump once the junction temperature exceeds approxi-
mately 160°C and re-enables the charge pump once the
junction temperature drops back to approximately 150°C.
The LTC3201 will cycle in and out of thermal shutdown
indefinitely without latchup or damage until the short-
circuit on V
OUT
is removed.
V
OUT
Capacitor Selection
The style and value of capacitors used with the LTC3201
determine several important parameters such as output
ripple, charge pump strength and minimum start-up time.
To reduce noise and ripple, it is recommended that low
ESR (<0.1Ω) capacitors be used for C
FILTER
, C
IN
, C
OUT
.
These capacitors should be ceramic.
The value of C
OUT
controls the amount of output ripple.
Increasing the size of C
OUT
to 10µF or greater will reduce
the output ripple at the expense of higher turn-on times
and start-up current. See the section Output Ripple. A 1µF
C
OUT
is recommended.
V
IN
, V
FILTER
Capacitor Selection
The value and resonant frequency of C
FILTER
and C
IN
greatly determine the current noise profile at V
IN
. C
FILTER
should be a high frequency 0.22µF capacitor with a reso-
nant frequency over 30MHz. Input capacitor C
IN
should be
a 1µF ceramic capacitor with a resonant frequency over
1MHz. The X5R capacitor is a good choice for both. The
values of C
FILTER
(0.22µF) and C
IN
(1µF) provide optimum
high and low frequency input current filtering. A higher
filter cap value will result in lower low frequency input
current ripple, but with increased high frequency ripple.
The key at the FILTER node is that the capacitor has to be
very high frequency. If capacitor technology improves the
bandwidth, then higher values should be used. Similarly,
increasing the input capacitor value but decreasing its
resonant frequency will not really help. Decreasing it will
help the high frequency performance while increasing the
low frequency current ripple.
Direct Connection to Battery
Due to the ultra low input current ripple, it is possible to
connect the LTC3201 directly to the battery without using
regulators or high frequency chokes.
Flying Capacitor Selection
Warning: A polarized capacitor such as tantalum or alumi-
num should never be used for the flying capacitor since its
voltage can reverse upon start-up. Low ESR ceramic
capacitors should always be used for the flying capacitor.
The flying capacitor controls the strength of the charge
pump. In order to achieve the rated output current it is
necessary to have at least 0.22µF of capacitance for the
flying capacitor. Capacitors of different materials lose
their capacitance with higher temperature and voltage at
different rates. For example, a ceramic capacitor made of
X7R material will retain most of its capacitance from
–40°C to 85°C whereas a Z5U and Y5V style capacitor will
lose considerable capacitance over that range. Z5U and
Y5V capacitors may also have a very strong voltage
coefficient causing them to lose 60% or more of their
capacitance when the rated voltage is applied. Therefore,
when comparing different capacitors it is often more
APPLICATIO S I FOR ATIO
WUUU
LTC3201
7
3201f
appropriate to compare the achievable capacitance for a
given case size rather than discussing the specified ca-
pacitance value. For example, over the rated voltage and
temperature, a 1µF, 10V, Y5V ceramic capacitor in an 0603
case may not provide any more capacitance than a 0.22µF
10V X7R available in the same 0603 case. The capacitor
manufacturer’s data sheet should be consulted to deter-
mine what value of capacitor is needed to ensure 0.22µF
at all temperatures and voltages.
Below is a list of ceramic capacitor manufacturers and
how to contact them:
AVX (843) 448-9411 www.avxcorp.com
Kemet (864) 963-6300 www.kemet.com
Murata (770) 436-1300 www.murata.com
Taiyo Yuden (800) 348-2496 www.t-yuden.com
Vishay (610) 644-1300 www.vishay.com
Open-Loop Output Impedance
The theoretical minimum open-loop output impedance of
a voltage doubling charge pump is given by:
RVV
IFC
OUT MIN IN OUT
OUT
() –
==
21
where F if the switching frequency (1.8MHz typ) and C is
the value of the flying capacitor. (Using units of MHz and
µF is convenient since they cancel each other). Note that
the charge pump will typically be weaker than the theoreti-
cal limit due to additional switch resistance. Under normal
operation, however, with V
OUT
≈ 4V, I
OUT
< 100mA,
V
IN
> 3V, the output impedance is given by the closed-loop
value of ~0.5Ω.
Output Ripple
The value of C
OUT
directly controls the amount of ripple for
a given load current. Increasing the size of C
OUT
will reduce
the output ripple at the expense of higher minimum turn-
on time and higher start-up current. The peak-to-peak
output ripple is approximated by the expression:
VI
FC
RIPPLE P P OUT
OUT
() •
−≅2
F is the switching frequency (1.8MHz typ).
Loop Stability
Both the style and the value of C
OUT
can affect the stability
of the LTC3201. The device uses a closed loop to adjust
the strength of the charge pump to match the required
output current. The error signal of this loop is directly
stored on the output capacitor. The output capacitor also
serves to form the dominant pole of the loop. To prevent
ringing or instability, it is important for the output capaci-
tor to maintain at least 0.47µF over all ambient and
operating conditions.
Excessive ESR on the output capacitor will degrade the
loop stability of the LTC3201. The closed loop DC imped-
ance is nominally 0.5Ω. The output will thus change by
50mV with a 100mA load. Output capacitors with ESR of
0.3Ω or greater could cause instability or poor transient
response. To avoid these problems, ceramic capacitors
should be used. A tight board layout with good ground
plane is also recommended.
Soft-Start
The LTC3201 has built-in soft-start circuitry to prevent
excessive input current flow at V
IN
during start-up. The
soft-start time is programmed at approximately 30µs.
Layout Considerations
Due to the high switching frequency and large transient
currents produced by the LTC3201, careful board layout is
necessary. A true ground plane is a must. To minimize
high frequency input noise ripple, it is especially important
that the filter capacitor be placed with the shortest dis-
tance to the LTC3201 (1/8 inch or less). The filter capacitor
should have the highest possible resonant frequency.
Conversely, the input capacitor does not need to be placed
close to the pin. The input capacitor serves to cancel out
the lower frequency input noise ripple. Extra inductance
on the V
IN
line actually helps input current ripple. Note that
if the V
IN
trace is lengthened to add parasitic inductance,
it starts to look like an antenna and worsen the radiated
noise. It is recommended that the filter capacitor be placed
on the left hand side next to Pin 3. The flying capacitor can
then be placed on the top of the device. It is also important
APPLICATIO S I FOR ATIO
WUUU
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
LTC3201
8
3201f
RELATED PARTS
PACKAGE DESCRIPTIO
U
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900
●
FAX: (408) 434-0507
●
www.linear.com
LINEAR TECHNOLOGY CORPORATION 2001
LT/TP 0102 2K • PRINTED IN USA
TYPICAL APPLICATIO
U
PART NUMBER DESCRIPTION COMMENTS
LTC1682/-3.3/-5 Doubler Charge Pumps with Low Noise LDO MS8 and SO-8 Packages, I
OUT
= 80mA, Output Noise = 60µV
RMS
LTC1751/-3.3/-5 Doubler Charge Pumps V
OUT
= 5V at 100mA, V
OUT
= 3.3V at 80mA, ADJ, MSOP Packages
LTC1754-3.3/-5 Doubler Charge Pumps with Shutdown ThinSOTTM Package, I
Q
= 13µA, I
OUT
= 50mA
LTC1928-5 Doubler Charge Pumps with Low Noise LDO ThinSOT Output Noise = 90µV
RMS
, V
OUT
= 5V, V
IN
= 2.7V to 4.4V
LT1932 Low Noise Boost Regulator LED Driver ThinSOT Package, High Efficiency, up to 16 LEDs
LTC3200/-5 Low Noise Doubler Charge Pump MS8 and ThinSOT (LTC3200-5) Package, I
OUT
= 100mA,
2MHz Fixed Frequency
LTC3202 Low Noise High Efficiency Charge Pump MS10 Package, 125mA Output, High Efficiency
to place the output capacitor as close to the pin as possible
to minimize inductive ringing and parasitic resistance.
Thermal Management
For higher input voltages and maximum output current
there can be substantial power dissipation in the
LTC3201. If the junction temperature increases above
approximately160°C the thermal shutdown circuitry will
automatically deactivate the output. To reduce the maxi-
mum junction temperature, a good thermal connection to
PC board is recommended. Connecting the GND pin (Pin
4) to a ground plane, and maintaining a solid ground plane
under the device on two layers of the PC board can reduce
the thermal resistance of the package and PC board
system.
MS Package
10-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1661)
ThinSOT is a trademark of Linear Technology Corporation.
MSOP (MS) 1001
0.53 ± 0.01
(.021 ± .006)
SEATING
PLANE
0.18
(.007)
1.10
(.043)
MAX
0.17 – 0.27
(.007 – .011) 0.13 ± 0.05
(.005 ± .002)
0.86
(.034)
REF
0.50
(.0197)
TYP
12345
4.88 ± 0.10
(.192 ± .004)
0.497 ± 0.076
(.0196 ± .003)
REF
8910 76
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
3.00 ± 0.102
(.118 ± .004)
NOTE 4
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
0.254
(.010) 0° – 6° TYP
DETAIL “A”
DETAIL “A”
GAUGE PLANE
5.23
(.206)
MIN
3.2 – 3.45
(.126 – .136)
0.889 ± 0.127
(.035 ± .005)
RECOMMENDED SOLDER PAD LAYOUT
WITHOUT EXPOSED PAD OPTION
3.05 ± 0.38
(.0120 ± .0015)
TYP
0.50
(.0197)
BSC
