650 kHz /1.3 MHz Step-Up
PWM DC-to-DC Switching Converters
Data Sheet
ADP1612/ADP1613
Rev. D
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FEATURES
Current limit
1.4 A for the ADP1612
2.0 A for the ADP 1613
Minimum input voltage
1.8 V for the ADP1612
2.5 V for the ADP1613
Pin-selectable 650 kHz or 1.3 MHz PWM frequency
Adjustable output voltage up to 20 V
Adjustable soft start
Undervoltage lockout
Thermal shutdown
8-lead MSOP
Supported by ADIsimPower™ design tool
ADIsimPower downloadable design tools for boost, coupled-
SEPIC, and SEPIC Cuk configurations
APPLICATIONS
TFT LCD bias supplies
Portable applications
Industrial/instrumentation equipment
TYPICAL APPLICATION CIRCUIT
ADP1612/
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
1.3MHz
650kHz
(DEFAULT)
V
OUT
V
IN
L1
C
IN
C
SS
C
OUT
C
COMP
R
COMP
R1
R2
D1
06772-001
Figure 1. Step-Up Regulator Configuration
GENERAL DESCRIPTION
The ADP1612/ADP1613 are step-up dc-to-dc switching con-
verters with an integrated power switch capable of providing
an output voltage as high as 20 V. With a package height of less
than 1.1 mm, the ADP1612/ADP1613 are optimal for space-
constrained applications such as portable devices or thin film
transistor (TFT) liquid crystal displays (LCDs).
The ADP1612/ADP1613 operate in current mode pulse-width
modulation (PWM) with up to 94% efficiency. Adjustable
soft start prevents inrush currents when the part is enabled.
The pin-selectable switching frequency and PWM current-mode
architecture allow for excellent transient response, easy noise
filtering, and the use of small, cost-saving external inductors
and capacitors. Other key features include undervoltage lockout
(UVLO), thermal shutdown (TSD), and logic controlled enable.
The ADP1612/ADP1613 are available in the lead-free
8-lead M S O P.
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-009
V
IN
= 5V
fSW
= 1.3M Hz
T
A
= 25° C
ADP1612, V
OUT
= 12V
ADP1612, V
OUT
= 15V
ADP1613, V
OUT
= 12V
ADP1613, V
OUT
= 15V
Figure 2. ADP1612/ADP1613 Efficiency for Various Output Voltages
ADP1612/ADP1613 Data Sheet
Rev. D | Page 2 of 28
TABLE OF CONTENTS
Features .............................................................................................. 1
Applications ....................................................................................... 1
Typical Application Circuit ............................................................. 1
General Description ......................................................................... 1
Revision History ............................................................................... 2
Specifications ..................................................................................... 3
Absolute Maximum Ratings ............................................................ 4
Thermal Resistance ...................................................................... 4
Boundary Condition .................................................................... 4
ESD Caution .................................................................................. 4
Pin Configuration and Function Descriptions ............................. 5
Typical Performance Characteristics ............................................. 6
Theory of Operation ...................................................................... 11
Current-Mode PWM Operation .............................................. 11
Frequency Selection ................................................................... 11
Soft Start ...................................................................................... 11
Thermal Shutdown (TSD) ......................................................... 12
UnderVoltage Lockout (UVLO) ............................................... 12
Enable/Shutdown Control ........................................................ 12
Applications Information .............................................................. 13
ADIsimPower Design Tool ....................................................... 13
Setting the Output Voltage ........................................................ 13
Inductor Selection ...................................................................... 13
Choosing the Input and Output Capacitors ........................... 14
Diode Selection ........................................................................... 14
Loop Compensation .................................................................. 14
Soft Start Capacitor .................................................................... 15
Typical Application Circuits ......................................................... 16
Step-Up Regulator ...................................................................... 16
Step-Up Regulator Circuit Examples ....................................... 16
SEPIC Converter ........................................................................ 22
TFT LCD Bias Supply ................................................................ 22
PCB Layout Guidelines .................................................................. 24
Outline Dimensions ....................................................................... 25
Ordering Guide .......................................................................... 25
REVISION HISTORY
11/12—Rev. C to Rev. D
Changes to Choosing the Input and Output Capacitors Section
and Loop Compensation Section .................................................. 14
7/12—Rev. B to Rev. C
Changes to Features Section............................................................. 1
Added ADIsimPower Design Tool Section .................................. 13
Changes to Ordering Guide ........................................................... 25
4/11—Rev. A to Rev. B
Changes to Features Section............................................................ 1
Changes to Reference Feedback Voltage Parameter .................... 3
Changes to Ordering Guide .......................................................... 25
9/09—Rev. 0 to Rev. A
Changes to Figure 45 ...................................................................... 17
Changes to Figure 48 and Figure 51 ............................................ 18
Changes to Figure 54 and Figure 57 ............................................ 19
Changes to Figure 60 and Figure 63 ............................................ 20
Changes to Figure 66 and Figure 69 ............................................ 21
Changes to Figure 72 ...................................................................... 22
Changes to Ordering Guide .......................................................... 25
4/09—Revision 0: Initial Version
Data Sheet ADP1612/ADP1613
Rev. D | Page 3 of 28
SPECIFICATIONS
VIN = 3.6 V, unless otherwise noted. Minimum and maximum values are guaranteed for TJ = −40°C to +125°C. Typical values specified
are at TJ = 25°C. All limits at temperature extremes are guaranteed by correlation and characterization using standard statistical quality
control (SQC), unless otherwise noted.
Table 1.
Parameter Symbol Conditions Min Typ Max Unit
SUPPLY
Input Voltage VIN ADP1612 1.8 5.5 V
ADP1613 2.5 5.5 V
Quiescent Current
Nonswitching State IQ VFB = 1.5 V, FREQ = VIN 900 1350 µA
FB
700
1300
µA
Shutdown IQSHDN VEN = 0 V 0.01 2 µA
Switching State1 IQSW FREQ = VIN, no load 4 5.8 mA
FREQ = GND, no load 2.2 4 mA
Enable Pin Bias Current IEN VEN = 3.6 V 3.3 7 µA
OUTPUT
Output Voltage VOUT VIN 20 V
Load Regulation ILOAD = 10 mA to 150 mA, VIN = 3.3 V, VOUT = 12 V 0.1 mV/mA
REFERENCE
Feedback Voltage VFB 1.215 1.235 1.255 V
Line Regulation ADP1612, VIN = 1.8 V to 5.5 V; ADP1613, VIN = 2.5 V to 5.5 V 0.07 0.24 %/V
ERROR AMPLIFIER
Transconductance GMEA ΔI = 4 µA 80 µA/V
Voltage Gain AV 60 dB
FB Pin Bias Current VFB = 1.3 V 1 50 nA
SWITCH
SW On Resistance RDSON ISW = 1.0 A 130 300 mΩ
SW Leakage Current VSW = 20 V 0.01 10 µA
Peak Current Limit2 ICL ADP1612, duty cycle = 70% 0.9 1.4 1.9 A
ADP1613, duty cycle = 70% 1.3 2.0 2.5 A
OSCILLATOR
Oscillator Frequency fSW FREQ = GND 500 650 720 kHz
FREQ = VIN 1.1 1.3 1.4 MHz
Maximum Duty Cycle DMAX COMP = open, VFB = 1 V, FREQ = VIN 88 90 %
FREQ Pin Current IFREQ FREQ = 3.6 V 5 8 μA
EN/FREQ LOGIC THRESHOLD ADP1612, VIN = 1.8 V to 5.5 V; ADP1613, VIN = 2.5 V to 5.5 V
Input Voltage Low VIL 0.3 V
Input Voltage High VIH 1.6 V
SOFT START
SS Charging Current ISS VSS = 0 V 3.4 5 6.2 µA
SS Voltage VSS VFB = 1.3 V 1.2 V
UNDERVOLTAGE LOCKOUT (UVLO)
Undervoltage Lockout Threshold ADP1612, VIN rising 1.70 V
IN
1.62
V
ADP1613, VIN rising 2.25 V
ADP1613, VIN falling 2.16 V
THERMAL SHUTDOWN
Thermal Shutdown Threshold 150 °C
Thermal Shutdown Hysteresis 20 °C
1 This parameter specifies the average current while switching internally and with SW (Pin 5) floating.
2 Current limit is a function of duty cycle. See the Typical Performance Characteristics section for typical values over operating ranges.
ADP1612/ADP1613 Data Sheet
Rev. D | Page 4 of 28
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter Rating
VIN, EN, FB to GND −0.3 V to +6 V
FREQ to GND −0.3 V to VIN + 0.3 V
COMP to GND 1.0 V to 1.6 V
SS to GND −0.3 V to +1.3 V
SW to GND 21 V
Operating Junction Temperature Range −40°C to +125°C
Storage Temperature Range −65°C to +150°C
Soldering Conditions
JEDEC J-STD-020
ESD (Electrostatic Discharge)
Human Body Model ±5 kV
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Absolute maximum ratings apply individually only, not in
combination.
THERMAL RESISTANCE
Junction-to-ambient thermal resistance (θJA) of the package is
specified for the worst-case conditions, that is, a device soldered
in a circuit board for surface-mount packages. The junction-to-
ambient thermal resistance is highly dependent on the application
and board layout. In applications where high maximum power
dissipation exists, attention to thermal board design is required.
The value of θJA may vary, depending on PCB material, layout,
and environmental conditions.
Table 3.
Package Type θJA θJC Unit
8-Lead MSOP
2-Layer Board1 206.9 44.22 °C/W
4-Layer Board1 162.2 44.22 °C/W
1 Thermal numbers per JEDEC standard JESD 51-7.
BOUNDARY CONDITION
Modeled under natural convection cooling at 25°C ambient
temperature, JESD 51-7, and 1 W power input with 2- and
4-layer boards.
ESD CAUTION
Data Sheet ADP1612/ADP1613
Rev. D | Page 5 of 28
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
COMP1
FB 2
EN 3
GND 4
SS
8
FREQ
7
VIN
6
SW
5
06772-002
ADP1612/
ADP1613
TOP VIEW
(Not t o Scale)
Figure 3. Pin Configuration
Table 4. Pin Function Descriptions
Pin No. Mnemonic Description
1 COMP Compensation Input. Connect a series resistor-capacitor network from COMP to GND to compensate the regulator.
2 FB Output Voltage Feedback Input. Connect a resistive voltage divider from the output voltage to FB to set the
regulator output voltage.
3 EN Enable Input. Drive EN low to shut down the regulator; drive EN high to turn on the regulator.
4 GND Ground.
5 SW Switching Output. Connect the power inductor from the input voltage to SW and connect the external rectifier
from SW to the output voltage to complete the step-up converter.
6 VIN Main Power Supply Input. VIN powers the ADP1612/ADP1613 internal circuitry. Connect VIN to the input source
voltage. Bypass VIN to GND with a 10 µF or greater capacitor as close to the ADP1612/ADP1613 as possible.
7 FREQ
Frequency Setting Input. FREQ controls the switching frequency. Connect FREQ to GND to program the oscillator
to 650 kHz, or connect FREQ to VIN to program it to 1.3 MHz. If FREQ is left floating, the part defaults to 650 kHz.
8 SS Soft Start Timing Capacitor Input. A capacitor connected from SS to GND brings up the output slowly at power-
up and reduces inrush current.
ADP1612/ADP1613 Data Sheet
Rev. D | Page 6 of 28
TYPICAL PERFORMANCE CHARACTERISTICS
VEN = VIN and TA = 25°C, unless otherwise noted.
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-012
V
IN
= 3.3V
f
SW
= 650kHz
T
A
= 25° C
V
OUT
= 5V
V
OUT
= 12V
V
OUT
= 15V
ADP1612
Figure 4. ADP1612 Efficiency vs. Load Current, VIN = 3.3 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-026
V
IN
= 3.3V
f
SW
= 1.3M Hz
T
A
= 25° C
V
OUT
= 5V
V
OUT
= 12V
V
OUT
= 15V
ADP1612
Figure 5. ADP1612 Efficiency vs. Load Current, VIN = 3.3 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-027
V
IN
= 5V
f
SW
= 650kHz
T
A
= 25° C
V
OUT
= 12V
V
OUT
= 15V
ADP1612
Figure 6. ADP1612 Efficiency vs. Load Current, VIN = 5 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-028
VIN = 5V
fSW = 1.3MHz
TA = 25° C
VOUT = 12V
VOUT = 15V
ADP1612
Figure 7. ADP1612 Efficiency vs. Load Current, VIN = 5 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-029
VIN = 5V
fSW = 650kHz
TA = 25° C
VOUT = 12V
VOUT = 15V
VOUT = 20V
ADP1613
Figure 8. ADP1613 Efficiency vs. Load Current, VIN = 5 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-030
VIN = 5V
fSW = 1.3MHz
TA = 25° C
VOUT = 12V
VOUT = 15V
VOUT = 20V
ADP1613
Figure 9. ADP1613 Efficiency vs. Load Current, VIN = 5 V, fSW = 1.3 MHz
Data Sheet ADP1612/ADP1613
Rev. D | Page 7 of 28
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.8 2.3 2.8 3.3 3.8 4.3 4.8
INPUT VOLTAGE (V)
CURRENT LIM IT ( A)
06772-010
ADP1612
T
A
= +25°C
T
A
= +85°C
T
A
= –40° C
Figure 10. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 5 V
2.0
1.8
1.6
1.4
1.2
1.0
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
CURRENT LIM IT ( A)
06772-013
ADP1612
T
A
= +25°C
T
A
= +85°C
T
A
= –40° C
Figure 11. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 8 V
1.6
1.4
1.2
1.0
0.8
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
CURRENT LIM IT ( A)
06772-011
ADP1612
T
A
= +25°C
T
A
= –40° C
T
A
= +85°C
Figure 12. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 15 V
3.4
3.2
3.0
2.8
2.6
2.4
2.2
2.0
2.5 3.0 3.5 4.0 4.5
INPUT VOLTAGE (V)
CURRENT LIM IT ( A)
06772-031
ADP1613
TA = +25°C
TA = +85°C
TA = –40° C
Figure 13. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 5 V
2.6
2.4
2.2
2.0
1.8
2.5 3.0 3.5 4.0
INPUT VOLTAGE (V)
4.5 5.0 5.5
CURRENT LIM IT ( A)
06772-032
ADP1613
T
A
= +25°C
T
A
= +85°C
T
A
= –40° C
Figure 14. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 8 V
2.6
2.4
2.2
2.0
1.8
1.6
1.4
2.5 3.0 3.5 4.0
INPUT VOLTAGE (V)
4.5 5.0 5.5
CURRENT LIM IT ( A)
06772-033
ADP1613
T
A
= +85°C
T
A
= +25°C
T
A
= –40° C
Figure 15. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 15 V
ADP1612/ADP1613 Data Sheet
Rev. D | Page 8 of 28
800
750
700
650
600
550
500
450
400
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
QUIESCE NT CURRENT ( µ A)
06772-014
T
A
= +25°C
T
A
= +125°C
T
A
= –40° C
ADP1612/ADP1613
Figure 16. ADP1612/ADP1613 Quiescent Current vs. Input Voltage,
Nonswitching, fSW = 650 kHz
800
750
700
650
600
550
500
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
QUIESCE NT CURRENT ( µ A)
06772-017
T
A
= +25°C
T
A
= +125°C
T
A
= –40° C
ADP1612/ADP1613
Figure 17. ADP1612/ADP1613 Quiescent Current vs. Input Voltage,
Nonswitching, fSW = 1.3 MHz
3.5
3.0
2.5
2.0
1.5
1.0
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
QUIESCE NT CURRENT ( mA)
06772-015
T
A
= +25°C
T
A
= –40° C
T
A
= +125°C
ADP1612/ADP1613
Figure 18. ADP1612/ADP1613 Quiescent Current vs. Input Voltage,
Switching, fSW = 650 kHz
6
5
4
3
2
1
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
QUIESCE NT CURRENT ( mA)
06772-018
T
A
= +125°C
T
A
= +25°C
T
A
= –40° C
ADP1612/ADP1613
Figure 19. ADP1612/ADP1613 Quiescent Current vs. Input Voltage,
Switching, fSW = 1.3 MHz
250
230
210
190
170
150
130
110
90
70
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
R
DSON
(mΩ)
06772-016
I
SW
= 1A
T
A
= –40° C
T
A
= +30°C T
A
= +85°C
ADP1612/ADP1613
Figure 20. ADP1612/ADP1613 On Resistance vs. Input Voltage
250
230
210
190
170
150
130
110
90
70
–40 –15 10 35 60 85
TEMPERATURE (°C)
R
DSON
(mΩ)
06772-019
V
IN
= 5.5V
I
SW
= 1A
V
IN
= 1.8V
V
IN
= 2.5V
V
IN
= 3.6V
ADP1612/ADP1613
Figure 21. ADP1612/ADP1613 On Resistance vs. Temperature
Data Sheet ADP1612/ADP1613
Rev. D | Page 9 of 28
660
650
640
630
620
610
600
590
580
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
FRE QUENCY ( kHz )
06772-020
T
A
= +25°C
T
A
= +125°C
T
A
= –40° C
ADP1612/ADP1613
Figure 22. ADP1612/ADP1613 Frequency vs. Input Voltage, fSW = 650 kHz
1.32
1.30
1.28
1.26
1.24
1.22
1.20
1.18
1.16
1.14
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
FREQUENCY (MHz)
06772-023
T
A
= +25°C
T
A
= +125°C
T
A
= –40° C
ADP1612/ADP1613
Figure 23. ADP1612/ADP1613 Frequency vs. Input Voltage, fSW = 1.3 MHz
7
6
5
4
3
2
1
000.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5
EN PIN VOLTAGE (V)
EN PIN CURRENT ( µ A)
06772-021
T
A
= +25°C
T
A
= +125°C
T
A
= –40° C
ADP1612/ADP1613
Figure 24. ADP1612/ADP1613 EN Pin Current vs. EN Pin Voltage
5.1
5.0
4.9
4.8
4.7
4.6
4.5
–40 –10 20 50 80 110
TEMPERATURE (°C)
SS P IN CURRENT ( µ A)
06772-024
V
IN
= 1.8V
V
IN
= 3.6V
V
IN
= 5.5V
ADP1612/ADP1613
Figure 25. ADP1612/ADP1613 SS Pin Current vs. Temperature
92.8
92.6
92.4
92.2
92.0
91.8
91.6
91.4
91.2
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
MAXIMUM DUTY CYCLE (%)
06772-022
T
A
= +25°C
T
A
= +125°C
T
A
= –40° C
ADP1612/ADP1613
Figure 26. ADP1612/ADP1613 Maximum Duty Cycle vs. Input Voltage,
fSW = 650 kHz
93.4
93.2
93.0
92.8
92.6
92.4
92.2
92.0
91.8
91.6
1.8 2.3 2.8 3.3 3.8 4.3 4.8 5.3
INPUT VOLTAGE (V)
MAXIMUM DUTY CYCLE (%)
06772-025
TA = +25°C
TA = +125°C
TA = –40° C
ADP1612/ADP1613
Figure 27. ADP1612/ADP1613 Maximum Duty Cycle vs. Input Voltage,
fSW = 1.3 MHz
ADP1612/ADP1613 Data Sheet
Rev. D | Page 10 of 28
06772-034
T
TIME ( 400ns/DIV)
V
IN
= 5V
V
OUT
= 12V
I
LOAD
= 20mA
L = 6.8µH
f
SW
= 1.3M Hz
C
OUT
= 10µF
OUTPUT VOLTAGE (5V/DIV)
INDUCTOR CURRE NT
(200mA/DIV)
SWITCH VOLTAGE (10V/DIV)
Figure 28. ADP1612/ADP1613 Switching Waveform in Discontinuous
Conduction Mode
06772-035
T
TIME ( 400ns/DIV)
V
IN
= 5V
V
OUT
= 12V
I
LOAD
= 200mA
L = 6.8µH
f
SW
= 1.3M Hz
C
OUT
= 10µF
OUTPUT VOLTAGE (5V/DIV)
INDUCTOR CURRE NT
(500mA/DIV)
SWITCH VOLTAGE (10V/DIV)
Figure 29. ADP1612/ADP1613 Switching Waveform in Continuous
Conduction Mode
06772-036
T
TIME ( 20ms/DIV )
V
IN
= 5V
V
OUT
= 12V
I
LOAD
= 250mA
L = 6.8µH
f
SW
= 1.3M Hz
OUTPUT VOLTAGE (5V/DIV)
INDUCTOR CURRENT (2A/DIV )
SW ITCH V OLTAGE ( 10V /DIV )
EN PIN VOLTAGE (5V/DIV)
Figure 30. ADP1612/ADP1613 Start-Up from VIN, CSS =33 nF
06772-037
T
TIME ( 20ms/DIV )
V
IN
= 5V
V
OUT
= 12V
I
LOAD
= 250mA
L = 6.8µH
f
SW
= 1.3M Hz
OUTPUT VOLTAGE (5V/DIV)
SW ITCH V OLTAGE ( 10V /DIV )
EN PIN VOLTAGE (5V/DIV)
INDUCTOR CURRENT (2A/DIV )
Figure 31. ADP1612/ADP1613 Start-Up from VIN, CSS =100 nF
06772-038
T
TIME ( 400µ s/DIV )
V
IN
= 5V
V
OUT
= 12V
I
LOAD
= 250mA
L = 6.8µH
f
SW
= 1.3M Hz
OUTPUT VOLTAGE (5V/DIV)
INDUCTOR CURRENT (500mA/DIV )
SW ITCH V OLTAGE ( 10V /DIV )
EN PIN VOLTAGE (5V/DIV)
Figure 32. ADP1612/ADP1613 Start-Up from Shutdown, CSS = 33 nF
06772-039
T
TIME ( 400µ s/DIV )
VIN = 5V
VOUT = 12V
ILOAD = 250mA
L = 6.8µH
fSW = 1.3MHz
OUTPUT VOLTAGE (5V/DIV)
INDUCTOR CURRENT (500mA/DIV )
SW ITCH V OLTAGE ( 10V /DIV )
EN PIN VOLTAGE (5V/DIV)
Figure 33. ADP1612/ADP1613 Start-Up from Shutdown, CSS = 100 nF
Data Sheet ADP1612/ADP1613
Rev. D | Page 11 of 28
THEORY OF OPERATION
FREQ
SW
PWM
COMPARATOR
UVLO
COMPARATOR
TSD
COMPARATOR
OSCILLATOR
S
RQ
D
COMPARATOR
D
REF
+
+
7
VIN
CURRENT
SENSING
5µA
DRIVER
BAND GAP
N1
BG
RESET
1.1MΩ
AGND
V
IN
UVLO
REF
T
SENSE
T
REF
ERROR
AMPLIFIER
V
BG
SOFT
START
2
1
5µA
V
SS
R
COMP
C
COMP
COMP
SS
FB
C
SS
R1
R2
C
IN
V
OUT
6
V
IN
L1
D1
AV
OUT
C
OUT
5
34
GND
AGND
>1.6V
EN
ADP1612/AD1613
06772-003
8
V
IN
<0.3V
>1.6V
<0.3V
Figure 34. Block Diagram with Step-Up Regulator Application Circuit
The ADP1612/ADP1613 current-mode step-up switching
converters boost a 1.8 V to 5.5 V input voltage to an output
voltage as high as 20 V. The internal switch allows a high
output current, and the high 650 kHz/1.3 MHz switching
frequency allows for the use of tiny external components.
The switch current is monitored on a pulse-by-pulse basis to
limit it to 1.4 A typical (ADP1612) or 2.0 A typical (ADP1613).
CURRENT-MODE PWM OPERATION
The ADP1612/ADP1613 utilize a current-mode PWM control
scheme to regulate the output voltage over all load conditions.
The output voltage is monitored at FB through a resistive voltage
divider. The voltage at FB is compared to the internal 1.235 V
reference by the internal transconductance error amplifier to
create an error voltage at COMP. The switch current is internally
measured and added to the stabilizing ramp. The resulting sum
is compared to the error voltage at COMP to control the PWM
modulator. This current-mode regulation system allows fast
transient response, while maintaining a stable output voltage.
By selecting the proper resistor-capacitor network from COMP
to GND, the regulator response is optimized for a wide range of
input voltages, output voltages, and load conditions.
FREQUENCY SELECTION
The frequency of the ADP1612/ADP1613 is pin-selectable
to operate at either 650 kHz to optimize the regulator for high
efficiency or at 1.3 MHz for use with small external components.
If FREQ is left floating, the part defaults to 650 kHz. Connect
FREQ to GND for 650 kHz operation or connect FREQ to VIN
for 1.3 MHz operation. When connected to VIN for 1.3 MHz
operation, an additional 5 μA, typical, of quiescent current is
active. This current is turned off when the part is shutdown.
SOFT START
To prevent input inrush current to the converter when the part is
enabled, connect a capacitor from SS to GND to set the soft start
period. Once the ADP1612/ADP1613 are turned on, SS sources
5 µA, typical, to the soft start capacitor (CSS) until it reaches
1.2 V at startup. As the soft start capacitor charges, it limits the
peak current allowed by the part. By slowly charging the soft
start capacitor, the input current ramps slowly to prevent it
from overshooting excessively at startup. When the ADP1612/
ADP1613 are in shutdown mode (EN ≤ 0.3 V), a thermal shut-
down event occurs, or the input voltage is below the falling
undervoltage lockout voltage, SS is internally shorted to GND
to discharge the soft start capacitor.
ADP1612/ADP1613 Data Sheet
Rev. D | Page 12 of 28
THERMAL SHUTDOWN (TSD)
The ADP1612/ADP1613 include TSD protection. If the die
temperature exceeds 150°C (typical), TSD turns off the NMOS
power device, significantly reducing power dissipation in the
device and preventing output voltage regulation. The NMOS
power device remains off until the die temperature reduces to
130°C (typical). The soft start capacitor is discharged during
TSD to ensure low output voltage overshoot and inrush
currents when regulation resumes.
UNDERVOLTAGE LOCKOUT (UVLO)
If the input voltage is below the UVLO threshold, the ADP1612/
ADP1613 automatically turn off the power switch and place
the part into a low power consumption mode. This prevents
potentially erratic operation at low input voltages and prevents
the power device from turning on when the control circuitry
cannot operate it. The UVLO levels have ~100 mV of hysteresis
to ensure glitch free startup.
ENABLE/SHUTDOWN CONTROL
The EN input turns the ADP1612/ADP1613 regulator on or
off. Drive EN low to turn off the regulator and reduce the
input current to 0.01 µA, typical. Drive EN high to turn on
the regulator.
When the step-up dc-to-dc switching converter is in shutdown
mode (EN ≤ 0.3 V), there is a dc path from the input to the output
through the inductor and output rectifier. This causes the output
voltage to remain slightly below the input voltage by the forward
voltage of the rectifier, preventing the output voltage from dropping
to ground when the regulator is shutdown. Figure 37 provides a
circuit modification to disconnect the output voltage from the
input voltage at shutdown.
Regardless of the state of the EN pin, when a voltage is applied to
VIN of the ADP1612/ADP1613, a large current spike occurs due
to the nonisolated path through the inductor and diode between
VIN and VOUT. The high current is a result of the output capacitor
charging. The peak value is dependent on the inductor, output
capacitor, and any load active on the output of the regulator.
Data Sheet ADP1612/ADP1613
Rev. D | Page 13 of 28
APPLICATIONS INFORMATION
ADIsimPower DESIGN TOOL
The ADP1612/ADP1613 are supported by ADIsimPower design
tool set. ADIsimPower is a collection of tools that produce
complete power designs optimized for a specific design goal.
The tools enable the user to generate a full schematic, bill of
materials, and calculate performance in minutes. ADIsimPower
can optimize designs for cost, area, efficiency, and parts count
while taking into consideration the operating conditions and
limitations of the IC and all real external components. For more
information about ADIsimPower design tools, refer to
www.analog.com/ADIsimPower. The tool set is available from
this website, and users can also request an unpopulated board
through the tool.
SETTING THE OUTPUT VOLTAGE
The ADP1612/ADP1613 feature an adjustable output voltage
range of VIN to 20 V. The output voltage is set by the resistor
voltage divider, R1 and R2, (see Figure 34) from the output
voltage (VOUT) to the 1.235 V feedback input at FB. Use the
following equation to determine the output voltage:
VOUT = 1.235 × (1 + R1/R2) (1)
Choose R1 based on the following equation:
−
×= 235.1
235.1
OUT
V
R2R1
(2)
INDUCTOR SELECTION
The inductor is an essential part of the step-up switching
converter. It stores energy during the on time of the power
switch, and transfers that energy to the output through the
output rectifier during the off time. To balance the tradeoffs
between small inductor current ripple and efficiency, induc-
tance values in the range of 4.7 µH to 22 µH are recommended.
In general, lower inductance values have higher saturation
current and lower series resistance for a given physical size.
However, lower inductance results in a higher peak current
that can lead to reduced efficiency and greater input and/or
output ripple and noise. A peak-to-peak inductor ripple current
close to 30% of the maximum dc input current typically yields
an optimal compromise.
For determining the inductor ripple current in continuous
operation, the input (VIN) and output (VOUT) voltages determine
the switch duty cycle (D) by the following equation:
OUT
IN
OUT
V
VV
D−
=
(3)
Using the duty cycle and switching frequency, fSW, determine
the on time by the following equation:
SW
ON
f
D
t=
(4)
The inductor ripple current (∆IL) in steady state is calculated by
L
tV
ION
IN
L
×
=∆
(5)
Solve for the inductance value (L) by the following equation:
L
ON
IN
I
tV
L∆
×
=
(6)
Ensure that the peak inductor current (the maximum input
current plus half the inductor ripple current) is below the rated
saturation current of the inductor. Likewise, make sure that the
maximum rated rms current of the inductor is greater than the
maximum dc input current to the regulator.
For CCM duty cycles greater than 50% that occur with input
voltages less than one-half the output voltage, slope compen-
sation is required to maintain stability of the current-mode
regulator. For stable current-mode operation, ensure that the
selected inductance is equal to or greater than the minimum
calculated inductance, LMIN, for the application parameters in
the following equation:
SW
IN
OUT
MIN f
VV
LL ×
×−
=> 7.2
)2(
(7)
Inductors smaller than the 4.7 µH to 22 µH recommended
range can be used as long as Equation 7 is satisfied for the given
application. For input/output combinations that approach the
90% maximum duty cycle, doubling the inductor is recom-
mended to ensure stable operation. Table 5 suggests a series
of inductors for use with the ADP1612/ADP1613.
Table 5. Suggested Inductors
Manufacturer Part Series
Dimensions
L × W × H (mm)
Sumida CMD4D11 5.8 × 4.4 × 1.2
CDRH4D28CNP 5.1 × 5.1 × 3.0
CDRH5D18NP 6.0 × 6.0 × 2.0
CDRH6D26HPNP 7.0 × 7.0 × 2.8
Coilcraft DO3308P 12.95 × 9.4 × 3.0
DO3316P 12.95 × 9.4 × 5.21
Toko D52LC 5.2 × 5.2 × 2.0
D62LCB
6.2 × 6.3 × 2.0
D63LCB 6.2 × 6.3 × 3.5
Würth
Elektronik
WE-TPC
Assorted
WE-PD, PD2, PD3, PD4 Assorted
ADP1612/ADP1613 Data Sheet
Rev. D | Page 14 of 28
CHOOSING THE INPUT AND OUTPUT CAPACITORS
The ADP1612/ADP1613 require input and output bypass capa-
citors to supply transient currents while maintaining constant
input and output voltages. Use a low equivalent series resistance
(ESR), 10 µF or greater input capacitor to prevent noise at the
ADP1612/ADP1613 input. Place the capacitor between VIN
and GND as close to the ADP1612/ADP1613 as possible.
Ceramic capacitors are preferred because of their low ESR
characteristics. Alternatively, use a high value, medium ESR
capacitor in parallel with a 0.1 µF low ESR capacitor as close
to the ADP1612/ADP1613 as possible.
The output capacitor maintains the output voltage and supplies
current to the load while the ADP1612/ADP1613 switch is on.
The value and characteristics of the output capacitor greatly
affect the output voltage ripple and stability of the regulator. A
low ESR ceramic dielectric capacitor is preferred. The output
voltage ripple (∆VOUT) is calculated as follows:
OUT
ONOUT
OUT
C
OUT
C
tI
C
Q
V×
==∆
(8)
where:
QC is the charge removed from the capacitor.
tON is the on time of the switch.
COUT is the output capacitance.
IOUT is the output load current.
SW
ON
f
D
t=
(9)
and
OUT
IN
OUT
V
VV
D−
=
(10)
Choose the output capacitor based on the following equation:
OUTOUTSW
INOUTOUT
OUT
VVf
VVI
C∆××
−×
≥)(
(11)
Multilayer ceramic capacitors are recommended for this
application.
DIODE SELECTION
The output rectifier conducts the inductor current to the output
capacitor and load while the switch is off. For high efficiency,
minimize the forward voltage drop of the diode. For this reason,
Schottky rectifiers are recommended. However, for high voltage,
high temperature applications, where the Schottky rectifier
reverse leakage current becomes significant and can degrade
efficiency, use an ultrafast junction diode.
Ensure that the diode is rated to handle the average output
load current. Many diode manufacturers derate the current
capability of the diode as a function of the duty cycle. Verify
that the output diode is rated to handle the average output
load current with the minimum duty cycle. The minimum
duty cycle of the ADP1612/ADP1613 is
OUT
MAXIN
OUT
MIN
V
VV
D
)(
−
=
(12)
where VIN(MAX) is the maximum input voltage.
The following are suggested Schottky diode manufacturers:
• ON Semiconductor
• Diodes, Inc.
LOOP COMPENSATION
The ADP1612/ADP1613 use external components to
compensate the regulator loop, allowing optimization of
the loop dynamics for a given application.
The step-up converter produces an undesirable right-half plane
zero in the regulation feedback loop. This requires compensating
the regulator such that the crossover frequency occurs well
below the frequency of the right-half plane zero. The right-
half plane zero is determined by the following equation:
L
R
V
V
RHPF
LOAD
OUT
IN
Z
×π
×
=2
)(
2
(13)
where:
FZ(RHP) is the right-half plane zero.
RLOAD is the equivalent load resistance or the output voltage
divided by the load current.
To stabilize the regulator, ensure that the regulator crossover
frequency is less than or equal to one-fifth of the right-half
plane zero.
The regulator loop gain is
OUTCSCOMPOUTMEA
OUT
IN
OUT
FB
VL ZGZRG
V
V
V
V
A×××××= ||
(14)
where:
AVL is the loop gain.
VFB is the feedback regulation voltage, 1.235 V.
VOUT is the regulated output voltage.
VIN is the input voltage.
GMEA is the error amplifier transconductance gain.
ROUT is 125 MΩ.
ZCOMP is the impedance of the series RC network from COMP
to GND.
GCS is the current sense transconductance gain (the inductor
current divided by the voltage at COMP), which is internally
set by the ADP1612/ADP1613.
ZOUT is the impedance of the load in parallel with the output
capacitor.
Data Sheet ADP1612/ADP1613
Rev. D | Page 15 of 28
To determine the crossover frequency, it is important to note
that, at that frequency, the compensation impedance (ZCOMP)
is dominated by a resistor, and the output impedance (ZOUT) is
dominated by the impedance of an output capacitor. Therefore,
when solving for the crossover frequency, the equation (by
definition of the crossover frequency) is simplified to
1
2
1=
××π
×××××=
OUT
C
CSCOMPMEA
OUT
IN
OUT
FB
VL
Cf
GRG
V
V
V
V
A
(15)
where:
fC is the crossover frequency.
RCOMP is the compensation resistor.
Solve for RCOMP,
CSMEA
INFB
OUTOUT
C
COMP GGVV
VCf
R×××
×××π
=
2
)(2
(16)
where:
VFB = 1.235 V.
GMEA = 80 µA/V.
GCS = 13.4 A/V.
IN
OUTOUT
C
COMP V
VCf
R
2
)(4746 ×××
=
(17)
Once the compensation resistor is known, set the zero formed
by the compensation capacitor and resistor to one-fourth of the
crossover frequency, or
COMPC
COMP Rf
C××π
=2
(18)
where CCOMP is the compensation capacitor.
R
COMP
C
COMP
C2
1
COMP
g
m
ERROR
AMPLIFIER
2
FB
V
BG
06772-004
Figure 35. Compensation Components
The capacitor, C2, is chosen to cancel the zero introduced by
output capacitance, ESR.
Solve for C2 as follows:
COMP
OUT
R
CESR
C2 ×
=
(19)
For low ESR output capacitance such as with a ceramic
capacitor, C2 is optional. For optimal transient performance,
RCOMP and CCOMP might need to be adjusted by observing the
load transient response of the ADP1612/ADP1613. For most
applications, the compensation resistor should be within the
range of 4.7 kΩ to 100 kΩ and the compensation capacitor
should be within the range of 100 pF to 3.3 n F.
SOFT START CAPACITOR
Upon startup (EN ≥ 1.6 V), the voltage at SS ramps up slowly
by charging the soft start capacitor (CSS) with an internal 5 µA
current source (ISS). As the soft start capacitor charges, it limits
the peak current allowed by the part to prevent excessive over-
shoot at startup. The necessary soft start capacitor, CSS, for a
specific overshoot and start-up time can be calculated for the
maximum load condition when the part is at current limit by:
SS
SSSS
V
t
IC ∆
=
(20)
where:
ISS = 5 μA (typical).
VSS = 1.2 V.
Δt = startup time, at current limit.
If the applied load does not place the part at current limit, the
necessary CSS will be smaller. A 33 nF soft start capacitor results
in negligible input current overshoot at start up, and therefore is
suitable for most applications. However, if an unusually large
output capacitor is used, a longer soft start period is required
to prevent input inrush current.
Conversely, if fast startup is a requirement, the soft start
capacitor can be reduced or removed, allowing the
ADP1612/ADP1613 to start quickly, but allowing greater
peak switch current.
ADP1612/ADP1613 Data Sheet
Rev. D | Page 16 of 28
TYPICAL APPLICATION CIRCUITS
Both the ADP1612 and ADP1613 can be used in the application
circuits in this section.
The ADP1612 is geared toward applications requiring input
voltages as low as 1.8 V, where the ADP1613 is more suited for
applications needing the output power capabilities of a 2.0 A
switch. The primary differences are shown in Table 6.
Table 6. ADP1612/ADP1613 Differences
Parameter ADP1612 ADP1613
Current Limit 1.4 A 2.0 A
Input Voltage Range 1.8 V to 5.5 V 2.5 V to 5.5 V
The Step-Up Regulator Circuit Examples section recommends
component values for several common input, output, and load
conditions. The equations in the Applications Information
section can be used to select components for alternate
configurations.
STEP-UP REGULATOR
The circuit in Figure 36 shows the ADP1612/ADP1613 in a
basic step-up configuration.
ADP1612/
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
1.3MHz
650kHz
(DEFAULT)
V
OUT
V
IN
L1
C
IN
C
SS
C
OUT
C
COMP
R
COMP
R1
R2
D1
06772-005
Figure 36. Step-Up Regulator
The modified step-up circuit in Figure 37 incorporates true
shutdown capability advantageous for battery-powered applica-
tions requiring low standby current. Driving the EN pin below
0.3 V shuts down the ADP1612/ADP1613 and completely
disconnects the input from the output.
ADP1612/
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
1.3MHz
650kHz
(DEFAULT)
V
OUT
L1
C
IN
C
SS
C
OUT
C
COMP
R
COMP
R1
R2
D1
06772-006
V
IN
R3
10kΩ
NTGD1100L
Q1A
B
Q1
ON
OFF
Figure 37. Step-Up Regulator with True Shutdown
STEP-UP REGULATOR CIRCUIT EXAMPLES
ADP1612 Step-Up Regulator
06772-040
ADP1612
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 5VV
IN
= 1.8V TO 4.2V
L1
4.7µH
C
SS
33nF
C
OUT
10µF
C
COMP
3300pF
R
COMP
6.8kΩ
R1
30kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-472M L
D1: MBRA340T3G
R1: RC0805F R- 0730KL
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-076K8L
C
COMP
: ECJ- 2V B1H332K
C
IN
: G RM 21BR61C106KE 15L
C
OUT: G RM 32DR71E 106KA12L
CSS: E CJ- 2V B1H333K
Figure 38. ADP1612 Step-Up Regulator Configuration
VOUT = 5 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k 10k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-041
V
OUT
= 5V
fSW
= 650kHz
T
A
= 25° C
V
IN
= 1.8V
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
ADP1612
Figure 39. ADP1612 Efficiency vs. Load Current
VOUT = 5 V, fSW = 650 kHz
06772-042
V
OUT
= 5V
f
SW
= 650kHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (50mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 40. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 5 V, fSW = 650 kHz
Data Sheet ADP1612/ADP1613
Rev. D | Page 17 of 28
06772-043
ADP1612
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 5VV
IN
= 1.8V TO 4.2V
L1
4.7µH
C
SS
33nF
C
OUT
10µF
C
COMP
1200pF
R
COMP
12kΩ
R1
30kΩ
R2
10kΩ
C
IN
10µF
L1: DO3316P-472M L
D1: MBRA340T3G
R1: RC0805F R- 0730KL
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0712KL
C
COMP
: ECJ- 2V B1H122K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
D1
3A, 40V
Figure 41. ADP1612 Step-Up Regulator Configuration
VOUT = 5 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30110 100 1k 10k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-044
V
OUT
= 5V
f
SW
= 1.3M Hz
T
A
= 25° C
V
IN
= 1.8V
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
ADP1612
Figure 42. ADP1612 Efficiency vs. Load Current
VOUT = 5 V, fSW = 1.3 MHz
06772-045
V
OUT
= 5V
f
SW
= 1.3M Hz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (50mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 43. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 5 V, fSW = 1.3 MHz
06772-046
ADP1612
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 12VV
IN
= 2.7V TO 5V
L1
10µH
C
SS
33nF
C
OUT
10µF
C
COMP
1800pF
R
COMP
22kΩ
R1
86.6kΩ
R2
10kΩ
D1
2A, 20V
C
IN
10µF
L1: DO3316P-103M L
D1: DF LS220L - 7
R1: ERJ- 6E NF8662V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0722KL
C
COMP
: ECJ- 2V B1H182K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 44. ADP1612 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 650 kHz
100
90
80
70
60
50
40110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-047
V
OUT
= 12V
fSW
= 650kHz
T
A
= 25° C
ADP1612
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
Figure 45. ADP1612 Efficiency vs. Load Current
VOUT = 12 V, fSW = 650 kHz
06772-048
V
OUT
= 12V
f
SW
= 650kHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (100mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 46. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 12 V, fSW = 650 kHz
ADP1612/ADP1613 Data Sheet
Rev. D | Page 18 of 28
06772-049
ADP1612
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 12VV
IN
= 2.7V TO 5V
L1
6.8µH
C
SS
33nF
C
OUT
10µF
C
COMP
680pF
R
COMP
18kΩ
R1
86.6kΩ
R2
10kΩ
D1
2A, 20V
C
IN
10µF
L1: DO3316P-682M L
D1: DF LS220L - 7
R1: ERJ- 6E NF8662V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0718KL
C
COMP
: CC0805KRX7R9BB681
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 47. ADP1612 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-050
V
OUT
= 12V
fSW
= 1.3M Hz
T
A
= 25° C
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
ADP1612
Figure 48. ADP1612 Efficiency vs. Load Current
VOUT = 12 V, fSW = 1.3 MHz
06772-051
V
OUT
= 12V
f
SW
= 1.3M Hz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (100mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 49. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 12 V, fSW = 1.3 MHz
06772-052
ADP1612
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 15VV
IN
= 2.7V TO 5V
L1
15µH
C
SS
33nF
C
OUT
10µF
C
COMP
1800pF
R
COMP
22kΩ
R1
110kΩ
R2
10kΩ
D1
2A, 20V
C
IN
10µF
L1: DO3316P-153M L
D1: DF LS220L - 7
R1: ERJ- 6E NF1103V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0722KL
C
COMP
: ECJ- 2V B1H182K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 50. ADP1612 Step-Up Regulator Configuration
VOUT = 15 V, fSW = 650 kHz
100
90
80
70
60
50
40110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-053
V
OUT
= 15V
fSW
= 650kHz
T
A
= 25° C
ADP1612
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
Figure 51. ADP1612 Efficiency vs. Load Current
VOUT = 15 V, fSW = 650 kHz
06772-054
V
OUT
= 15V
f
SW
= 650kHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 52. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT = 15 V, fSW = 650 kHz
Data Sheet ADP1612/ADP1613
Rev. D | Page 19 of 28
06772-055
ADP1612
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 15VV
IN
= 2.7V TO 5V
L1
10µH
C
SS
33nF
C
OUT
10µF
C
COMP
1800pF
R
COMP
10kΩ
R1
110kΩ
R2
10kΩ
D1
2A, 20V
C
IN
10µF
L1: DO3316P-103M L
D1: DF LS220L - 7
R1: ERJ- 6E NF1103V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0710KL
C
COMP
: ECJ- 2V B1H182K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 53. ADP1612 Step-Up Regulator Configuration
VOUT =15 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-056
V
OUT
= 15V
fSW
= 1.3M Hz
T
A
= 25° C
ADP1612
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
Figure 54. ADP1612 Efficiency vs. Load Current
VOUT =15 V, fSW = 1.3 MHz
06772-057
VOUT = 15V
fSW = 1.3MHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 55. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V)
VOUT =15 V, fSW = 1.3 MHz
ADP1613 Step-Up Regulator
06772-058
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 12VV
IN
= 2.7V TO 5V
L1
10µH
C
SS
33nF
C
OUT
10µF
C
COMP
2200pF
R
COMP
12kΩ
R1
86.6kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-103M L
D1: MBRA340T3G
R1: ERJ- 6E NF8662V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0712KL
C
COMP
: ECJ- 2V B1H222K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 56. ADP1613 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-059
V
OUT
= 12V
fSW
= 650kHz
T
A
= 25° C
ADP1613
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
Figure 57. ADP1613 Efficiency vs. Load Current
VOUT = 12 V, fSW = 650 kHz
06772-060
VOUT = 12V
fSW = 650kHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 58. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 12 V, fSW = 650 kHz
ADP1612/ADP1613 Data Sheet
Rev. D | Page 20 of 28
06772-061
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 12VV
IN
= 2.7V TO 5V
L1
6.8µH
C
SS
33nF
C
OUT
10µF
C
COMP
1000pF
R
COMP
10kΩ
R1
86.6kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-682M L
D1: MBRA340T3G
R1: ERJ- 6E NF8662V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0710KL
C
COMP
: ECJ- 2V B1H102K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 59. ADP1613 Step-Up Regulator Configuration
VOUT = 12 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-062
V
OUT
= 12V
fSW
= 1.3M Hz
T
A
= 25° C
ADP1613
V
IN
= 2.7V
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
Figure 60. ADP1613 Efficiency vs. Load Current
VOUT = 12 V, fSW = 1.3 MHz
06772-063
V
OUT
= 12V
f
SW
= 1.3M Hz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (100mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 61. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 12 V, fSW = 1.3 MHz
06772-064
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 15VV
IN
= 3.3V TO 5.5V
L1
15µH
C
SS
33nF
C
OUT
10µF
C
COMP
1800pF
R
COMP
10kΩ
R1
110kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-153M L
D1: MBRA340T3G
R1: ERJ- 6E NF1103V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0710KL
C
COMP
: ECJ- 2V B1H182K
C
IN
: G RM 21BR61C106KE 15L
COUT: G RM 32DR71E 106KA12L
CSS: E CJ- 2V B1H333K
Figure 62. ADP1613 Step-Up Regulator Configuration
VOUT = 15 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-065
V
OUT
= 15V
fSW
= 650kHz
T
A
= 25° C
ADP1613
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
V
IN
= 5.5V
Figure 63. ADP1613 Efficiency vs. Load Current
VOUT = 15 V, fSW = 650 kHz
06772-066
V
OUT
= 15V
f
SW
= 650kHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 64. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 15 V, fSW = 650 kHz
Data Sheet ADP1612/ADP1613
Rev. D | Page 21 of 28
06772-067
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 15VV
IN
= 3.3V TO 5.5V
L1
10µH
C
SS
33nF
C
OUT
10µF
C
COMP
1200pF
R
COMP
8.2kΩ
R1
110kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-103M L
D1: MBRA340T3G
R1: ERJ- 6E NF1103V
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-078K2L
C
COMP
: ECJ- 2V B1H122K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 65. ADP1613 Step-Up Regulator Configuration
VOUT = 15 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30
20110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-068
V
OUT
= 15V
fSW
= 1.3M Hz
T
A
= 25° C
ADP1613
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
V
IN
= 5.5V
Figure 66. ADP1613 Efficiency vs. Load Current
VOUT = 15 V, fSW = 1.3 MHz
06772-069
V
OUT
= 15V
f
SW
= 1.3M Hz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 67. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 15 V, fSW = 1.3 MHz
06772-070
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 20VV
IN
= 3.3V TO 5.5V
L1
15µH
C
SS
33nF
C
OUT
10µF
C
COMP
820pF
R
COMP
18kΩ
R1
150kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-153M L
D1: MBRA340T3G
R1: RC0805JR-07150KL
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-0718KL
C
COMP
: CC0805KRX7R9BB821
C
IN
: G RM 21BR61C106KE 15L
C
OUT: G RM 32DR71E 106KA12L
CSS: E CJ- 2V B1H333K
Figure 68. ADP1613 Step-Up Regulator Configuration
VOUT = 20 V, fSW = 650 kHz
100
90
80
70
60
50
40
30110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-071
V
OUT
= 20V
fSW
= 650kHz
T
A
= 25° C
ADP1613
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
V
IN
= 5.5V
Figure 69. ADP1613 Efficiency vs. Load Current
VOUT = 20 V, fSW = 650 kHz
06772-072
V
OUT
= 20V
f
SW
= 650kHz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE ( 200mV /DIV )
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 70. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 20 V, fSW = 650 kHz
ADP1612/ADP1613 Data Sheet
Rev. D | Page 22 of 28
06772-073
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 20VV
IN
= 3.3V TO 5.5V
L1
10µH
C
SS
33nF
C
OUT
10µF
C
COMP
1200pF
R
COMP
8.2kΩ
R1
150kΩ
R2
10kΩ
D1
3A, 40V
C
IN
10µF
L1: DO3316P-103M L
D1: MBRA340T3G
R1: RC0805JR-07150KL
R2: CRCW 080510K0FKEA
R
COMP
: RC0805JR-078K2L
C
COMP
: ECL-2VB1H122K
C
IN
: G RM 21BR61C106KE 15L
C
OUT
: G RM 32DR71E 106KA12L
C
SS
: ECJ- 2V B1H333K
Figure 71. ADP1613 Step-Up Regulator Configuration
VOUT = 20 V, fSW = 1.3 MHz
100
90
80
70
60
50
40
30
20110 100 1k
LOAD CURRENT ( mA)
EF FICIENCY ( %)
06772-074
V
OUT
= 20V
fSW
= 1.3M Hz
T
A
= 25° C
ADP1613
V
IN
= 3.3V
V
IN
= 4.2V
V
IN
= 5.0V
V
IN
= 5.5V
Figure 72. ADP1613 Efficiency vs. Load Current
VOUT = 20 V, fSW = 1.3 MHz
06772-075
V
OUT
= 20V
f
SW
= 1.3M Hz
T
TIME ( 100µ s/DIV )
OUTPUT VOLTAGE (200mV/DIV)
AC-COUPLED
LOAD CURRENT ( 50mA/DIV )
Figure 73. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V)
VOUT = 20 V, fSW = 1.3 MHz
SEPIC CONVERTER
The circuit in Figure 74 shows the ADP1612/ADP1613 in a
single-ended primary inductance converter (SEPIC) topology.
This topology is useful for an unregulated input voltage, such as
a battery-powered application in which the input voltage can vary
between 2.7 V to 5 V and the regulated output voltage falls within
the input voltage range.
The input and the output are dc isolated by a coupling capacitor
(C1). In steady state, the average voltage of C1 is the input voltage.
When the ADP1612/ADP1613 switch turns on and the diode
turns off, the input voltage provides energy to L1 and C1 provides
energy to L2. When the ADP1612/ADP1613 switch turns off
and the diode turns on, the energy in L1 and L2 is released to
charge the output capacitor (COUT) and the coupling capacitor
(C1) and to supply current to the load.
ADP1612/
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
V
OUT
= 3.3VV
IN
= 2.0V TO 5.5V
L1
DO3316P
4.7µH
C
IN
10µF
C
SS
C
OUT
10µF
C1
10µF
R
COMP
82kΩ
C
COMP
220pF
R1
16.9kΩ
L2
DO3316P
4.7µH
R2
10kΩ
MBRA210LT
2A, 10V
06772-008
Figure 74. SEPIC Converter
TFT LCD BIAS SUPPLY
Figure 75 shows a power supply circuit for TFT LCD module
applications. This circuit has +10 V, −5 V, and +22 V outputs.
The +10 V is generated in the step-up configuration. The −5 V
and +22 V are generated by the charge-pump circuit. During
the step-up operation, the SW node switches between +10 V
and ground (neglecting the forward drop of the diode and on
resistance of the switch). When the SW node is high, C5 charges
up to +1 0 V. When the SW node is low, C5 holds its charge and
forward-biases D8 to charge C6 to −10 V. The Zener diode (D9)
clamps and regulates the output to −5 V.
The VGH output is generated in a similar manner by the charge-
pump capacitors, C1, C2, and C4. The output voltage is tripled
and regulated down to 22 V by the Zener diode, D5.
Data Sheet ADP1612/ADP1613
Rev. D | Page 23 of 28
DO3316P
4.7µH
06772-007
C1
10nF
C4
10nF
D3
D2
D5
D4
C5
10nF
C6
10µF
D8
D7
R4
200Ω
D9
BZT52C5VIS
VGL
–5V
R3
200Ω
C3
10µF D5
BZT52C22
C2
1µF
BAV99
BAV99
BAV99
ADP1612/
ADP1613
6
3
7
8
5
2
1
4
VIN
EN
FREQ
SS
SW
FB
COMP
GND
ON
OFF
1.3MHz
650kHz
(DEFAULT)
VOUT = 10VVIN = 3.3V
CIN
10µF
CSS
COUT
10µF
CCOMP
1200pF
RCOMP
27kΩ
R1
71.5kΩ
R2
10kΩ
D1
VGH
+22V
Figure 75. TFT LCD Bias Supply
ADP1612/ADP1613 Data Sheet
Rev. D | Page 24 of 28
PCB LAYOUT GUIDELINES
06772-076
Figure 76. Example Layout for ADP1612/ADP1613 Boost Application
(Top Layer)
06772-077
Figure 77. Example Layout for ADP1612/ADP1613 Boost Application
(Bottom Layer)
For high efficiency, good regulation, and stability, a well-designed
printed circuit board layout is required.
Use the following guidelines when designing printed circuit
boards (also see Figure 34 for a block diagram and Figure 3
for a pin configuration).
• Keep the low ESR input capacitor, CIN (labeled as C7 in
Figure 76), close to VIN and GND. This minimizes noise
injected into the part from board parasitic inductance.
• Keep the high current path from CIN (labeled as C7 in
Figure 76) through the L1 inductor to SW and GND as
short as possible.
• Keep the high current path from VIN through L1, the
rectifier (D1) and the output capacitor, COUT (labeled as
C4 in Figure 76) as short as possible.
• Keep high current traces as short and as wide as possible.
• Place the feedback resistors as close to FB as possible to
prevent noise pickup. Connect the ground of the feedback
network directly to an AGND plane that makes a Kelvin
connection to the GND pin.
• Place the compensation components as close as possible to
COMP. Connect the ground of the compensation network
directly to an AGND plane that makes a Kelvin connection
to the GND pin.
• Connect the softstart capacitor, CSS (labeled as C1 in
Figure 76) as close to the device as possible. Connect the
ground of the softstart capacitor to an AGND plane that
makes a Kelvin connection to the GND pin.
• Avoid routing high impedance traces from the compensa-
tion and feedback resistors near any node connected to SW
or near the inductor to prevent radiated noise injection.
Data Sheet ADP1612/ADP1613
Rev. D | Page 25 of 28
OUTLINE DIMENSIONS
COMPLIANT TO JEDEC STANDARDS MO-187-AA
6°
0°
0.80
0.55
0.40
4
8
1
5
0.65 BSC
0.40
0.25
1.10 MAX
3.20
3.00
2.80
COPLANARITY
0.10
0.23
0.09
3.20
3.00
2.80
5.15
4.90
4.65
PIN 1
IDENTIFIER
15° MAX
0.95
0.85
0.75
0.15
0.05
10-07-2009-B
Figure 78. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
ORDERING GUIDE
Model1 Temperature Range Package Description2 Package Option Branding
ADP1612ARMZ-R7 −40°C to +125°C 8-Lead Mini Small Outline Package [MSOP] RM-8 L7Z
ADP1612-5-EVALZ Evaluation Board, 5 V Output Voltage Configuration
ADP1613ARMZ-R7 −40°C to +125°C 8-Lead Mini Small Outline Package [MSOP] RM-8 L96
ADP1613-12-EVALZ Evaluation Board, 12 V Output Voltage Configuration
1 Z = RoHS Compliant Part.
ADP1612/ADP1613 Data Sheet
Rev. D | Page 26 of 28
NOTES
Data Sheet ADP1612/ADP1613
Rev. D | Page 27 of 28
NOTES
ADP1612/ADP1613 Data Sheet
Rev. D | Page 28 of 28
NOTES
©2009–2012 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06772-0-11/12(D)
Mouser Electronics
Authorized Distributor
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