EL2245CS-T7 - Intersil Corporation

FN7060

CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.

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EL2245, EL2445

Dual/Quad Low-Power 100MHz Gain-of-2

Stable Op Amp

The EL2245 and EL2445 are dual and

quad versions of the popular EL2045.

They are high speed, low power, low

cost monolithic operational amplifiers built on Elantec's

proprietary complementar y bipolar process. The EL2245

and EL2445 are gain-of-2 stable and f eature a 275V/µs slew

rate and 100MHz bandwidth at gain-of-2 while requiring only

5.2mA of supply current per ampli fi e r.

The power supply operating range of the EL2245 and

EL2445 is from ±18V down to as little as ±2V. For single-

supply operation, the EL2245 and EL2445 operate from 36V

down to as little as 2.5V. The excellent power supply

operating range of the EL2245 and EL2445 ma kes them an

obvious choice for applications on a single +5V or +3V

supply.

The EL2245 and EL2445 also feature an extremely wide

output voltage swing of ±13.6V with VS = ±15V and

RL=1kΩ. At ±5V, output voltage swing is a wide ±3.8V with

RL = 500Ω and ±3.2V with RL = 150Ω. Further more, for

single-supply operation at +5V, output voltage swing is an

excellent 0.3V to 3.8V with RL = 500Ω.

At a gain of +2, the EL2245 and EL2445 have a -3dB

bandwidth of 100MHz with a phase margin of 50°. Because

of their conventional voltage-feedback topology, the EL2245

and EL2445 allow the use of reactive or non-linear elements

in their feedback network. This versatility combined with low

cost and 75mA of output-current drive mak e the EL2245 and

EL2445 an ideal choice for price-sensitive applications

requiring low pow er and high speed.

Features

• 100MHz gain-bandwidth

• Gain-of-2 stable

• Low supply current (per amplifier) - 5.2mA at VS = ±15V

• Wide supply range - 2.5V to 36V

• High slew rate - 275V/µs

• Fast-settling - 80ns to 0.1% for a 10V step

• Low differential gain - 0.02% at AV=+2, R

L = 150Ω

• Low differential phase - 0.07° at AV = +2, RL = 150Ω

• Wide output voltage swing - ±13.6V with VS = ±15V,

RL=1kΩ

Applications

• Video amplifiers

• Single-supply amplifiers

• Active filters/integrators

• High speed signal processing

• ADC/DAC buffers

• Pulse/RF amplifiers

• Pin diode receivers

• Log amplifiers

Ordering Information

PART NUMBER PACKAGE TAPE &

REEL PKG. NO.

EL2245CN 8-Pin PDIP - MDP0031

EL2245CS 8-Pin SO - MDP0027

EL2245CS-T7 8-Pin SO 7” MDP0027

EL2245CS-T13 8-Pin SO 13” MDP0027

EL2445CN 14-Pin PDIP - MDP0031

EL2445CS 14-Pin SO (0.150") - MDP0027

EL2445CS-T7 14-Pin SO (0.150") 7” MDP0027

EL2445CS-T13 14-Pin SO (0.150") 13” MDP0027

Data Sheet March 27, 2002

Pinouts EL2245

(8-PIN SO, PDIP)

TOP VIEW

EL2445

[14-PIN SO (0.150”), PDIP]

TOP VIEW

OUT

IN1-

IN1+

V-

V+

OUT2

IN2-

IN2+

OUT1

IN1-

IN1+

V+

OUT4

IN4-

IN4+

V-

IN2+

IN2-

OUT2

IN3+

IN3-

OUT3

-+ -+

EL2245, EL2445

Absolute Maximum Ratings (TA = 25°C)

Supply Voltage (VS). . . . . . . . . . . . . . . . . . . . . . . . . . . .±18V or 36V

Input Voltage (VIN). . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±VS

Differential Input Voltage (dVIN). . . . . . . . . . . . . . . . . . . . . . . . .±10V

Continuous Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . 40mA

Power Dissipation (PD) . . . . . . . . . . . . . . . . . . . . . . . . . See Curves

Operating Temperature Range (TA). . . . . . . . . . . . . .-40°C to +85°C

Operating Junction Temperature (TJ) . . . . . . . . . . . . . . . . . .+150°C

Storage Temperature (TST) . . . . . . . . . . . . . . . . . . .-65°C to +150°C

CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the

device at these or any other conditi ons above those indicated in the operational sections of this specification is not implied.

IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests

are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA

DC Electrical Specificat ions VS = ±15V, RL = 1kΩ, unless otherwise specified.

PARAMETER DESCRIPTION CONDITION TEMP MIN TYP MAX UNIT

VOS Input Offset Voltage VS = ±15V 25°C 0.5 4.0 mV

TMIN, TMAX 6.0 mV

TCVOS Average Offset Voltage Drift (Note 1) All 10.0 µV/°C

IBInput Bias Current VS = ±15V 25°C 2.8 8.2 µA

TMIN, TMAX 9.2 µA

VS = ±5V 25°C 2.8 µA

IOS Input Offset Current VS = ±15V 25°C 50 300 nA

TMIN, TMAX 400 nA

VS = ±5V 25°C 50 nA

TCIOS Average Offset Current Drift (Note 1) All 0.3 nA/°C

AVOL Open-loop Gain VS = ±15V,VOUT = ±10V, RL = 1kΩ25°C 1500 3000 V/V

TMIN, TMAX 1500 V/V

VS = ±5V, VOUT = ±2.5V, RL = 500Ω25°C 2500 V/V

VS = ±5V, VOUT = ±2.5V, RL = 150Ω25°C 1750 V/V

PSRR Power Supply Rejection Ratio VS = ±5V to ±15V 25°C 65 80 dB

TMIN, TMAX 60 dB

CMRR Common-mode Rejection Ratio VCM = ±12V, VOUT = 0V 25°C 70 90 dB

TMIN, TMAX 70 dB

CMIR Common-mode Input Range VS = ±15V 25°C ±14.0 V

VS = ±5V 25°C ±4.2 V

VS = +5V 25°C 4.2/0.1 V

VOUT Output Voltage Swing VS = ±15V, RL = 1kΩ25°C ±13.4 ±13.6 V

TMIN, TMAX ±13.1 V

VS = ±15V, RL = 500Ω25°C ±12.0 ±13.4 V

VS = ±5V, RL = 500Ω25°C ±3.4 ±3.8 V

VS = ±5V, RL = 150Ω25°C ±3.2 V

VS = +5V, RL = 500Ω25°C 3.6/0.4 3.8/0.3 V

TMIN, TMAX 3.5/0.5 V

ISC Output Short Circuit Current 25°C 40 75 mA

TMIN, TMAX 35 mA

EL2245, EL2445

ISSupply Current (per amplifier) VS = ±15V, no load 25°C 5.2 7 mA

TMIN 7.6 mA

TMAX 7.6 mA

VS = ±5V, no load 25°C 5.0 mA

RIN Input Resistance Differential 25°C 150 kΩ

Common-mode 25°C 15 MΩ

CIN Input Capacitance AV = +1 @10MHz 25°C 1.0 pF

ROUT Output Resistance AV = +1 25°C 50 mΩ

PSOR Power-supply Operating Range Dual-supply 25°C ±2.0 ±18.0 V

Single-supply 25°C 2.5 36.0 V

NOTE:

1. Measured from TMIN to TMAX.

Closed-Loop AC Electrical Specifications VS = ±15V, AV = +2, RL = 1kΩ unless otherwise specified.

PARAMETER DESCRIPTION CONDITION TEMP MIN TYP MAX UNIT

BW -3dB Bandwidth

(VOUT = 0.4VPP)VS = ±15V, AV = +2 25°C 100 MHz

VS = ±15V, AV = -1 25°C 75 MHz

VS = ±15V, AV = +5 25°C 20 MHz

VS = ±15V, AV = +10 25°C 10 MHz

VS = ±15V, AV = +20 25°C 5 MHz

VS = ±5V, AV = +2 25°C 75 MHz

GBWP Gain-bandwidth Product VS = ±15V 25°C 200 MHz

VS = ±5V 25°C 150 MHz

PM Phase Margin RL = 1 kΩ, CL = 10pF 25°C 50 °

CS Channel Separation f = 5MHz 25°C 85 dB

SR Slew Rate (Note 1) VS = ±15V, RL = 1kΩ25°C 200 275 V/µs

VS = ±5V, RL = 500Ω25°C 200 V/µs

FPBW Full-power Bandwidth (Note 2) VS = ±15V 25°C 3.2 4.4 MHz

VS = ±5V 25°C 12.7 MHz

tR, tFRise Time, Fall Time 0.1V step 25°C 3.0 ns

OS Overshoot 0.1V step 25°C 20 %

tPD Propagation Delay 25°C 2.5 ns

tSSettling to +0.1% (AV = +1) VS = ±15V, 10V step 25°C 80 ns

VS = ±5V, 5V step 25°C 60 ns

dG Differential Gain (Note 3) NTSC/PAL 25°C 0.02 %

dP Differential Phase (Note 3) NTSC/PAL 25°C 0.07 °

eN Input Noise Voltage 10kHz 25°C 15.0 nV/√Hz

iN Input Noise Current 10kHz 25°C 1.50 pA/√Hz

NOTES:

1. Slew rate is measured on rising edge.

2. For VS = ±15V, VOUT = 20VPP. For VS = ±5V, VOUT = 5VPP. Full-power bandwidth is based on slew rate measurement using: FPBW = SR/(2π

* Vpeak).

3. Video performance measured at VS = ±15V, AV = +2 with 2 times normal video level across RL = 150Ω. This corresponds to standard video

levels across a back-terminated 75Ω load. For other values of RL, see curves.

DC Electrical Specificat ions VS = ±15V, RL = 1kΩ, unless otherwise specified. (Continued)

PARAMETER DESCRIPTION CONDITION TEMP MIN TYP MAX UNIT

EL2245, EL2445

Test Circuit

Typical Performance Curves

Non-Inverting

Frequency Response Inverting Frequency

Response Frequency Response for

Various Load Resistances

Equivalent Input Noise

Output Voltage Swing

vs Frequency

Open-Loop Gain and

Phase vs Frequency

CMRR, PSRR and Closed-

Loop Output Resistance

vs Frequency 2nd and 3rd Harmonic

Distortion vs Frequency Settling Time vs

Output Voltage Change

Supply Current vs

Supply Voltag e Common-Mode Input

Range vs Supply Voltage Output Voltage Range

vs Supply Voltag e

EL2245, EL2445

Typical Performance Curves (Continued)

Gain-Bandwidth Product

vs Supply Voltage Open-Loop Gain

vs Supply Voltage Slew-Rate vs

Supply Voltage

Voltage Swing

vs Load Resistance

Open-Loop Gain

vs Load Resistance

Bias and Offset Current

vs Input Common-Mode Voltage

Offset Voltage

vs Temperature Bias and Output

Current vs Temperature Supply Current

vs Temperature

Slew Rate vs

Temperature

Open-Loop Gain PSRR

and CMRR vs Temperature

Gain-Bandwidth Product

vs Temperature

EL2245, EL2445

Typical Performance Curves (Continued)

Short-Circuit Current

vs Temperature

Differential Gain and

Phase vs DC Input

Offset at 3.58MHz

Differential Gain and

Phase vs DC Input

Offset at 4.43MHz

Differential Gain and

Phase vs Number of

150Ω Loads at 3.58MHz

Differential Gain and

Phase vs Number of

150Ω Loads at 4.43MHz

Channel Separation

vs Frequency

Small-Signal

Step Response Large-Signal

Step Response

EL2245, EL2445

Typical Performance Curves (Continued)

Simplified Schematic (Per Amplifier)

Package Power Dissipation vs Ambient Temperature

JEDEC JESD51-3 Low Effective Thermal Conductivity

(Single Layer) Test Boa r d

1.8

1.6

1.4

1.2

0.8

0.6

0.4

0.2

00 25507510012515085

Ambient Temperature (°C)

Power Dissipation (W)

1.54W

1.25W PDIP14

θJA=81°C/W

PDIP8

θJA=100°C/W

Package Power Dissipation vs Ambient Temperature

JEDEC JESD51-3 Low Effective Thermal Conduc ti vi ty

(Single Layer) Test Board

1.2

0.8

0.6

0.4

0.2

00 25507510012515085

Ambient Temperature (°C)

Power Dissipation (W)

1.042W

781mW

SO14

θJA=120°C/W

SO8

θJA=160°C/W

Gain-Bandwidth Product vs Load Capacitance

100

01 10 100 1k 10k

Load Capacitance (pF)

Gain-Bandwidth Product (MHz)

VS=±15V

AV=-2

Overshoot vs Load Capacitance

050 450 1050

Load Capacitance (pF)

Overshoot (%)

VS=±15V

RG=1kΩ

650250 850

EL2245, EL2445

Burn-In Circuit (Per Amplifier)

Applications Information

Product Description

The EL2245 and EL2445 are dual and quad low-power

wideband monolithic operational amplifiers built on Elantec's

proprietary high-speed complementary bipolar process. The

EL2245 and EL2445 use a classical voltage-feedbac k

topology which allows them to be used in a variety of

applications where current-feedback amplifiers are not

appropriate because of restrictions placed upon the

feedback element used with the amplifier. The conventional

topology of the EL2245 and EL2445 allows, for example, a

capacitor to be placed in the feedback path, making it an

excellent choice for applications such as active filters,

sample-and-holds, or integrators. Similarly, because of the

ability to use diodes in the feedback network, the EL2245

and EL2445 are an excellent choice for applications such as

f ast log amplifiers.

Power Dissipation

With the wide power supply range and large output drive

capability of the EL2245 and EL2445, it is possible to e xceed

the 150°C maximum junction temperatures under certain

load and power-supply conditions. It is theref ore important to

calculate the maximum junction temperature (TJMAX) for all

applications to determine if power supply voltages, load

conditions, or package type need to be modified for the

EL2245 and EL2445 to remain in the safe operating area.

These parameters are related as follows:

where:

PDMAXTOTAL is the sum of the maximum power dissipation

of each amplifier in the package (PDMAX). PDmax for each

amplifier can be calculated as follows:

where:

TMAX = Maximum ambient temperature

θJA = Thermal resistance of the package

PDMAX = Maximum power dissipation of each amplifier

VS = Supply voltage

ISMAX = Maximum supply current of each amplifier

VOUTMAX = Maximum output voltage swing of the

application

RL = Load resistance

To serve as a guide for the user, we can calculate maximum

allowable supply voltages for the example of the video cable-

driver below since we know that TJMAX = 150°C , TMAX =

85°C, ISMAX = 7.6mA per amplifier, and the package θJAs

are shown in Table 1. If we assume (f or this example) that we

are driving a back-terminated video cable, then the

maximum average value (over duty-cycle) of VOUTMAX is

1.4V, and RL = 150Ω, giving the results seen in Table 1.

Single-Supply Operation

The EL2245 and EL2445 have been designed to have a

wide input and output voltage range. This design also makes

the EL2245 and EL2445 an excellent choice for single-

supply operation. Using a single positive supply, the lower

input voltage range is within 100mV of ground (RL = 500Ω),

and the lower output voltage range is within 300mV of

ground. Upper input voltage range reaches 4.2V, and output

voltage range reaches 3.8V with a 5V supply and

RL= 500Ω. This results in a 3.5V output swing on a single

5V supply. This wide output voltage range also allows single-

supply operation with a supply voltage as high as 36V or as

low as 2.5V. On a single 2.5V supply, the EL2245 and

EL2445 still have 1V of output swing.

Gain-Bandwidth Product and the -3dB Bandwidth

The EL2245 and EL2445 have a bandwidth at gain-of-2 of

100MHz while using only 5.2mA of supply current per

amplifier. For gains greater than 4, their closed-loop -3dB

bandwidth is approximately equal to the gain-bandwidth

product divided by the noise gain of the circuit. For gains

less than 4, higher-order poles in the amplifiers' transfer

ALL PACKAGES USE THE SAME SCHEMATIC

TJMAX TMAX ΘJA PDMAXTOTAL

×()+=

PDMAX 2V

SISMAX VS

(VOUTMAX)VOUTMAX

----------------------------

×–+××=

TABLE 1.

PART PACKAGE ΘJA

MAX PDISS

@TMAX MAX VS

DUALS

EL2245CN PDIP8 100°C/W 0.650W @85°C ±16.6V

EL2245CS SO8 160°C/W 0.406W @85°C ±10.5V

QUADS

EL2445CN PDIP14 81°C/W 0.802W @85°C ±11.5V

EL2445CS SO14 120°C/W 0.542W @85°C ±7.5V

EL2245, EL2445

function contri bute to even higher closed loop bandwidths.

For example, the EL2245 and EL2445 have a -3dB

bandwidth of 100MHz at a gain of +2, dropping to 20MHz at

a gain of +5. It is important to note tha t the EL22 45 and

EL2445 hav e been designed so that this “extra” bandwidth in

low-gain applications does not come at the expense of

stability. As seen in the typical performance curves, the

EL2245 and EL2445 in a gain of +2 only exhibit 1.0dB of

peaking with a 1kΩ load.

Video Performance

An industry-standard method of measuring the video

distortion of components such as the EL2245/ EL2445 is to

measure the amount of differential gain (dG) and differential

phase (dP) that they introduce. To make these

measurements, a 0.286VPP (40 IRE) signal is applied to the

de vice with 0V DC offset (0 IRE) at either 3.58MHz f or NTSC

or 4.43MHz f or PAL. A second measurement is then made at

0.714V DC offset (100 IRE). Diff erential gain is a measure of

the change in amplitude of the sine wave, and is measured

in percent. Differential phase is a measure of the change in

phase, and is measured in degrees.

For signal transmission and distribution, a back-termin ated

cable (75Ω in series at the drive end, and 75Ω to ground at

the receiving end) is preferred since the impedance match at

both ends will absorb any reflections. Howe v er, when double

termination is used, the received signal is halved; therefore a

gain of 2 configuration is typically used to compensate for

the attenuation.

The EL2245 and EL2445 have been designed as an

economical solution for applications requiring low video

distortion. They have been thoroughly characterized for

video performance in the topology described above, and the

results have been included as typical dG and dP

specifications and as typical performa nce curves. In a gain

of +2, driving 150Ω, with standard video test levels at the

input, the EL2245 and EL2445 exhibit dG and dP of only

0.02% and 0.07° at NTSC and PAL. Because dG and dP can

vary with different DC offsets, the video performance of the

EL2245 and EL2445 has been characterized over the entire

DC offset range from -0.714V to +0.714V. For more

infor m ation, refer to the curves of dG and dP vs DC Input

Offset.

Output Drive Capability

The EL2245 and EL2445 have been designed to drive low

impedance loads. They can easily drive 6VPP into a 150Ω

load. This high output drive capability makes the EL2245

and EL2445 an ideal choice for RF, IF and video

applications. Furthermore, the current drive of the EL2245

and EL2445 remains a minimum of 35mA at low

temperatures.

Printed-Circuit Layout

The EL2245 and EL2445 are well behaved, and easy to

apply in most applications. However, a few simple

techniques will help assure rapid, high quality results. As

with any high-frequency device, good PCB layout is

necessary for optimum performance. Ground-plane

construction is highly recommended, as is good power

supply bypassing. A 0.1µF ceramic capacitor is

recommended for bypassing both supplies. Lead lengths

should be as short as possible, and bypass capacitors

should be as close to the device pins as possible. For good

AC performance, parasitic capacitances should be kept to a

minimum at both inputs and at the output. Resistor values

should be kept under 5kΩ because of the RC time constant s

associated with the parasitic capacitance. Metal-film and

carbon resistors are both acceptable, use of wire-wound

resistors is not recommended because of their parasitic

inductance. Similarly, capacitors should be low-inductance

for best performance.

The EL2245 and EL2445 Macromodel

This macromodel has been developed to assist the user in

simulating the EL2245 and EL2445 with surrounding

circuitr y. It has been developed for the PSPICE simulator

(copywritten b y the Microsim Corporation), and may need to

be rearranged for other simulators. It approxi mates DC, AC,

and transient response for resistive lo ads, but does not

accurately model capacitive loading. This model is slightly

more complicated than the models used for low-frequency

op-amps, but it is much more accurate for AC analysis.

The model does not simulate these characteristics

accurately:

•Noise

•Settling time

• Non-linearities

• Temperature effects

• Manufacturing variations

•CMRR

• PSRR

EL2245, EL2445

EL2245 and EL2445 Macromodel

* Connections: +input

* | -input

* | | +Vsupply

* | | | -Vsupply

* | | | | output

* | | | | |

.subckt M2245 3 2 7 4 6

* Input stage

ie 7 37 1mA

r6 36 37 400

r7 38 37 400

rc1 4 30 850

rc2 4 39 850

q1 30 3 36 qp

q2 39 2 38 qpa

ediff 33 0 39 30 1.0

rdiff 33 0 1Meg

* Compensation Section

ga 0 34 33 0 1m

rh 34 0 2Meg

ch 34 0 1.3pF

rc 34 40 1K

cc 40 0 1pF

* Poles

ep 41 0 40 0 1

r pa 41 42 200

cpa 42 0 1pF

r pb 42 43 200

cpb 43 0 1pF

* Output Stage

ios1 7 50 1.0mA

ios2 51 4 1.0mA

q3 4 43 50 qp

q4 7 43 51 qn

q5 7 50 52 qn

q6 4 51 53 qp

ros1 52 6 25

ros2 6 53 25

* Power Supply Current

ips 7 4 2.7mA

* Models

.model qn npn(is=800E-18 bf=200 tf=0.2nS)

.model qpa pnp(is=864E-18 bf=10 0 tf=0.2nS)

.model qp pnp(is=800E-18 bf=125 tf=0.2nS)

.ends

EL2245, EL2445

EL2245 and EL2445 Macromodel (Continued)

EL2245, EL2445

All Intersil U.S. products are man ufactured, assembled and tested utilizing ISO9000 quality systems.

Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/q uality

Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without

notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and

reliable. However, no responsibility is assumed by Intersil or its subsidiaries fo r its use; nor for any infringements of patents or other rights of third par ties which may result

from its use. No license i s gr a nted b y imp lica tion or oth erw ise unde r any patent or pat en t rights of In t ersil or its sub sidi aries.

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