LTC1748 14-Bit, 80Msps Low Noise ADC U FEATURES DESCRIPTIO The LTC (R)1748 is an 80Msps, sampling 14-bit A/D converter designed for digitizing high frequency, wide dynamic range signals. Pin selectable input ranges of 1V and 1.6V along with a resistor programmable mode allow the LTC1748's input range to be optimized for a wide variety of applications. Sample Rate: 80Msps 76.3dB SNR and 90dB SFDR (3.2V Range) 72.6dB SNR and 90dB SFDR (2V Range) No Missing Codes Single 5V Supply Power Dissipation: 1.4W Selectable Input Ranges: 1V or 1.6V 240MHz Full Power Bandwidth S/H Pin Compatible Family 25Msps: LTC1746 (14-Bit), LTC1745 (12-Bit) 50Msps: LTC1744 (14-Bit), LTC1743 (12-Bit) 65Msps: LTC1742 (14-Bit), LTC1741 (12-Bit) 80Msps: LTC1748 (14-Bit), LTC1747 (12-Bit) 48-Pin TSSOP Package The LTC1748 is perfect for demanding communications applications with AC performance that includes 76.3dB SNR and 90dB spurious free dynamic range. Ultralow jitter of 0.15psRMS allows undersampling of IF frequencies with excellent noise performance. DC specs include 3LSB INL and no missing codes. The digital interface is compatible with 5V, 3V, 2V and LVDS logic systems. The ENC and ENC inputs may be driven differentially from PECL, GTL and other low swing logic families or from single-ended TTL or CMOS. The low noise, high gain ENC and ENC inputs may also be driven by a sinusoidal signal without degrading performance. A separate output power supply can be operated from 0.5V to 5V, making it easy to connect directly to any low voltage DSPs or FIFOs. U APPLICATIO S Telecommunications Receivers Cellular Base Stations Spectrum Analysis Imaging Systems The TSSOP package with a flow-through pinout simplifies the board layout. , LTC and LT are registered trademarks of Linear Technology Corporation. W BLOCK DIAGRA 80Msps, 14-Bit ADC with a 2V Differential Input Range OVDD 0.5V TO 5V 0.1F 0.1F AIN+ 1V DIFFERENTIAL ANALOG INPUT S/H AMP AIN- CORRECTION LOGIC AND SHIFT REGISTER 14-BIT PIPELINED ADC 14 OUTPUT LATCHES * * * OF D13 D0 CLKOUT OGND SENSE BUFFER RANGE SELECT VDD 5V 1F 1F DIFF AMP 1F VCM GND 2.35VREF CONTROL LOGIC 4.7F 1748 BD REFLB REFHA 4.7F REFLA 0.1F 1F REFHB ENC 0.1F 1F ENC MSBINV OE DIFFERENTIAL ENCODE INPUT 1748fa 1 LTC1748 W U PACKAGE/ORDER INFORMATION U W W W OVDD = VDD (Notes 1, 2) Supply Voltage (VDD) ............................................. 5.5V Analog Input Voltage (Note 3) .... - 0.3V to (VDD + 0.3V) Digital Input Voltage (Note 4) ..... - 0.3V to (VDD + 0.3V) Digital Output Voltage ................. - 0.3V to (VDD + 0.3V) OGND Voltage ..............................................- 0.3V to 1V Power Dissipation ............................................ 2000mW Operating Temperature Range LTC1748C ............................................... 0C to 70C LTC1748I ............................................ - 40C to 85C Storage Temperature Range ................. - 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C U ABSOLUTE MAXIMUM RATINGS ORDER PART NUMBER TOP VIEW SENSE VCM GND AIN+ AIN- GND VDD VDD GND REFLB REFHA GND GND REFLA REFHB GND VDD VDD GND VDD GND MSBINV ENC ENC 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 48 47 46 45 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 OF OGND D13 D12 D11 OVDD D10 D9 D8 D7 OGND GND GND D6 D5 D4 OVDD D3 D2 D1 D0 OGND CLKOUT OE LTC1748CFW LTC1748IFW FW PACKAGE 48-LEAD PLASTIC TSSOP TJMAX = 150C, JA = 35C/W Consult LTC Marketing for parts specified with wider operating temperature ranges. U CO VERTER CHARACTERISTICS The indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 5) PARAMETER Resolution (No Missing Codes) Integral Linearity Error Differential Linearity Error Offset Error Gain Error Full-Scale Tempco Offset Tempco Input Referred Noise (Transition Noise) CONDITIONS (Note 6) (Note 7) External Reference (SENSE = 1.6V) Internal Reference External Reference (SENSE = 1.6V) MIN 14 -3 -1 - 35 - 3.5 SENSE = 1.6V TYP MAX 0.75 0.5 8 1 40 20 20 0.82 3 1.5 35 3.5 UNITS Bits LSB LSB mV %FS ppm/C ppm/C V/C LSBRMS U U A ALOG I PUT The indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 5) SYMBOL VIN IIN CIN PARAMETER Analog Input Range (Note 8) Analog Input Leakage Current Analog Input Capacitance tACQ tAP tJITTER CMRR Sample-and-Hold Acquisition Time Sample-and-Hold Acquisition Delay Time Sample-and-Hold Acquisition Delay Time Jitter Analog Input Common Mode Rejection Ratio CONDITIONS 4.75V VDD 5.25V 0 < AIN+, AIN- < VDD Sample Mode ENC < ENC Hold Mode ENC > ENC MIN 1.5V < (AIN- = AIN+) < 3V TYP 1 to 1.6 -1 MAX 1 8 4 5 0 0.15 80 6 UNITS V A pF pF ns ns psRMS dB 1748fa 2 LTC1748 W U DY A IC ACCURACY TA = 25C, AIN = -1dBFS (Note 5) SYMBOL PARAMETER CONDITIONS SNR Signal-to-Noise Ratio SFDR Spurious Free Dynamic Range MIN TYP 5MHz Input Signal (2V Range) 5MHz Input Signal (3.2V Range) 75 72.6 76.3 dB dB 30MHz Input Signal (2V Range) 30MHz Input Signal (3.2V Range) 74 72.5 76.1 dB dB 70MHz Input Signal (2V Range) 70MHz Input Signal (3.2V Range) 72.2 75.4 dB dB 140MHz Input Signal (2V Range) 71.4 dB 250MHz Input Signal (2V Range) 68.9 dB 5MHz Input Signal (2V Range) 90 dB 90 dB 5MHz Input Signal (3.2V Range) (Other) 94 dB 90 dB 30MHz Input Signal (3.2V Range) (2nd and 3rd) 80 88 dB 30MHz Input Signal (3.2V Range) (Other) 85 94 dB 70MHz Input Signal (2V Range) 85 dB 70MHz Input Signal (3.2V Range) (2nd and 3rd) 76 dB 70MHz Input Signal (3.2V Range) (Other) 94 dB 140MHz Input Signal (2VRange) (2nd and 3rd) 77 dB 140MHz Input Signal (2V Range) (Other) 93 dB 250MHz Input Signal (2V Range) (2nd and 3rd) 64 dB 250MHz Input Signal (2V Range) (Other) THD IMD UNITS 5MHz Input Signal (3.2V Range) (2nd and 3rd) 30MHz Input Signal (2V Range) S/(N + D) MAX 89 dB 72.4 76.0 dB dB 30MHz Input Signal (2V Range) 30MHz Input Signal (3.2V Range) 72.3 75.6 dB dB 70MHz Input Signal (2V Range) 70MHz Input Signal (3.2V Range) 71 71 dB dB 5MHz Input Signal, First 5 Harmonics (2V Range) 5MHz Input Signal, First 5 Harmonics (3.2V Range) -90 -90 dB dB 30MHz Input Signal, First 5 Harmonics (2V Range) 30MHz Input Signal, First 5 Harmonics (3.2V Range) -90 -85 dB dB 70MHz Input Signal, First 5 Harmonics (2V Range) 70MHz Input Signal, First 5 Harmonics (3.2V Range) -78 -74 dB dB Intermodulation Distortion fIN1 = 2.52MHz, fIN2 = 5.2MHz (2V Range) fIN1 = 2.52MHz, fIN2 = 5.2MHz (3.2V Range) 97 93 dBc dBc Sample-and-Hold Bandwidth RSOURCE = 50 240 MHz Signal-to-(Noise + Distortion) Ratio Total Harmonic Distortion 5MHz Input Signal (2V Range) 5MHz Input Signal (3.2V Range) U U U I TER AL REFERE CE CHARACTERISTICS 74.5 (Note 5) PARAMETER CONDITIONS MIN TYP MAX VCM Output Voltage IOUT = 0 2.30 2.35 2.40 VCM Output Tempco IOUT = 0 VCM Line Regulation 4.75V VDD 5.25V 3 mV/V VCM Output Resistance 1mA IOUT 1mA 4 30 UNITS V ppm/C 1748fa 3 LTC1748 U U DIGITAL I PUTS A D DIGITAL OUTPUTS The indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 5) SYMBOL PARAMETER CONDITIONS MIN VIH High Level Input Voltage VDD = 5.25V, MSBINV and OE VIL Low Level Input Voltage VDD = 4.75V, MSBINV and OE IIN Digital Input Current VIN = 0V to VDD CIN Digital Input Capacitance MSBINV and OE Only VOH High Level Output Voltage OVDD = 4.75V VOL Low Level Output Voltage OVDD = 4.75V Hi-Z Output Leakage D13 to D0 COZ ISOURCE ISINK UNITS 0.8 V 10 A 2.4 4 IO = 160A IO = 1.6mA IOZ MAX IO = -10A IO = - 200A TYP V 1.5 pF 4.74 V 4.74 V 0.05 0.1 V 0.4 V 10 A VOUT = 0V to VDD, OE = High Hi-Z Output Capacitance D13 to D0 OE = High (Note 8) Output Source Current VOUT = 0V - 50 mA Output Sink Current VOUT = 5V 50 mA 15 pF U W POWER REQUIRE E TS The indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 5) SYMBOL PARAMETER CONDITIONS MIN TYP VDD Positive Supply Voltage 5.25 V IDD Positive Supply Current 280 310 mA PDIS Power Dissipation 1.4 1.55 W OVDD Digital Output Supply Voltage VDD V 4.75 0.5 MAX UNITS WU TI I G CHARACTERISTICS The indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. (Note 5) SYMBOL PARAMETER CONDITIONS MIN t0 ENC Period (Note 9) t1 ENC High (Note 8) t2 ENC Low (Note 8) t3 Aperture Delay (Note 8) t4 ENC to CLKOUT Falling CL = 10pF (Note 8) t5 ENC to CLKOUT Rising CL = 10pF (Note 8) TYP MAX UNITS 12.5 2000 ns 6 1000 ns 6 1000 ns 0 1 2.4 ns 4 t1 + t 4 ns ns For 80Msps 50% Duty Cycle CL = 10pF (Note 8) 7.25 8.65 10.25 ns t6 ENC to DATA Delay CL = 10pF (Note 8) 2 4.9 7.2 ns t7 ENC to DATA Delay (Hold Time) (Note 8) 1.4 3.4 4.7 ns t8 ENC to DATA Delay (Setup Time) CL = 10pF (Note 8) For 80Msps 50% Duty Cycle CL = 10pF (Note 8) 5.3 10.5 ns t9 CLKOUT to DATA Delay (Hold Time), 80Msps 50% Duty Cycle (Note 8) 6 ns t10 CLKOUT to DATA Delay (Setup Time), 80Msps 50% Duty Cycle CL = 10pF (Note 8) 2.1 ns t11 DATA Access Time After OE CL = 10pF (Note 8) 10 25 ns t12 BUS Relinquish (Note 8) 10 25 ns Data Latency t0 - t 6 7.6 5 ns cycles 1748fa 4 LTC1748 ELECTRICAL CHARACTERISTICS Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: All voltage values are with respect to GND (unless otherwise noted). Note 3: When these pin voltages are taken below GND or above VDD, they will be clamped by internal diodes. This product can handle input currents of greater than 100mA below GND or above VDD without latchup. Note 4: When these pin voltages are taken below GND, they will be clamped by internal diodes. This product can handle input currents of >100mA below GND without latchup. These pins are not clamped to VDD. Note 5: VDD = 5V, fSAMPLE = 80MHz, differential ENC/ENC = 2VP-P 80MHz sine wave, input range = 1.6V differential, unless otherwise specified. Note 6: Integral nonlinearity is defined as the deviation of a code from a straight line passing through the actual endpoints of the transfer curve. The deviation is measured from the center of the quantization band. Note 7: Bipolar offset is the offset voltage measured from - 0.5 LSB when the output code flickers between 00 0000 0000 0000 and 11 1111 1111 1111. Note 8: Guaranteed by design, not subject to test. Note 9: Recommended operating conditions. U W TYPICAL PERFOR A CE CHARACTERISTICS INL, 3.2V Range 2.5 DNL, 3.2V Range 1.0 TA = 25C 2.0 -20 0.6 1.0 0.5 0 -0.5 AMPLITUDE (dBFS) 0.4 ERROR (LSB) ERROR (LSB) 0 TA = 25C -10 TA = 25C 0.8 1.5 0.2 0 -0.2 -30 -40 -50 -60 -70 -80 -1.0 -0.4 -1.5 -0.6 -2.0 -0.8 -110 -2.5 -1.0 -120 0 4096 8192 12288 OUTPUT CODE -90 -100 0 16384 4096 12288 8192 OUTPUT CODE 1748 G01 16384 0 TA = 25C -10 -20 -30 -40 AMPLITUDE (dBFS) -20 -30 -40 AMPLITUDE (dBFS) -20 -80 -50 -60 -70 -80 -60 -80 -90 -100 -100 -100 -110 -110 -110 -120 -120 -120 10 15 20 25 30 FREQUENCY (MHz) 35 40 1748 G04 0 5 10 40 -70 -90 5 35 -50 -90 0 15 20 25 30 FREQUENCY (MHz) 0 TA = 25C -10 -30 -40 -70 10 8192 Point FFT, Input Frequency = 30.068MHz, -1dB, 3.2V Range 0 TA = 25C -10 -60 5 1748 G03 8192 Point FFT, Input Frequency = 15.068MHz, -20dB, 3.2V Range -50 0 1748 G02 8192 Point FFT, Input Frequency = 15.068MHz, -10dB, 3.2V Range AMPLITUDE (dBFS) 8192 Point FFT, Input Frequency = 15.068MHz, -1dB, 3.2V Range 15 20 25 30 FREQUENCY (MHz) 35 40 1748 G05 0 5 10 15 20 25 30 FREQUENCY (MHz) 35 40 1748 G06 1748fa 5 LTC1748 U W TYPICAL PERFOR A CE CHARACTERISTICS 8192 Point FFT, Input Frequency = 30.068MHz, -10dB, 3.2V Range 0 TA = 25C -10 0 TA = 25C -10 -20 -20 -30 -40 -30 -40 -50 -60 -70 -80 AMPLITUDE (dBFS) -20 -30 -40 AMPLITUDE (dBFS) AMPLITUDE (dBFS) 0 TA = 25C -10 -50 -60 -70 -80 -60 -70 -80 -90 -90 -100 -100 -100 -110 -110 -110 -120 -120 -120 0 5 10 15 20 25 30 FREQUENCY (MHz) 35 40 0 5 10 15 20 25 30 FREQUENCY (MHz) 1748 G07 35 40 AMPLITUDE (dBFS) -20 -30 -40 AMPLITUDE (dBFS) -20 -30 -40 -80 -50 -60 -70 -80 -60 -80 -90 -100 -100 -100 -110 -110 -110 -120 -120 -120 10 15 20 25 30 FREQUENCY (MHz) 35 40 0 5 10 15 20 25 30 FREQUENCY (MHz) 1748 G10 35 40 0 TA = 25C -10 -20 -30 -40 AMPLITUDE (dBFS) -20 -30 -40 AMPLITUDE (dBFS) -20 -80 -50 -60 -70 -80 -60 -80 -90 -100 -100 -100 -110 -110 -110 -120 -120 -120 10 15 20 25 30 FREQUENCY (MHz) 35 40 1748 G13 0 5 10 40 -70 -90 5 35 -50 -90 0 15 20 25 30 FREQUENCY (MHz) 0 TA = 25C -10 -30 -40 -70 10 8192 Point FFT, Input Frequency = 69.1MHz, -1dB, 3.2V Range 0 TA = 25C -10 -60 5 1748 G12 8192 Point FFT, Input Frequency = 50.64MHz, -20dB, 3.2V Range -50 0 1748 G11 8192 Point FFT, Input Frequency = 50.64MHz, -10dB, 3.2V Range 40 -70 -90 5 35 -50 -90 0 15 20 25 30 FREQUENCY (MHz) 0 TA = 25C -10 -20 -70 10 1748 G09 -30 -40 -60 5 8192 Point FFT, Input Frequency = 50.64MHz, -1dB, 3.2V Range 0 TA = 25C -10 -50 0 1748 G08 8192 Point FFT, Input Frequency = 40.64MHz, -20dB, 3.2V Range 0 TA = 25C -10 AMPLITUDE (dBFS) -50 -90 8192 Point FFT, Input Frequency = 40.64MHz, -10dB, 3.2V Range AMPLITUDE (dBFS) 8192 Point FFT, Input Frequency = 40.64MHz, -1dB, 3.2V Range 8192 Point FFT, Input Frequency = 30.068MHz, -20dB, 3.2V Range 15 20 25 30 FREQUENCY (MHz) 35 40 1748 G14 0 5 10 15 20 25 30 FREQUENCY (MHz) 35 40 1748 G15 1748fa 6 LTC1748 U W TYPICAL PERFOR A CE CHARACTERISTICS 8192 Point FFT, Input Frequency = 69.1MHz, -10dB, 3.2V Range 0 TA = 25C -10 0 TA = 25C -10 0 -10 -20 -20 -30 -40 -30 -40 -50 -60 -70 -80 AMPLITUDE (dBFS) -20 -30 -40 AMPLITUDE (dBFS) AMPLITUDE (dBFS) 8192 Point 2-Tone FFT, Input Frequency = 5MHz and 7MHz, -7dB, 3.2V Range 8192 Point FFT, Input Frequency = 69.1MHz, -20dB, 3.2V Range -50 -60 -70 -80 -60 -70 -80 -90 -90 -100 -100 -100 -110 -110 -110 -120 -120 -120 5 10 15 20 25 30 FREQUENCY (MHz) 35 40 0 5 10 15 20 25 30 FREQUENCY (MHz) 35 1748 G16 -20 -20 100 -30 -40 -30 -40 90 80 AMPLITUDE (dBFS) -70 -80 SFDR dBc AND dBFS 120 110 -60 -50 -60 -70 -80 30 20 -110 -110 10 -120 -120 35 40 0 5 10 15 20 25 30 FREQUENCY (MHz) 35 1748 G19 SFDR vs 50.3MHz Input Level TA = 25C dBFS 100 60 SFDR dBc AND dBFS 70 dBc 50 40 90 80 SFDR vs 70.3MHz Input Level 120 TA = 25C 110 100 dBFS 70 60 50 dBc 40 70 60 50 30 20 20 20 10 10 10 0 1748 G22 0 1748 G23 dBc 40 30 0 -80 -70 -60 -50 -40 -30 -20 -10 INPUT LEVEL (dBFS) dBFS 90 80 30 0 -80 -70 -60 -50 -40 -30 -20 -10 INPUT LEVEL (dBFS) 0 1748 G21 120 TA = 25C 110 90 80 dBc 0 -80 -70 -60 -50 -40 -30 -20 -10 INPUT LEVEL (dBFS) 40 SFDR dBc AND dBFS 100 TA = 25C 1748 G20 SFDR vs 30MHz Input Level 120 110 dBFS 40 -100 15 20 25 30 FREQUENCY (MHz) 40 35 50 -100 10 15 20 25 30 FREQUENCY (MHz) 60 -90 5 10 70 -90 0 5 SFDR vs 15MHz Input Level 0 TA = 25C -10 -50 0 1748 G18 8192 Point 2-Tone FFT, Input Frequency = 65MHz and 70MHz, -7dB, 3.2V Range 0 TA = 25C -10 AMPLITUDE (dBFS) 40 1748 G17 8192 Point 2-Tone FFT, Input Frequency = 25MHz and 30MHz, -7dB, 3.2V Range SFDR dBc AND dBFS -50 -90 0 TA = 25C 0 -80 -70 -60 -50 -40 -30 -20 -10 INPUT LEVEL (dBFS) 0 1748 G24 1748fa 7 LTC1748 U W TYPICAL PERFOR A CE CHARACTERISTICS SFDR vs Input Frequency and Amplitude, 2V Range, 2nd and 3rd Harmonic SFDR vs Input Frequency and Amplitude, 3.2V Range, 2nd and 3rd Harmonic 100 100 TA = 25C TA = 25C -20dB 95 -20dB 95 -10dB 14000 -6dB 80 -1dB 75 -1dB 80 65 65 60 0 20 40 80 60 INPUT FREQUENCY (MHz) 100 4000 2000 20 80 60 INPUT FREQUENCY (MHz) 0 40 8147 8148 8149 8150 8151 8152 8153 CODE 1748 G27 SNR vs Input Level and Frequency 3.2V Range 77.0 TA = 25C 77.5 76.8 77.0 76.6 SNR (dBFS) 76.5 76.0 75.5 SFDR vs Sample Rate, 5MHz Input, -1dB, 3.2V Range 100 TA = 25C 90 76.4 76.2 76.0 75.8 75.0 75.6 74.5 75.4 0 20 40 80 60 INPUT FREQUENCY (MHz) 75.2 -80 100 -60 75 65 -40 -20 60 0 0 20 40 80 60 SAMPLE RATE (Msps) 1748 G29 100 1748 G30 High Input Frequency SFDR, -1dB, 2V Range High Input Frequency SNR, -1dB, 2V Range 100 TA = 25C 73.0 4TH OR HIGHER HARMONIC 72.5 95 77 72.0 90 75 74 71.5 85 SNR (dBFS) SFDR (dBFS) 76 80 75 73 72 40 60 80 SAMPLE RATE (Msps) 100 1748 G31 71.0 70.5 70.0 2ND OR 3RD HARMONIC 70 20 80 INPUT LEVEL SNR vs Sample Rate, 5MHz Input, -1dB, 3.2V Range 0 85 70 15MHz 30MHz 50MHz 70MHz 1748 G28 78 TA = 25C 95 SFDR (dBFS) 78.0 0 100 1748 G26 SNR vs Input Frequency 3.2V Range SNR (dBFS) 8000 6000 70 1748 G25 SNR (dBFS) 10000 75 70 74.0 12000 85 COUNT SFDR (dBFS) SFDR (dBFS) -6dB 85 TA = 25C 16000 -10dB 90 90 60 Shorted Input Histogram 18000 69.5 65 69.0 60 68.5 0 50 100 200 150 INPUT FREQUENCY (MHz) 250 1748 G33 0 200 50 150 100 INPUT FREQUENCY (MHz) 250 1748 G34 1748fa 8 LTC1748 U W TYPICAL PERFOR A CE CHARACTERISTICS Offset and Gain Error vs Temperature Supply Current vs Sample Rate 300 8 6 TA = 25C 290 ERROR (LSB) 2 OFFSET ERROR 0 -2 -4 SUPPLY CURRENT (mA) GAIN ERROR 4 280 270 260 250 240 -6 -8 - 50 -30 230 50 30 10 TEMPERATURE (C) -10 70 90 0 20 40 60 80 100 SAMPLE RATE (Msps) 1748 G35 1748 G32 U U U PI FU CTIO S SENSE (Pin 1): Reference Sense Pin. Ground selects 1V. VDD selects 1.6V. Greater than 1V and less than 1.6V applied to the SENSE pin selects an input range of VSENSE, 1.6V is the largest valid input range. VCM (Pin 2): 2.35V Output and Input Common Mode Bias. Bypass to ground with 4.7F ceramic chip capacitor. GND (Pins 3, 6, 9, 12, 13, 16, 19, 21, 36, 37): ADC Power Ground. AIN+ (Pin 4): Positive Differential Analog Input. AIN- (Pin 5): Negative Differential Analog Input. VDD (Pins 7, 8, 17, 18, 20): 5V Supply. Bypass to AGND with 1F ceramic chip capacitors at Pin 8 and Pin 18. REFLB (Pin 10): ADC Low Reference. Bypass to Pin 11 with 0.1F ceramic chip capacitor. Do not connect to Pin 14. REFHA (Pin 11): ADC High Reference. Bypass to Pin 10 with 0.1F ceramic chip capacitor, to Pin 14 with a 4.7F ceramic capacitor and to ground with 1F ceramic capacitor. REFLA (Pin 14): ADC Low Reference. Bypass to Pin 15 with 0.1F ceramic chip capacitor, to Pin 11 with a 4.7F ceramic capacitor and to ground with 1F ceramic capacitor. REFHB (Pin 15): ADC High Reference. Bypass to Pin 14 with 0.1F ceramic chip capacitor. Do not connect to Pin 11. MSBINV (Pin 22): MSB Inversion Control. Low inverts the MSB, 2's complement output format. High does not invert the MSB, offset binary output format. ENC (Pin 23): Encode Input. The input sample starts on the positive edge. ENC (Pin 24): Encode Complement Input. Conversion starts on the negative edge. Bypass to ground with 0.1F ceramic for single-ended ENCODE signal. OE (Pin 25): Output Enable. Low enables outputs. Logic high makes outputs Hi-Z. OE should not exceed the votlage on OVDD. CLKOUT (Pin 26): Data Valid Output. Latch data on the rising edge of CLKOUT. OGND (Pins 27, 38, 47): Output Driver Ground. D0-D3 (Pins 28 to 31): Digital Outputs. OVDD (Pins 32, 43): Positive Supply for the Output Drivers. Bypass to ground with 0.1F ceramic chip capacitor. D4-D6 (Pins 33 to 35): Digital Outputs. D7-D10 (Pins 39 to 42): Digital Outputs. D11-D13 (Pins 44 to 46): Digital Outputs. OF (Pin 48): Over/Under Flow Output. High when an over or under flow has occurred. 1748fa 9 LTC1748 WU W TI I G DIAGRA N ANALOG INPUT * t3 t1 t2 t0 ENC t7 t8 DATA (N - 4) DB13 TO DB0 DATA (N - 5) DB13 TO DB0 DATA DATA (N - 3) t6 CLKOUT t4 t5 t10 t9 OE t11 t12 DATA N DB13 TO DB0, OF AND CLKOUT 1748 TD U W DATA U U APPLICATIO S I FOR ATIO DYNAMIC PERFORMANCE Signal-to-Noise Plus Distortion Ratio The signal-to-noise plus distortion ratio [S/(N + D)] is the ratio between the RMS amplitude of the fundamental input frequency and the RMS amplitude of all other frequency components at the ADC output. The output is band limited to frequencies above DC to below half the sampling frequency. Signal-to-Noise Ratio The signal-to-noise ratio (SNR) is the ratio between the RMS amplitude of the fundamental input frequency and the RMS amplitude of all other frequency components except the first five harmonics and DC. Total Harmonic Distortion Total harmonic distortion is the ratio of the RMS sum of all harmonics of the input signal to the fundamental itself. The out-of-band harmonics alias into the frequency band between DC and half the sampling frequency. THD is expressed as: THD = 20Log V22 + V32 + V 42 + ...Vn2 V1 where V1 is the RMS amplitude of the fundamental frequency and V2 through Vn are the amplitudes of the second through nth harmonics. The THD calculated in this data sheet uses all the harmonics up to the fifth. Intermodulation Distortion If the ADC input signal consists of more than one spectral component, the ADC transfer function nonlinearity can produce intermodulation distortion (IMD) in addition to THD. IMD is the change in one sinusoidal input caused by the presence of another sinusoidal input at a different frequency. If two pure sine waves of frequencies fa and fb are applied to the ADC input, nonlinearities in the ADC transfer function can create distortion products at the sum and difference frequencies of mfa nfb, where m and n = 0, 1, 2, 3, etc. The 3rd order intermodulation products are 2fa + fb, 2fb + fa, 2fa - fb and 2fb - fa. The intermodulation distortion is defined as the ratio of the RMS value of either input tone to the RMS value of the largest 3rd order intermodulation product. 1748fa 10 LTC1748 U W U U APPLICATIO S I FOR ATIO Spurious Free Dynamic Range (SFDR) when sampling an AC input. The signal to noise ratio due to the jitter alone will be: Spurious free dynamic range is the peak harmonic or spurious noise that is the largest spectral component excluding the input signal and DC. This value is expressed in decibels relative to the RMS value of a full scale input signal. SNRJITTER = -20log (2) * FIN * TJITTER CONVERTER OPERATION The LTC1748 is a CMOS pipelined multistep converter. The converter has four pipelined ADC stages; a sampled analog input will result in a digitized value five cycles later, see the Timing Diagram section. The analog input is differential for improved common mode noise immunity and to maximize the input range. Additionally, the differential input drive will reduce even order harmonics of the sample-and-hold circuit. The encode input is also differential for improved common mode noise immunity. Input Bandwidth The input bandwidth is that input frequency at which the amplitude of the reconstructed fundamental is reduced by 3dB for a full scale input signal. Aperture Delay Time The time from when a rising ENC equals the ENC voltage to the instant that the input signal is held by the sample and hold circuit. The LTC1748 has two phases of operation, determined by the state of the differential ENC/ENC input pins. For brevity, the text will refer to ENC greater than ENC as ENC high and ENC less than ENC as ENC low. Aperture Delay Jitter The variation in the aperture delay time from conversion to conversion. This random variation will result in noise Each pipelined stage shown in Figure 1 contains an ADC, a reconstruction DAC and an interstage residue amplifier. AIN+ AIN- VCM FIRST PIPELINED ADC STAGE (5 BITS) INPUT S/H SECOND PIPELINED ADC STAGE (4 BITS) THIRD PIPELINED ADC STAGE (4 BITS) FOURTH PIPELINED ADC STAGE (4 BITS) 2.35V REFERENCE 4.7F SHIFT REGISTER AND CORRECTION RANGE SELECT REFL SENSE REFH INTERNAL CLOCK SIGNALS OVDD 0.5V TO 5V OF REF BUF DIFFERENTIAL INPUT LOW JITTER CLOCK DRIVER DIFF REF AMP D13 CONTROL LOGIC AND CALIBRATION LOGIC OUTPUT DRIVERS D0 CLKOUT 1748 F01 REFLB REFHA 4.7F 0.1F 1F REFLA REFHB ENC ENC MSBINV OE OGND 0.1F 1F Figure 1. Functional Block Diagram 1748fa 11 LTC1748 U W U U APPLICATIO S I FOR ATIO In operation, the ADC quantizes the input to the stage and the quantized value is subtracted from the input by the DAC to produce a residue. The residue is amplified and output by the residue amplifier. Successive stages operate out of phase so that when the odd stages are outputting their residue, the even stages are acquiring that residue and visa versa. When ENC is low, the analog input is sampled differentially directly onto the input sample-and-hold capacitors, inside the "Input S/H" shown in the block diagram. At the instant that ENC transitions from low to high, the sampled input is held. While ENC is high, the held input voltage is buffered by the S/H amplifier which drives the first pipelined ADC stage. The first stage acquires the output of the S/H during this high phase of ENC. When ENC goes back low, the first stage produces its residue which is acquired by the second stage. At the same time, the input S/H goes back to acquiring the analog input. When ENC goes back high, the second stage produces its residue which is acquired by the third stage. An identical process is repeated for the third stage, resulting in a third stage residue that is sent to the fourth stage ADC for final evaluation. Each ADC stage following the first has additional range to accommodate flash and amplifier offset errors. Results from all of the ADC stages are digitally synchronized such that the results can be properly combined in the correction logic before being sent to the output buffer. SAMPLE/HOLD OPERATION AND INPUT DRIVE Sample/Hold Operation Figure 2 shows an equivalent circuit for the LTC1748 CMOS differential sample-and-hold. The differential analog inputs are sampled directly onto sampling capacitors (CSAMPLE) through CMOS transmission gates. This direct capacitor sampling results in lowest possible noise for a given sampling capacitor size. The capacitors shown attached to each input (CPARASITIC) are the summation of all other capacitance associated with each input. During the sample phase when ENC/ENC is low, the transmission gate connects the analog inputs to the sampling capacitors and they charge to, and track the differential input voltage. When ENC/ENC transitions from low to LTC1748 VDD CSAMPLE 4pF AIN+ CPARASITIC 4pF VDD CSAMPLE 4pF AIN- CPARASITIC 4pF 5V BIAS 2V 6k ENC ENC 6k 2V 1748 F02 Figure 2. Equivalent Input Circuit high the sampled input voltage is held on the sampling capacitors. During the hold phase when ENC/ENC is high the sampling capacitors are disconnected from the input and the held voltage is passed to the ADC core for processing. As ENC/ENC transitions from high to low the inputs are reconnected to the sampling capacitors to acquire a new sample. Since the sampling capacitors still hold the previous sample, a charging glitch proportional to the change in voltage between samples will be seen at this time. If the change between the last sample and the new sample is small the charging glitch seen at the input will be small. If the input change is large, such as the change seen with input frequencies near Nyquist, then a larger charging glitch will be seen. Common Mode Bias The ADC sample-and-hold circuit requires differential drive to achieve specified performance. Each input should swing 0.8V for the 3.2V range or 0.5V for the 2V range, around a common mode voltage of 2.35V. The VCM output pin (Pin 2) may be used to provide the common mode bias level. VCM can be tied directly to the center tap of a transformer to set the DC input level or as a reference level to an op amp differential driver circuit. The VCM pin must be bypassed to ground close to the ADC with a 4.7F or greater capacitor. 1748fa 12 LTC1748 U W U U APPLICATIO S I FOR ATIO Input Drive Impedance As with all high performance, high speed ADCs the dynamic performance of the LTC1748 can be influenced by the input drive circuitry, particularly the second and third harmonics. Source impedance and input reactance can influence SFDR. At the falling edge of encode the sampleand-hold circuit will connect the 4pF sampling capacitor to the input pin and start the sampling period. The sampling period ends when encode rises, holding the sampled input on the sampling capacitor. Ideally the input circuitry should be fast enough to fully charge the sampling capacitor during the sampling period 1/(2FENCODE); however, this is not always possible and the incomplete settling may degrade the SFDR. The sampling glitch has been designed to be as linear as possible to minimize the effects of incomplete settling. For the best performance, it is recomended to have a source impedence of 100 or less for each input. The S/H circuit is optimized for a 50 source impedance. If the source impedance is less than 50, a series resistor should be added to increase this impedance to 50. The source impedence should be matched for the differential inputs. Poor matching will result in higher even order harmonics, especially the second. Input Drive Circuits Figure 3 shows the LTC1748 being driven by an RF transformer with a center tapped secondary. The secondary center tap is DC biased with VCM, setting the ADC input signal at its optimum DC level. Figure 3 shows a 1:1 turns ratio transformer. Other turns ratios can be used if the source impedence seen by the ADC does not exceed 100 for each ADC input. A disadvantage of using a transformer is the loss of low frequency response. Most small RF transformers have poor performance at frequencies below 1MHz. Figure 4 demonstrates the use of operational amplifiers to convert a single ended input signal into a differential input signal. The advantage of this method is that it provides low frequency input response; however, the limited gain bandwidth of most op amps will limit the SFDR at high input frequencies. The 25 resistors and 12pF capacitors on the analog inputs serve two purposes: isolating the drive circuitry from the sample-and-hold charging glitches and limiting the wideband noise at the converter input. For input frequencies higher than 100MHz, the capacitors may need to be decreased to prevent excessive signal loss. Reference Operation Figure 5 shows the LTC1748 reference circuitry consisting of a 2.35V bandgap reference, a difference amplifier and switching and control circuit. The internal voltage reference can be configured for two pin selectable input ranges of 2V(1V differential) or 3.2V(1.6V differential). Tying the SENSE pin to ground selects the 2V range; tying the SENSE pin to VDD selects the 3.2V range. The 2.35V bandgap reference serves two functions: its output provides a DC bias point for setting the common VCM 4.7F 5V SINGLE-ENDED INPUT 2.35V 1/2 RANGE VCM 0.1F 1:1 100 25 100 25 12pF 12pF 25 1/2 LT1810 4.7F ANALOG INPUT 12pF + 25 AIN+ - LTC1748 12pF 25 AIN+ LTC1748 100 25 AIN- + 25 1/2 LT1810 - 12pF 500 25 AIN- 12pF 500 1748 F04 1748 F03 Figure 3. Single-Ended to Differential Conversion Using a Transformer Figure 4. Differential Drive with Op Amps 1748fa 13 LTC1748 U W U U APPLICATIO S I FOR ATIO mode voltage of any external input circuitry; additionally, the reference is used with a difference amplifier to generate the differential reference levels needed by the internal ADC circuitry. VDD. The SENSE pin should be tied high or low as close to the converter as possible. If the SENSE pin is driven externally, it should be bypassed to ground as close to the device as possible with a 1F ceramic capacitor. An external bypass capacitor is required for the 2.35V reference output, VCM. This provides a high frequency low impedance path to ground for internal and external circuitry. This is also the compensation capacitor for the reference. It will not be stable without this capacitor. Input Range The difference amplifier generates the high and low reference for the ADC. High speed switching circuits are connected to these outputs and they must be externally bypassed. Each output has two pins: REFHA and REFHB for the high reference and REFLA and REFLB for the low reference. The doubled output pins are needed to reduce package inductance. Bypass capacitors must be connected as shown in Figure 5. Other voltage ranges in between the pin selectable ranges can be programmed with two external resistors as shown in Figure 6a. An external reference can be used by applying its output directly or through a resistor divider to SENSE. It is not recommended to drive the SENSE pin with a logic device since the logic threshold is close to ground and The input range can be set based on the application. For oversampled signal processing in which the input frequency is low (<10MHz), the largest input range will provide the best signal-to-noise performance while maintaining excellent SFDR. For high input frequencies (> 40MHz), the 2V range will have the best SFDR performance for the 2nd and 3rd harmonics, but the SNR will degrade by 3.5dB. See the Typical Performance Characteristics section. Driving the Encode Inputs The noise performance of the LTC1748 can depend on the encode signal quality as much as on the analog input. The ENC/ENC inputs are intended to be driven differentially, primarily for noise immunity from common mode noise sources. Each input is biased through a 6k resistor to a 2V bias. The bias resistors set the DC operating point for transformer coupled drive circuits and can set the logic threshold for single-ended drive circuits. LTC1748 VCM 2.35V 4 2.35V BANDGAP REFERENCE VCM 2.35V 4.7F 1.6V TIE TO VDD FOR 3.2V RANGE; TIE TO GND FOR 2V RANGE; RANGE = 2 * VSENSE FOR 1V < VSENSE < 1.6V 1F 4.7F 1V 12.5k 1.1V RANGE DETECT AND CONTROL LTC1748 SENSE 1F 11k SENSE 1748 F06a REFLB 0.1F REFHA BUFFER INTERNAL ADC HIGH REFERENCE Figure 6a. 2.2V Range ADC 2.35V 4.7F 4.7F DIFF AMP 1F REFLA 0.1F REFHB VCM 5V 0.1F INTERNAL ADC LOW REFERENCE 4 LT1790-1.25 1, 2 6 1.25V SENSE LTC1748 1F 1748 F06b 1748 F05 Figure 5. Equivalent Reference Circuit Figure 6b. 2.5V Range ADC with External Reference 1748fa 14 LTC1748 U W U U APPLICATIO S I FOR ATIO LTC1748 5V BIAS VDD ANALOG INPUT TO INTERNAL ADC CIRCUITS 2V BIAS 6k ENC 0.1F 1:4 CLOCK INPUT 50 VDD 2V BIAS 6k ENC 1748 F07 Figure 7. Transformer Driven ENC/ENC 3.3V MC100LVELT22 ENC VTHRESHOLD = 2V 3.3V 130 Q0 ENC D0 2V ENC 130 LTC1748 0.1F ENC Q0 83 LTC1748 83 1748 F08a 1748 F08b Figure 8a. Single-Ended ENC Drive, Not Recommended for Low Jitter Figure 8b. ENC Drive Using a CMOS-to-PECL Translator Any noise present on the encode signal will result in additional aperture jitter that will be RMS summed with the inherent ADC aperture jitter. The encode inputs have a common mode range of 1.8V to VDD. Each input may be driven from ground to VDD for single-ended drive. In applications where jitter is critical (high input frequencies) take the following into consideration: Maximum and Minimum Encode Rates 1. Differential drive should be used. 2. Use as large an amplitude as possible; if transformer coupled use a higher turns ratio to increase the amplitude. 3. If the ADC is clocked with a sinusoidal signal, filter the encode signal to reduce wideband noise. 4. Balance the capacitance and series resistance at both encode inputs so that any coupled noise will appear at both inputs as common mode noise. The maximum encode rate for the LTC1748 is 80Msps. For the ADC to operate properly the encode signal should have a 50% (4%) duty cycle. Each half cycle must have at least 6ns for the ADC internal circuitry to have enough settling time for proper operation. Achieving a precise 50% duty cycle is easy with differential sinusoidal drive using a transformer or using symmetric differential logic such as PECL or LVDS. When using a single-ended encode signal asymmetric rise and fall times can result in duty cycles that are far from 50%. 1748fa 15 LTC1748 U W U U APPLICATIO S I FOR ATIO At sample rates slower than 80Msps the duty cycle can vary from 50% as long as each half cycle is at least 6ns. output may be used but is not required since the ADC has a series resistor of 43 on chip. The lower limit of the LTC1748 sample rate is determined by droop of the sample-and-hold circuits. The pipelined architecture of this ADC relies on storing analog signals on small valued capacitors. Junction leakage will discharge the capacitors. The specified minimum operating frequency for the LTC1748 is 1Msps. Lower OVDD voltages will also help reduce interference from the digital outputs. Format The LTC1748 parallel digital output can be selected for offset binary or 2's complement format. The format is selected with the MSBINV pin; high selects offset binary. DIGITAL OUTPUTS Overflow Bit Digital Output Buffers Figure 9 shows an equivalent circuit for a single output buffer. Each buffer is powered by OVDD and OGND, isolated from the ADC power and ground. The additional N-channel transistor in the output driver allows operation down to low voltages. The internal resistor in series with the output makes the output appear as 50 to external circuitry and may eliminate the need for external damping resistors. Output Loading As with all high speed/high resolution converters the digital output loading can affect the performance. The digital outputs of the LTC1748 should drive a minimal capacitive load to avoid possible interaction between the digital outputs and sensitive input circuitry. The output should be buffered with a device such as an ALVCH16373 CMOS latch. For full speed operation the capacitive load should be kept under 10pF. A resistor in series with the An overflow output bit indicates when the converter is overranged or underranged. When OF outputs a logic high the converter is either overranged or underranged. Output Clock The ADC has a delayed version of the ENC input available as a digital output, CLKOUT. The CLKOUT pin can be used to synchronize the converter data to the digital system. This is necessary when using a sinusoidal encode. Data will be updated just after CLKOUT falls and can be latched on the rising edge of CLKOUT. Output Driver Power Separate output power and ground pins allow the output drivers to be isolated from the analog circuitry. The power supply for the digital output buffers, OVDD, should be tied to the same power supply as for the logic being driven. For example if the converter is driving a DSP powered by a 3V supply then OVDD should be tied to that same 3V supply. LTC1748 VDD OVDD VDD 0.5V TO VDD 0.1F OVDD DATA FROM LATCH PREDRIVER LOGIC 43 TYPICAL DATA OUTPUT OE OGND 1748 F09 Figure 9. Equivalent Circuit for a Digital Output Buffer 1748fa 16 LTC1748 U W U U APPLICATIO S I FOR ATIO OVDD can be powered with any voltage up to 5V. The logic outputs will swing between OGND and OVDD. Output Enable The outputs may be disabled with the output enable pin, OE. OE low disables all data outputs including OF and CLKOUT. The data access and bus relinquish times are too slow to allow the outputs to be enabled and disabled during full speed operation. The output Hi-Z state is intended for use during long periods of inactivity. The voltage on OE can swing between GND and OVDD. OE should not be driven above OVDD. GROUNDING AND BYPASSING The LTC1748 requires a printed circuit board with a clean unbroken ground plane. A multilayer board with an internal ground plane is recommended. The pinout of the LTC1748 has been optimized for a flowthrough layout so that the interaction between inputs and digital outputs is minimized. Layout for the printed circuit board should ensure that digital and analog signal lines are separated as much as possible. In particular, care should be taken not to run any digital track alongside an analog signal track or underneath the ADC. High quality ceramic bypass capacitors should be used at the VDD, VCM, REFHA, REFHB, REFLA and REFLB pins as shown in the block diagram on the front page of this data sheet. Bypass capacitors must be located as close to the pins as possible. Of particular importance are the capacitors between REFHA and REFLB and between REFHB and REFLA. These capacitors should be as close to the device as possible (1.5mm or less). Size 0402 ceramic capacitors are recomended. The large 4.7F capacitor between REFHA and REFLA can be somewhat further away. The traces connecting the pins and bypass capacitors must be kept short and should be made as wide as possible. The LTC1748 differential inputs should run parallel and close to each other. The input traces should be as short as possible to minimize capacitance and to minimize noise pickup. An analog ground plane separate from the digital processing system ground should be used. All ADC ground pins labeled GND should connect to this plane. All ADC VDD bypass capacitors, reference bypass capacitors and input filter capacitors should connect to this analog plane. The LTC1748 has three output driver ground pins, labeled OGND (Pins 27, 38 and 47). These grounds should connect to the digital processing system ground. The output driver supply, OVDD should be connected to the digital processing system supply. OVDD bypass capacitors should bypass to the digital system ground. The digital processing system ground should be connected to the analog plane at ADC OGND (Pin 38). HEAT TRANSFER Most of the heat generated by the LTC1748 is transferred from the die through the package leads onto the printed circuit board. In particular, ground pins 12, 13, 36 and 37 are fused to the die attach pad. These pins have the lowest thermal resistance between the die and the outside environment. It is critical that all ground pins are connected to a ground plane of sufficient area. The layout of the evaluation circuit shown on the following pages has a low thermal resistance path to the internal ground plane by using multiple vias near the ground pins. A ground plane of this size results in a thermal resistance from the die to ambient of 35C/W. Smaller area ground planes or poorly connected ground pins will result in higher thermal resistance. 1748fa 17 18 E3 GND 8 E4 GND Y1 11 E5 GND JP1 R6 200 C31 0.1F C30 5V 0.1F 14 * C29 1F * C2 0.1F * R1** 0 JP3 C5 12pF C15 0.1F JP4 C14 4.7F C27 0.1F C9 0.1F C26 0.1F RY* RX* C3 10F C18 R B 4.7F 24.9 C13 0.1F C8 4.7F C7 0.1F C24 12pF RA 24.9 INPUT TWOS RANGE COMPLEMENT SELECT SELECT C32 30pF 5V R22 100 C8 4.7F C25 12pF R10** 0 R7 24.9 R4 100 R2 24.9 C11 1F T2 MINICIRCUITS T1-1T * R21 100 JP5 OPTIONAL XTAL CLK R3 100 T1 MINICIRCUITS T1-1T *RX, RY = OPTIONAL INPUT RANGE SET **DO NOT INSTALL R1 AND R10 C17 0.1F 7 4 1 J5 ENCODE INPUT J4 OPTIONAL - INPUT J3 ANALOG INPUT J1 OPTIONAL +INPUT R8 0 5V 4 3 OUT 24 23 22 21 20 19 18 17 16 15 14 13 12 11 10 9 8 7 6 5 4 3 2 1 C1 2F SENSE ENC ENC MSBINV GND VDD GND VDD VDD GND REFHB REFLA GND GND REFHA REFLB GND VDD VDD GND AIN- AIN+ GND VCM 2 1 OF 25 26 27 28 29 30 31 32 33 34 35 36 37 38 39 40 41 42 43 44 45 46 47 48 C4 4.7F C16 10F OE CLKOUT OGND D0 D1 D2 D3 OVDD D4 D5 D6 GND GND OGND D7 D8 D9 D10 OVDD D11 D12 D13 OGND U5 LTC1748 TAB GND IN U3 LT1521-3 E4 PGND E1 5V C10 0.1F C12 0.1F C23 0.1F 1LE 1D1 1D2 GND 1D3 1D4 VCC 1D5 1D6 GND 1D7 1D8 2D1 2D2 GND 2D3 2D4 VCC 2D5 2D6 GND 2D7 2D8 2LE C19 0.1F 48 47 46 45 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 C20 0.1F 1OE 1Q1 1Q2 GND 1Q3 1Q4 VCC 1Q5 1Q6 GND 1Q7 1Q8 2Q1 2Q2 GND 2Q3 2Q4 VCC 2Q5 2Q6 GND 2Q7 2Q8 2OE U4 P174VCX16373V 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 CLKOUT CLKOUT 3V JP2 C21 0.1F RN8C 33 RN8B 33 RN8A 33 RN7D 33 RN7C 33 RN7B 33 RN7A 33 RN6D 33 RN6C 33 RN6B 33 RN6A 33 RN5D 33 RN5C 33 RN5B 33 RN5A 33 1748 TA01 C22 0.1F U2 10T74ALVC1G86 3V C28 0.1F R9 33 1 3 5 7 9 11 13 15 17 19 21 23 25 27 29 31 33 35 37 39 2 4 6 8 10 12 14 16 18 20 22 24 26 28 30 32 34 36 38 40 J2 3201S-40G1 U U W R5 1 APPLICATIO S I FOR ATIO U Evaluation Circuit Schematic of the LTC1748 LTC1748 1748fa LTC1748 U W U U APPLICATIO S I FOR ATIO Silkscreen Top Layer 1 Component Side Layer 2 GND Plane Layer 3 Power Plane Layer 4 Solder Side 1748fa Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LTC1748 U PACKAGE DESCRIPTIO FW Package 48-Lead Plastic TSSOP (6.1mm) (Reference LTC DWG # 05-08-1651) 12.4 - 12.6* (.488 - .496) 0.95 0.10 8.1 0.10 48 47 46 45 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 6.2 0.10 7.9 - 8.3 (.311 - .327) 0.32 0.05 0.50 TYP 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 RECOMMENDED SOLDER PAD LAYOUT 1.20 (.0473) MAX 6.0 - 6.2** (.236 - .244) 0 - 8 -T.10 C -C0.09 - 0.20 (.0035 - .008) 0.45 - 0.75 (.018 - .029) 0.50 (.0197) BSC 0.17 - 0.27 (.0067 - .0106) 0.05 - 0.15 (.002 - .006) FW48 TSSOP 0502 NOTE: 1. CONTROLLING DIMENSION: MILLIMETERS MILLIMETERS 2. DIMENSIONS ARE IN (INCHES) 3. DRAWING NOT TO SCALE *DIMENSIONS DO NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED .152mm (.006") PER SIDE **DIMENSIONS DO NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED .254mm (.010") PER SIDE RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LTC1405 12-Bit, 5Msps Sampling ADC with Parallel Output Pin Compatible with the LTC1420 LTC1406 8-Bit, 20Msps ADC Undersampling Capability up to 70MHz LTC1411 14-Bit, 2.5Msps ADC 5V, No Pipeline Delay, 80dB SINAD LTC1412 12-Bit, 3Msps, Sampling ADC 5V, No Pipeline Delay, 72dB SINAD LTC1414 14-Bit, 2.2Msps ADC 5V, 81dB SINAD and 95dB SFDR LTC1420 12-Bit, 10Msps ADC 71dB SINAD and 83dB SFDR at Nyquist LTC1461 Micropower Precision Series Reference 0.04% Max Initial Accuracy, 3ppm/C Drift LTC1666 12-Bit, 50Msps DAC Pin Compatible with the LTC1668, LTC1667 LTC1667 14-Bit, 50Msps DAC Pin Compatible with the LTC1668, LTC1666 LTC1668 16-Bit, 50Msps DAC 16-Bit, No Missing Codes, 90dB SINAD, -100dB THD LTC1741 12-Bit, 65Msps ADC Pin Compatible with the LTC1748 LTC1742 14-Bit, 65Msps ADC Pin Compatible with the LTC1748 LTC1743 12-Bit, 50Msps ADC Pin Compatible with the LTC1748 LTC1744 14-Bit, 50Msps ADC Pin Compatible with the LTC1748 LTC1745 12-Bit, 25Msps ADC Pin Compatible with the LTC1748 LTC1746 14-Bit, 25Msps ADC Pin Compatible with the LTC1748 LTC1747 12-Bit, 80Msps ADC Pin Compatible with the LTC1748 LT(R)1807 325MHz, Low Distortion Dual Op Amp Rail-to-Rail Input and Output 1748fa 20 Linear Technology Corporation LT/TP 1103 1K REV A * PRINTED IN THE USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 FAX: (408) 434-0507 www.linear.com LINEAR TECHNOLOGY CORPORATION 2003