LMH6715
LMH6715 Dual Wideband Video Op Amp
Literature Number: SNOSA10B
LMH6715
Dual Wideband Video Op Amp
General Description
The LMH6715 combines National’s VIP10™high speed
complementary bipolar process with National’s current feed-
back topology to produce a very high speed dual op amp.
The LMH6715 provides 400MHz small signal bandwidth at a
gain of +2V/V and 1300V/µs slew rate while consuming only
5.8mA per amplifier from ±5V supplies.
The LMH6715 offers exceptional video performance with its
0.02% and 0.02˚ differential gain and phase errors for NTSC
and PAL video signals while driving up to four back termi-
nated 75Ωloads. The LMH6715 also offers a flat gain re-
sponse of 0.1dB to 100MHz and very low channel-to-
channel crosstalk of −70dB at 10MHz. Additionally, each
amplifier can deliver 70mA of output current. This level of
performance makes the LMH6715 an ideal dual op amp for
high density, broadcast quality video systems.
The LMH6715’s two very well matched amplifiers support a
number of applications such as differential line drivers and
receivers. In addition, the LMH6715 is well suited for Sallen
Key active filters in applications such as anti-aliasing filters
for high speed A/D converters. Its small 8-pin SOIC package,
low power requirement, low noise and distortion allow the
LMH6715 to serve portable RF applications such as IQ
channels.
Features
T
A
= 25˚C, R
L
= 100Ω, typical values unless specified.
nVery low diff. gain, phase: 0.02%, 0.02˚
nWide bandwidth: 480MHz (A
V
= +1V/V); 400MHz (A
V
=
+2V/V)
n0.1dB gain flatness to 100MHz
nLow power: 5.8mA/channel
n−70dB channel-to-channel crosstalk (10MHz)
nFast slew rate: 1300V/µs
nUnity gain stable
nImproved replacement for CLC412
Applications
nHDTV, NTSC & PAL video systems
nVideo switching and distribution
nIQ amplifiers
nWideband active filters
nCable drivers
nDC coupled single-to-differential conversions
Differential Gain & Phase with
Multiple Video Loads
20042908
Frequency Response vs. V
OUT
20042916
January 2003
LMH6715 Dual Wideband Video Op Amp
© 2003 National Semiconductor Corporation DS200429 www.national.com
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance (Note 4)
Human Body Model 2000V
Machine Model 150V
V
CC
±6.75V
I
OUT
(Note 3)
Common-Mode Input Voltage ±V
CC
Differential Input Voltage 2.2V
Maximum Junction Temperature +150˚C
Storage Temperature Range −65˚C to +150˚C
Lead Temperature (Soldering 10
sec)
+300˚C
Operating Ratings
Thermal Resistance
Package (θ
JC
)(θ
JA
)
SOIC 65˚C/W 145˚C/W
Operating Temperature Range −40˚C to +85˚C
Nominal Operating Voltage ±5V to ±6V
Electrical Characteristics
A
V
= +2, R
F
= 500Ω,V
CC
=±5V,R
L
= 100Ω; unless otherwise specified. Boldface limits apply at the temperature extremes.
Symbol Parameter Conditions Min Typ Max Units
Frequency Domain Response
SSBW -3dB Bandwidth V
OUT
<0.5V
PP
,R
F
= 300Ω280 400 MHz
LSBW -3dB Bandwidth V
OUT
<4.0V
PP
,R
F
= 300Ω170 MHz
Gain Flatness V
OUT
<0.5V
PP
GFP Peaking DC to 100MHz, R
F
= 300Ω0.1 dB
GFR Rolloff DC to 100MHz, R
F
= 300Ω0.1 dB
LPD Linear Phase Deviation DC to 100MHz, R
F
= 300Ω0.25 deg
DG Differential Gain R
L
= 150Ω, 4.43MHz 0.02 %
DP Differential Phase R
L
= 150Ω, 4.43MHz 0.02 deg
Time Domain Response
Tr Rise and Fall Time 0.5V Step 1.4 ns
4V Step 3 ns
Ts Settling Time to 0.05% 2V Step 12 ns
OS Overshoot 0.5V Step 1 %
SR Slew Rate 2V Step 1300 V/µs
Distortion And Noise Response
HD2 2nd Harmonic Distortion 2V
PP
, 20MHz −60 dBc
HD3 3rd Harmonic Distortion 2V
PP
, 20MHz −75 dBc
Equivalent Input Noise
V
N
Non-Inverting Voltage >1MHz 3.4 nV/
I
N
Inverting Current >1MHz 10.0 pA/
I
NN
Non-Inverting Current >1MHz 1.4 pA/
SNF Noise Floor >1MHz −153 dB
1Hz
XTLKA Crosstalk Input Referred 10MHz −70 dB
Static, DC Performance
V
IO
Input Offset Voltage ±2±6
±8
mV
DV
IO
Average Drift ±30 µV/˚C
I
BN
Input Bias Current Non-Inverting ±5±12
±20
µA
DI
BN
Average Drift ±30 nA/˚C
I
BI
Input Bias Current Inverting ±6±21
±35
µA
DI
BI
Average Drift ±20 nA/˚C
PSRR Power Supply Rejection Ratio DC 46
44
60 dB
LMH6715
www.national.com 2
Electrical Characteristics (Continued)
A
V
= +2, R
F
= 500Ω,V
CC
=±5V,R
L
= 100Ω; unless otherwise specified. Boldface limits apply at the temperature extremes.
Symbol Parameter Conditions Min Typ Max Units
CMRR Common Mode Rejection Ratio DC 50
47
56 dB
I
CC
Supply Current per Amplifier R
L
=∞4.7
4.1
5.8 7.6
8.1
mA
Miscellaneous Performance
R
IN
Input Resistance Non-Inverting 1000 kΩ
C
IN
Input Capacitance Non-Inverting 1.0 pF
R
OUT
Output Resistance Closed Loop .06 Ω
V
O
Output Voltage Range R
L
=∞±4.0 V
V
OL
R
L
= 100Ω±3.5
±3.4
±3.9 V
CMIR Input Voltage Range Common Mode ±2.2 V
I
O
Output Current 70 mA
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications, see the Electrical Characteristics tables.
Note 2: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of
the device such that TJ=T
A. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self heating where TJ>TA.
See Applications Section for information on temperature de-rating of this device." Min/Max ratings are based on product characterization and simulation. Individual
parameters are tested as noted.
Note 3: The maximum output current (IOUT) is determined by device power dissipation limitations. See the Power Dissipation section of the Application Division for
more details.
Note 4: Human body model, 1.5kΩin series with 100pF. Machine model, 0ΩIn series with 200pF.
Connection Diagram
8-Pin SOIC
20042904
Top View
Ordering Information
Package Part Number Package Marking Transport Media NSC Drawing
8-pin SOIC LMH6715MA LMH6715MA Rails M08A
LMH6715MAX 2.5k Units Tape and Reel
LMH6715
www.national.com3
Typical Performance Characteristics (T
A
= 25˚C, V
CC
=±5V, A
V
=±2V/V, R
F
= 500Ω,R
L
=
100Ω, unless otherwise specified).
Non-Inverting Frequency Response Inverting Frequency Response
20042913 20042912
Non-Inverting Frequency Response vs. V
OUT
Small Signal Channel Matching
20042916 20042901
Frequency Response vs. Load Resistance Non-Inverting Frequency Response vs. R
F
20042915 20042914
LMH6715
www.national.com 4
Typical Performance Characteristics (T
A
= 25˚C, V
CC
=±5V, A
V
=±2V/V, R
F
= 500Ω,R
L
= 100Ω,
unless otherwise specified). (Continued)
Small Signal Pulse Response Large Signal Pulse Response
20042918 20042919
Input-Referred Crosstalk Settling Time vs. Accuracy
20042907 20042924
−3dB Bandwidth vs. V
OUT
DC Errors vs. Temperature
20042925 20042926
LMH6715
www.national.com5
Typical Performance Characteristics (T
A
= 25˚C, V
CC
=±5V, A
V
=±2V/V, R
F
= 500Ω,R
L
= 100Ω,
unless otherwise specified). (Continued)
Open Loop Transimpedance, Z(s) Equivalent Input Noise vs. Frequency
20042920 20042923
Differential Gain & Phase vs. Load Differential Gain vs. Frequency
20042908 20042909
Differential Phase vs. Frequency Gain Flatness & Linear Phase Deviation
20042910 20042911
LMH6715
www.national.com 6
Typical Performance Characteristics (T
A
= 25˚C, V
CC
=±5V, A
V
=±2V/V, R
F
= 500Ω,R
L
= 100Ω,
unless otherwise specified). (Continued)
2nd Harmonic Distortion vs. Output Voltage 3rd Harmonic Distortion vs. Output Voltage
20042902 20042905
Closed Loop Output Resistance PSRR & CMRR
20042906 20042917
Suggested R
S
vs. C
L
20042927
LMH6715
www.national.com7
Application Section
Application Introduction
Offered in an 8-pin package for reduced space and cost, the
wideband LMH6715 dual current-feedback op amp provides
closely matched DC and AC electrical performance charac-
teristics making the part an ideal choice for wideband signal
processing. Applications such as broadcast quality video
systems, IQ amplifiers, filter blocks, high speed peak detec-
tors, integrators and transimedance amplifiers will all find
superior performance in the LMH6715 dual op amp.
FEEDBACK RESISTOR SELECTION
One of the key benefits of a current feedback operational
amplifier is the ability to maintain optimum frequency re-
sponse independent of gain by using appropriate values for
the feedback resistor (R
F
). The Electrical Characteristics and
Typical Performance plots specify an R
F
of 500Ω, a gain of
+2V/V and ±5V power supplies (unless otherwise specified).
Generally, lowering R
F
from it’s recommended value will
peak the frequency response and extend the bandwidth
while increasing the value of R
F
will cause the frequency
response to roll off faster. Reducing the value of R
F
too far
below it’s recommended value will cause overshoot, ringing
and, eventually, oscillation.
Frequency Response vs. R
F
20042914
The plot labeled “Frequency Response vs. R
F
” shows the
LMH6715’s frequency response as R
F
is varied (R
L
= 100Ω,
A
V
= +2). This plot shows that an R
F
of 200Ωresults in
peaking and marginal stability. An R
F
of 300Ωgives near
maximal bandwidth and gain flatness with good stability, but
with very light loads (R
L
>300Ω) the device may show some
peaking. An R
F
of 500Ωgives excellent stability with good
bandwidth and is the recommended value for most applica-
tions. Since all applications are slightly different it is worth
some experimentation to find the optimal R
F
for a given
circuit. For more information see Application Note OA-13
which describes the relationship between R
F
and closed-
loop frequency response for current feedback operational
amplifiers.
When configuring the LMH6715 for gains other than +2V/V,
it is usually necessary to adjust the value of the feedback
resistor. The two plots labeled “R
F
vs. Non-inverting Gain”
and “R
F
vs. Inverting Gain” provide recommended feedback
resistor values for a number of gain selections.
20042935
FIGURE 1. Non-Inverting Configuration with Power
Supply Bypassing
20042937
FIGURE 2. Inverting Configuration with Power Supply
Bypassing
LMH6715
www.national.com 8
Application Introduction (Continued)
R
F
vs. Non-Inverting Gain
20042921
Both plots show the value of R
F
approaching a minimum
value (dashed line) at high gains. Reducing the feedback
resistor below this value will result in instability and possibly
oscillation. The recommended value of R
F
is depicted by the
solid line, which begins to increase at higher gains. The
reason that a higher R
F
is required at higher gains is the
need to keep R
G
from decreasing too far below the output
impedance of the input buffer. For the LMH6715 the output
resistance of the input buffer is approximately 160Ωand 50Ω
is a practical lower limit for R
G
. Due to the limitations on R
G
the LMH6715 begins to operate in a gain bandwidth limited
fashion for gains of ±5V/V or greater.
R
F
vs. Inverting Gain
20042922
When using the LMH6715 as a replacement for the CLC412,
identical bandwidth can be obtained by using an appropriate
value of R
F
. The chart “Frequency Response vs. R
F
” shows
that an R
F
of approximately 700Ωwill provide bandwidth
very close to that of the CLC412. At other gains a similar
increase in R
F
can be used to match the new and old parts.
CIRCUIT LAYOUT
With all high frequency devices, board layouts with stray
capacitances have a strong influence over AC performance.
The LMH6715 is no exception and its input and output pins
are particularly sensitive to the coupling of parasitic capaci-
tances (to AC ground) arising from traces or pads placed too
closely (<0.1”) to power or ground planes. In some cases,
due to the frequency response peaking caused by these
parasitics, a small adjustment of the feedback resistor value
will serve to compensate the frequency response. Also, it is
very important to keep the parasitic capacitance across the
feedback resistor to an absolute minimum.
The performance plots in the data sheet can be reproduced
using the evaluation boards available from National. The
CLC730036 board uses all SMT parts for the evaluation of
the LMH6715. The board can serve as an example layout for
the final production printed circuit board.
Care must also be taken with the LMH6715’s layout in order
to achieve the best circuit performance, particularly channel-
to-channel isolation. The decoupling capacitors (both tanta-
lum and ceramic) must be chosen with good high frequency
characteristics to decouple the power supplies and the
physical placement of the LMH6715’s external components
is critical. Grouping each amplifier’s external components
with their own ground connection and separating them from
the external components of the opposing channel with the
maximum possible distance is recommended. The input
(R
IN
) and gain setting resistors (R
F
) are the most critical. It is
also recommended that the ceramic decoupling capacitor
(0.1µF chip or radial-leaded with low ESR) should be placed
as closely to the power pins as possible.
POWER DISSIPATION
Follow these steps to determine the Maximum power dissi-
pation for the LMH6715:
1. Calculate the quiescent (no-load) power: P
AMP
=I
CC
(V
CC
-V
EE
)
2. Calculate the RMS power at the output stage: P
O
=(V
CC
-V
LOAD
)(I
LOAD
), where V
LOAD
and I
LOAD
are the voltage and
current across the external load.
3. Calculate the total RMS power: Pt = P
AMP
+P
O
The maximum power that the LMH6715, package can dissi-
pate at a given temperature can be derived with the following
equation:
Pmax = (150o- Tamb)/ θ
JA
, where Tamb = Ambient tempera-
ture (˚C) and θ
JA
= Thermal resistance, from junction to
ambient, for a given package (˚C/W). For the SOIC package
θ
JA
is 145˚C/W.
MATCHING PERFORMANCE
With proper board layout, the AC performance match be-
tween the two LMH6715’s amplifiers can be tightly controlled
as shown in Typical Performance plot labeled “Small-Signal
Channel Matching”.
The measurements were performed with SMT components
using a feedback resistor of 300Ωat a gain of +2V/V.
The LMH6715’s amplifiers, built on the same die, provide the
advantage of having tightly matched DC characteristics.
SLEW RATE AND SETTLING TIME
One of the advantages of current-feedback topology is an
inherently high slew rate which produces a wider full power
bandwidth. The LMH6715 has a typical slew rate of 1300V/
µs. The required slew rate for a design can be calculated by
the following equation: SR = 2πfV
pk
.
Careful attention to parasitic capacitances is critical to
achieving the best settling time performance. The LMH6715
LMH6715
www.national.com9
Application Introduction (Continued)
has a typical short term settling time to 0.05% of 12ns for a
2V step. Also, the amplifier is virtually free of any long term
thermal tail effects at low gains.
When measuring settling time, a solid ground plane should
be used in order to reduce ground inductance which can
cause common-ground-impedance coupling. Power supply
and ground trace parasitic capacitances and the load ca-
pacitance will also affect settling time.
Placing a series resistor (R
s
) at the output pin is recom-
mended for optimal settling time performance when driving a
capacitive load. The Typical Performance plot labeled “R
S
and Settling Time vs. Capacitive Load” provides a means for
selecting a value of R
s
for a given capacitive load.
DC & NOISE PERFORMANCE
A current-feedback amplifier’s input stage does not have
equal nor correlated bias currents, therefore they cannot be
canceled and each contributes to the total DC offset voltage
at the output by the following equation:
The input resistance is the resistance looking from the non-
inverting input back toward the source. For inverting DC-
offset calculations, the source resistance seen by the input
resistor R
g
must be included in the output offset calculation
as a part of the non-inverting gain equation. Application note
OA-7 gives several circuits for DC offset correction. The
noise currents for the inverting and non-inverting inputs are
graphed in the Typical Performance plot labeled “Equivalent
Input Noise”. A more complete discussion of amplifier input-
referred noise and external resistor noise contribution can be
found in OA-12.
DIFFERENTIAL GAIN & PHASE
The LMH6715 can drive multiple video loads with very low
differential gain and phase errors. The Typical Performance
plots labeled “Differential Gain vs. Frequency” and “Differen-
tial Phase vs. Frequency” show performance for loads from
1 to 4. The Electrical Characteristics table also specifies
performance for one 150Ωload at 4.43MHz. For NTSC
video, the performance specifications also apply. Application
note OA-24 “Measuring and Improving Differential Gain &
Differential Phase for Video”, describes in detail the tech-
niques used to measure differential gain and phase.
I/O VOLTAGE & OUTPUT CURRENT
The usable common-mode input voltage range (CMIR) of
the LMH6715 specified in the Electrical Characteristics table
of the data sheet shows a range of ±2.2 volts. Exceeding
this range will cause the input stage to saturate and clip the
output signal.
The output voltage range is determined by the load resistor
and the choice of power supplies. With ±5 volts the class A/B
output driver will typically drive ±3.9V into a load resistance
of 100Ω. Increasing the supply voltages will change the
common-mode input and output voltage swings while at the
same time increase the internal junction temperature.
Applications Circuits
SINGLE-TO-DIFFERENTIAL LINE DRIVER
The LMH6715’s well matched AC channel-response allows a
single-ended input to be transformed to highly matched
push-pull driver. From a 1V single-ended input the circuit of
Figure 3 produces 1V differential signal between the two
outputs. For larger signals the input voltage divider (R
1
=
2R
2
) is necessary to limit the input voltage on channel 2.
DIFFERENTIAL LINE RECEIVER
Figure 4 and Figure 5 show two different implementations of
an instrumentation amplifier which convert differential sig-
nals to single-ended. Figure 5 allows CMRR adjustment
through R
2
.
20042945
FIGURE 3. Single-to-Differential Line Driver
20042946
FIGURE 4. Differential Line Receiver
LMH6715
www.national.com 10
Applications Circuits (Continued)
NON-INVERTING CURRENT-FEEDBACK INTEGRATOR
The circuit of Figure 6 achieves its high speed integration by
placing one of the LMH6715’s amplifiers in the feedback
loop of the second amplifier configured as shown.
LOW NOISE WIDE-BANDWIDTH TRANSIMPEDANCE
AMPLIFIER
Figure 7 implements a low noise transimpedance amplifier
using both channels of the LMH6715. This circuit takes
advantage of the lower input bias current noise of the non-
inverting input and achieves negative feedback through the
second LMH6715 channel. The output voltage is set by the
value of R
F
while frequency compensation is achieved
through the adjustment of R
T
.
20042947
FIGURE 5. Differential Line Receiver with CMRR
Adjustment
20042949
FIGURE 6. Current Feedback Integrator
20042950
FIGURE 7. Low-Noise, Wide Bandwidth,
Transimpedance Amp.
LMH6715
www.national.com11
Physical Dimensions inches (millimeters)
unless otherwise noted
8-Pin SOIC
NS Package Number M08A
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www.national.com
LMH6715 Dual Wideband Video Op Amp
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
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