Microstepping DMOS Driver with Translator
A5979
8
Allegro MicroSystems, LLC
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
www.allegromicro.com
FUNCTIONAL DESCRIPTION
Device Operation
The A5979 is a complete microstepping motor driver with built-
in translator for easy operation with minimal control lines. It is
designed to operate bipolar stepper motors in full-, half-,
quarter-, and sixteenth-step modes. The current in each of the two
output full-bridges, all N-channel DMOS, is regulated with fixed
off-time pulse-width modulated (PWM) control circuitry. The
full-bridge current at each step is set by the value of an external
current-sense resistor (RS), a reference voltage (VREF), and the
output voltage of its DAC (which in turn is controlled by the
output of the translator).
At power-up, or reset, the translator sets the DACs and phase
current polarity to the initial home state (see figures for home-
state conditions), and sets the current regulator for both phases to
mixed-decay mode. When a step command signal occurs on the
STEP input, the translator automatically sequences the DACs to
the next level (see Table 2 for the current level sequence and cur-
rent polarity). The microstep resolution is set by inputs MS1 and
MS2 as shown in Table 1. If the new DAC output level is lower
than the previous level, the decay mode for that full-bridge will
be set by the PFD input (fast, slow, or mixed decay). If the new
DAC level is higher or equal to the previous level, then the decay
mode for that full-bridge will be slow decay. This automatic
current-decay selection will improve microstepping performance
by reducing the distortion of the current waveform due to the
motor BEMF.
When stepping, if the new output levels of the DACs are higher
than or equal to their previous levels, then the decay mode for
that full-bridge is set to slow. If the new output levels of the
DACs are lower than their previous output levels, then the decay
mode for that full-bridge is set by the state of the PFD input (see
PFD input description). This automatic current decay selection
improves microstepping performance by reducing the distortion
of the current waveform that results from the back-EMF of the
motor. See Figure 6 on page 14 for decay mode detail.
Internal PWM Current Control
Each full-bridge is controlled by a fixed off-time PWM current-
control circuit that limits the load current to an appropriate
level (ITRIP). Initially, a diagonal pair of source and sink DMOS
outputs are enabled, and current flows through the motor wind-
ing and the current-sense resistor, RS. When the voltage across
RS rises to the DAC output voltage, the current-sense comparator
resets the PWM latch, which turns off the source driver (in slow-
decay mode) or the sink and source drivers (in fast- or mixed-
decay mode).
The maximum level of current limiting is set by the selection of
RS and the voltage at the VREF input with a transconductance
function approximated by:
ITRIPmax = VREF / (8 × RS)
The DAC output reduces the VREF output to the current-sense
comparator in precise steps (see Table 2 for % ITRIPmax at each
step).
ITRIP = (% ITRIPmax / 100) × ITRIPmax
It is critical to ensure that the maximum rating on the SENSE
terminal is not exceeded (0.5 V). For full-step mode, VREF can be
applied up to the maximum rating of VDD, because the peak sense
value is 0.707 × VREF / 8. In all other modes, VREF should not
exceed 4 V.
Fixed Off-Time
The internal PWM current-control circuitry uses a one-shot to
control the time that the drivers remain off. The one-shot off-
time, tOFF, is determined by the selection of an external resis-
tor (RT) and capacitor (CT) connected between the RC timing
terminal and ground. The off-time, over a range of values of CT
= 470 pF to 1500 pF and RT = 12 kΩ to 100 kΩ is approximated
by:
tOFF = RT × CT
RC Blanking
In addition to the fixed off-time of the PWM control circuit, the
CT component sets the comparator blanking time. This func-
tion blanks the output of the current-sense comparator when the
outputs are switched by the internal current-control circuitry. The
comparator output is blanked to prevent false overcurrent detec-
tion due to reverse-recovery currents of the clamp diodes, and/
or switching transients related to the capacitance of the load. The
blank time, tBLANK, can be approximated by:
tBLANK = 1400 × CT