VIN
EN
GND
FB
VOUT
LMZ10503
VIN VOUT
SS
Cin
CO
Rfbt
Rcomp Ccomp
Rfbb
CSS
1
2
34, EP
5
6, 7
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An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
LMZ10503
SNVS641K –JANUARY 2010–REVISED MAY 2017
LMZ10503 3-A SIMPLE SWITCHER
®
Power Module With 5.5-V Maximum Input Voltage
1
1 Features
1• Integrated Shielded Inductor
• Flexible Start-up Sequencing Using External Soft
Start, Tracking, and Precision Enable
• Protection Against In-Rush Currents and Faults
Such as Input UVLO and Output Short Circuit
• Single Exposed Pad and Standard Pinout for Easy
Mounting and Manufacturing
• Pin-to-Pin Compatible With
– LMZ10504 (4 A / 20 W Maximum)
– LMZ10505 (5 A / 25 W Maximum)
• Electrical Specifications
– 15-W Maximum Total Output Power
– Up to 3-A Output Current
– Input Voltage Range 2.95 V to 5.5 V
– Output Voltage Range 0.8 V to 5 V
– ±1.63% Feedback Voltage Accuracy Over
Temperature
• Performance Benefits
– Operates at High Ambient Temperatures
– High Efficiency up to 96% Reduces System
Heat Generation
– Low Radiated Emissions (EMI) Tested to
EN55022 Class B Standard (EN 55022:2006,
+A1:2007, FCC Part 15 Subpart B: 2007. See
Table 9 and layout information for more
regarding device under test.)
– Fast Transient Response for Powering FPGAs
and ASICs
• Create a Custom Design Using the LMZ10503
With the WEBENCH®Power Designer
2 Applications
• Point-of-Load Conversions From 3.3-V and 5-V
Rails
• Space-Constrained Applications
• Noise Sensitive Applications (that is, Transceiver,
Medical)
3 Description
The LMZ10503 SIMPLE SWITCHER power module
is a complete, easy-to-use DC-DC solution capable of
driving up to a 3-A load with exceptional power
conversion efficiency, output voltage accuracy, line
and load regulation. The LMZ10503 is available in an
innovative package that enhances thermal
performance and allows for hand or machine
soldering.
The LMZ10503 can accept an input voltage rail
between 2.95 V and 5.5 V and can deliver an
adjustable and highly accurate output voltage as low
as 0.8 V. One megahertz fixed-frequency PWM
switching provides a predictable EMI characteristic.
Two external compensation components can be
adjusted to set the fastest response time, while
allowing the option to use ceramic and/or electrolytic
output capacitors. Externally programmable soft-start
capacitor facilitates controlled startup. The LMZ10503
is a reliable and robust solution with the following
features: lossless cycle-by-cycle peak current limit to
protect for over current or short-circuit fault, thermal
shutdown, input undervoltage lockout, and prebiased
start-up.
Device Information(1)(2)
PART NUMBER PACKAGE BODY SIZE (NOM)
LMZ10503 TO-PMOD (7) 10.16 mm × 9.85 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
(2) Peak reflow temperature equals 245°C. See Design Summary
LMZ1xxx and LMZ2xxx Power Module Family (SNAA214) for
more details.
Typical Application Circuit Efficiency VOUT = 3.3 V
2
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Table of Contents
1 Features.................................................................. 1
2 Applications ........................................................... 1
3 Description............................................................. 1
4 Revision History..................................................... 2
5 Pin Configuration and Functions......................... 3
6 Specifications......................................................... 4
6.1 Absolute Maximum Ratings ...................................... 4
6.2 ESD Ratings.............................................................. 4
6.3 Recommended Operating Conditions....................... 4
6.4 Thermal Information.................................................. 4
6.5 Electrical Characteristics........................................... 5
6.6 Typical Characteristics.............................................. 7
7 Detailed Description............................................ 10
7.1 Overview................................................................. 10
7.2 Functional Block Diagram....................................... 10
7.3 Feature Description................................................. 10
7.4 Device Functional Modes........................................ 13
8 Application and Implementation ........................ 14
8.1 Application Information............................................ 14
8.2 Typical Application.................................................. 14
8.3 System Examples ................................................... 20
9 Power Supply Recommendations...................... 23
10 Layout................................................................... 23
10.1 Layout Guidelines ................................................. 23
10.2 Layout Examples................................................... 24
10.3 Estimate Power Dissipation and Thermal
Considerations......................................................... 26
10.4 Power Module SMT Guidelines ............................ 27
11 Device and Documentation Support................. 28
11.1 Device Support...................................................... 28
11.2 Documentation Support ........................................ 28
11.3 Receiving Notification of Documentation Updates 28
11.4 Community Resources.......................................... 28
11.5 Trademarks........................................................... 29
11.6 Electrostatic Discharge Caution............................ 29
11.7 Glossary................................................................ 29
12 Mechanical, Packaging, and Orderable
Information........................................................... 29
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision J (September 2015) to Revision K Page
• Changed language of WEBENCH list item; added additional content and links for WEBENCH further in data sheet ......... 1
• Changed equation 1 in Enable and UVLO .......................................................................................................................... 10
Changes from Revision I (October 2013) to Revision J Page
• Added Pin Configuration and Functions section, ESD Ratings table, Feature Description section, Device Functional
Modes,Application and Implementation section, Power Supply Recommendations section, Layout section, Device
and Documentation Support section, and Mechanical, Packaging, and Orderable Information section .............................. 1
• Removed Easy-To-Use PFM 7-Pin Package image ............................................................................................................. 1
Changes from Revision H (April 2013) to Revision I Page
• Deleted 10 mils....................................................................................................................................................................... 4
• Changed 10 mils................................................................................................................................................................... 23
• Added Power Module SMT Guidelines................................................................................................................................. 27
Exposed Pad
Connect to GND
5 FB
6 VOUT
3 SS
1 VIN
2 EN
4 GND
7 VOUT
3
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5 Pin Configuration and Functions
NDW Package
7-Lead TO-PMOD
Top View
Pin Functions
PIN TYPE DESCRIPTION
NAME NO.
EN 2 Analog Active-high enable input for the device.
Exposed Pad — Ground Exposed pad is used as a thermal connection to remove heat from the device. Connect this pad to
the PCB ground plane in order to reduce thermal resistance value. EP must also provide a direct
electrical connection to the input and output capacitors ground terminals. Connect EP to pin 4.
FB 5 Analog Feedback pin. This is the inverting input of the error amplifier used for sensing the output voltage.
Keep the copper area of this node small.
GND 4 Ground Power ground and signal ground. Provide a direct connection to the EP. Place the bottom
feedback resistor as close as possible to GND and FB pin.
SS 3 Analog Soft-start control pin. An internal 2-µA current source charges an external capacitor connected
between SS and GND pins to set the output voltage ramp rate during startup. The SS pin can also
be used to configure the tracking feature.
VIN 1 Power Power supply input. A low ESR input capacitance should be located as close as possible to the
VIN pin and exposed pad (EP).
VOUT 6, 7 Power The output terminal of the internal inductor. Connect the output filter capacitor between VOUT pin
and EP.
4
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(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) For soldering specifications, refer to the Absolute Maximum Ratings for Soldering (SNOA549).
(3) If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/Distributors for availability and
specifications.
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1)(2)(3)
MIN MAX UNIT
VIN, VOUT, EN, FB, SS to GND –0.3 6 V
Power Dissipation Internally Limited
Junction Temperature 150 °C
Peak Reflow Case Temperature (30 sec) 245 °C
Storage Temperature, Tstg –65 150 °C
(1) The human body model is a 100-pF capacitor discharged through a 1.5-kΩresistor into each pin. Test method is per JESD22-AI14S.
6.2 ESD Ratings VALUE UNIT
V(ESD) Electrostatic discharge Human body model (HBM)(1) ±2000 V
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted) MIN MAX UNIT
VIN to GND 2.95 5.5 V
Junction Temperature (TJ) –40 125 °C
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report.
(2) RθJA measured on a 2.25-in × 2.25-in (5.8 cm x 5.8 cm) 4-layer board, with 1-oz. copper, thirty six thermal vias, no air flow, and 1-W
power dissipation. Refer to Layout or Evaluation Board Application Note AN-2024 LMZ1420x / LMZ1200x Evaluation Board (SNVA422).
6.4 Thermal Information
THERMAL METRIC(1) LMZ10503
UNITNDW (TO-PMOD)
7 PINS
RθJA Junction-to-ambient thermal resistance (2) 20 °C/W
RθJC(top) Junction-to-case (top) thermal resistance 1.9 °C/W
5
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(1) Minimum and maximum limits are 100% production tested at an ambient temperature (TA) of 25°C. Limits over the operating
temperature range are ensured through correlation using Statistical Quality Control (SQC) methods. Limits are used to calculate
Average Outgoing Quality Level (AOQL).
(2) Typical numbers are at 25°C and represent the most likely parametric norm.
6.5 Electrical Characteristics
Specifications are for TJ= 25°C unless otherwise specified. Minimum and maximum limits are ensured through test, design,
or statistical correlation. Typical values represent the most likely parametric norm at TJ= 25°C, and are provided for reference
purposes only. VIN = VEN = 3.3 V, unless otherwise indicated in the conditions column.
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
SYSTEM PARAMETERS
VFB Total Feedback Voltage
Variation Including Line and
Load Regulation
VIN = 2.95 V to 5.5 V
VOUT = 2.5 V
IOUT = 0 A to 3 A
0.8 V
over the operating junction
temperature range TJof –40°C
to 125°C
0.78 0.82
VFB Feedback Voltage Variation VIN = 3.3 V, VOUT = 2.5
V
IOUT = 0 A
0.8 V
over the operating junction
temperature range TJof –40°C
to 125°C
0.787 0.812
VFB Feedback Voltage Variation VIN = 3.3 V, VOUT = 2.5
V
IOUT = 3 A
0.798 V
over the operating junction
temperature range TJof –40°C
to 125°C
0.785 0.81
VIN(UVLO) Input UVLO Threshold
(Measured at VIN pin)
Rising
2.6 V
over the operating junction
temperature range TJof –40°C
to 125°C
2.95
Falling
2.4
over the operating junction
temperature range TJof –40°C
to 125°C
1.95
ISS Soft-Start Current Charging Current 2 µA
IQNon-Switching Input
Current VFB = 1 V
1.7 mA
over the operating junction
temperature range TJof –40°C
to 125°C
3
ISD Shutdown Quiescent
Current VIN = 5.5 V, VEN = 0 V
260 µA
over the operating junction
temperature range TJof –40°C
to 125°C
500
IOCL Output Current Limit
(Average Current) VOUT = 2.5 V
5.2 A
over the operating junction
temperature range TJof –40°C
to 125°C
3.8 6.7
fFB Frequency Fold-back In current limit 250 kHz
PWM SECTION
fSW Switching Frequency 1000 kHz
over the operating junction temperature range TJof –40°C
to 125°C 750 1160
Drange PWM Duty Cycle Range over the operating junction temperature range TJof –40°C
to 125°C 0% 100%
ENABLE CONTROL
VEN-IH EN Pin Rising Threshold 1.23 V
over the operating junction temperature range TJof –40°C
to 125°C 1.8
VEN-IF EN Pin Falling Threshold 1.06 V
over the operating junction temperature range TJof –40°C
to 125°C 0.8
6
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Electrical Characteristics (continued)
Specifications are for TJ= 25°C unless otherwise specified. Minimum and maximum limits are ensured through test, design,
or statistical correlation. Typical values represent the most likely parametric norm at TJ= 25°C, and are provided for reference
purposes only. VIN = VEN = 3.3 V, unless otherwise indicated in the conditions column.
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
THERMAL CONTROL
TSD TJfor Thermal Shutdown 145 °C
TSD-HYS Hysteresis for Thermal
Shutdown 10 °C
PERFORMANCE PARAMETERS
ΔVOUT Output Voltage Ripple Refer to Table 1
VOUT = 2.5 V
Bandwidth Limit = 2 MHz
7 mVpk-
pk
ΔVOUT Output Voltage Ripple Refer to Table 5 Bandwidth Limit = 20 MHz 5 mVpk-
pk
ΔVFB /
VFB Feedback Voltage Line
Regulation ΔVIN = 2.95 V to 5.5 V
IOUT = 0 A 0.04%
ΔVOUT /
VOUT Output Voltage Line
Regulation ΔVIN = 2.95 V to 5.5 V
IOUT = 0 A, VOUT = 2.5 V 0.04%
ΔVFB /
VFB Feedback Voltage Load
Regulation IOUT = 0 A to 3 A 0.25%
ΔVOUT /
VOUT Output Voltage Load
Regulation IOUT = 0 A to 3 A
VOUT = 2.5 V 0.25%
EFFICIENCY
ηPeak Efficiency (1 A) VIN =
5 V
VOUT = 3.3 V 96.3%
VOUT = 2.5 V 94.9%
VOUT = 1.8 V 93.3%
VOUT = 1.5 V 92.2%
VOUT = 1.2 V 90.5%
VOUT = 0.8 V 86.9%
ηPeak Efficiency (1 A) VIN =
3.3 V
VOUT = 2.5 V 95.7%
VOUT = 1.8 V 94%
VOUT = 1.5 V 92.9%
VOUT = 1.2 V 91.3%
VOUT = 0.8 V 87.9%
ηFull Load Efficiency (3 A)
VIN = 5 V
VOUT = 3.3 V 94.8%
VOUT = 2.5 V 93%
VOUT = 1.8 V 90.8%
VOUT = 1.5 V 89.3%
VOUT = 1.2 V 87.1%
VOUT = 0.8 V 82.3%
ηFull Load Efficiency (3 A)
VIN = 3.3 V
VOUT = 2.5 V 92.4%
VOUT = 1.8 V 89.8%
VOUT = 1.5 V 88.2%
VOUT = 1.2 V 85.9%
VOUT = 0.8 V 80.8%
7
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6.6 Typical Characteristics
Unless otherwise specified, the following conditions apply: VIN = VEN = 5 V, CIN is 47 µF 10-V X5R ceramic capacitor; TA=
25°C for efficiency curves and waveforms.
VOUT = 3.3 V
Figure 1. Efficiency
VOUT = 2.5 V
Figure 2. Efficiency
VOUT = 1.8 V
Figure 3. Efficiency
VOUT = 1.5 V
Figure 4. Efficiency
VOUT = 1.2 V
Figure 5. Efficiency
VOUT = 0.8 V
Figure 6. Efficiency
8
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Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = VEN = 5 V, CIN is 47 µF 10-V X5R ceramic capacitor; TA=
25°C for efficiency curves and waveforms.
VIN = 5 V, RθJA = 20°C/W
Figure 7. Current Derating
VIN = 3.3 V, RθJA = 20°C/W
Figure 8. Current Derating
VIN = 5 V, VOUT = 2.5 V, IOUT = 3 A
Figure 9. Radiated Emissions (EN55022, Class B)
Evaluation Board
VOUT = 2.5 V, IOUT = 0 A
Figure 10. Start-Up
VOUT = 2.5 V, IOUT = 0 A
Figure 11. Prebiased Start-Up
VIN = 3.3 V, VOUT = 2.5 V, IOUT = 0.3 A to 2.7 A to 0.3-A Step
20-MHz Bandwidth Limited. Refer to Table 5 for BOM, includes
optional components
Figure 12. Load Transient Response
9
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Typical Characteristics (continued)
Unless otherwise specified, the following conditions apply: VIN = VEN = 5 V, CIN is 47 µF 10-V X5R ceramic capacitor; TA=
25°C for efficiency curves and waveforms.
VIN = 5 V, VOUT = 2.5 V, IOUT = 0.3 A to 2.7 A to 0.3-A step
20-MHz Bandwidth Limited. Refer to Table 5 for BOM, includes
optional components
Figure 13. Load Transient Response
VIN = 3.3 V, VOUT = 2.5 V, IOUT = 3 A,
20 mV/DIV. Refer to Table 5 for BOM
Figure 14. Output Voltage Ripple
VIN = 5 V, VOUT = 2.5 V, IOUT = 3 A,
20 mV/DIV. Refer to Table 5 for BOM
Figure 15. Output Voltage Ripple
ent enb
IN(UVLO) enb
R R
V 1.23V R
u
EN
VIN
Voltage
Mode
Control VOUT
GND
SS
FB
2.2 PH
2.2 PF
2.2 PF
1:
1
2
3
4, EP
5
6, 7
Drivers
P-MOSFET
N-MOSFET
10
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7 Detailed Description
7.1 Overview
The LMZ10503 SIMPLE SWITCHER power module is a complete, easy-to-use DC-DC solution capable of
driving up to a 3-A load with exceptional power conversion efficiency, output voltage accuracy, line and load
regulation. The LMZ10503 is available in an innovative package that enhances thermal performance and allows
for hand or machine soldering. The LMZ10503 is a reliable and robust solution with the following features:
lossless cycle-by-cycle peak current limit to protect for overcurrent or short-circuit fault, thermal shutdown, input
undervoltage lockout, and prebiased start-up.
7.2 Functional Block Diagram
7.3 Feature Description
7.3.1 Enable
The LMZ10503 features an enable (EN) pin and associated comparator to allow the user to easily sequence the
LMZ10503 from an external voltage rail, or to manually set the input UVLO threshold. The turnon or rising
threshold and hysteresis for this comparator are typically 1.23 V and 0.15 V respectively. The precise reference
for the enable comparator allows the user to ensure that the LMZ10503 will be disabled when the system
demands it to be.
The EN pin should not be left floating. For always-on operation, connect EN to VIN.
7.3.2 Enable and UVLO
Using a resistor divider from VIN to EN as shown in the schematic diagram below, the input voltage at which the
part begins switching can be increased above the normal input UVLO level according to
(1)
For example, suppose that the required input UVLO level is 3.69 V. Choosing Renb = 10 kΩ, then we calculate
Rent = 20 kΩ.
SS
C 2.5 nF / ms
ss ss
SS FB
t I
CV
u
VIN
EN
GND
VOUT
Renb
Rent
VIN
Cin1
Master Power Supply
VOUT1
VOUT2
CO1
LMZ10503
VIN
EN
GND
LMZ10503
Renb
Rent
VIN
Cin1
11
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Feature Description (continued)
Figure 16. Setting Enable and UVLO
Alternatively, the EN pin can be driven from another voltage source to cater to system sequencing requirements
commonly found in FPGA and other multi-rail applications. Figure 17 shows an LMZ10503 that is sequenced to
start based on the voltage level of a master system rail (VOUT1).
Figure 17. Setting Enable and UVLO Using External Power Supply
7.3.3 Soft-Start
The LMZ10503 begins to operate when both the VIN and EN, voltages exceed the rising UVLO and enable
thresholds, respectively. A controlled soft-start eliminates inrush currents during start-up and allows the user
more control and flexibility when sequencing the LMZ10503 with other power supplies.
In the event of either VIN or EN decreasing below the falling UVLO or enable threshold respectively, the voltage
on the soft-start pin is collapsed by discharging the soft-start capacitor by a 14-µA (typical) current sink to
ground.
7.3.4 Soft-Start Capacitor
Determine the soft-start capacitance with the following relationship:
where
• VFB is the internal reference voltage (nominally 0.8 V), ISS is the soft-start charging current (nominally 2 µA)
and CSS is the external soft-start capacitance. (2)
Thus, the required soft-start capacitor per unit output voltage startup time is given by:
(3)
For example, a 4-ms soft-start time will yield a 10-nF capacitance. The minimum soft-start capacitance is 680 pF.
VOLTAGE
TIME
RATIOMETRIC STARTUP
VOUT2
EN
VOUT1
trkt
trkb OUT1
R
RV 1.0V
VIN
EN
GND
SS
Rtrkb
Rtrkt
VIN
Cin1
Master Power
Supply
VOUT1
VOUT2
CO1
VSS
LMZ10503VOUT
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Feature Description (continued)
7.3.5 Tracking
The LMZ10503 can track the output of a master power supply during soft-start by connecting a resistor divider to
the SS pin. In this way, the output voltage slew rate of the LMZ10503 will be controlled by a master supply for
loads that require precise sequencing. When the tracking function is used, a small value soft-start capacitor
should be connected to the SS pin to alleviate output voltage overshoot when recovering from a current limit
fault.
Figure 18. Tracking Using External Power Supply
7.3.6 Tracking - Equal Soft-Start Time
One way to use the tracking feature is to design the tracking resistor divider so that the master supply output
voltage, VOUT1, and the LMZ10503 output voltage, VOUT2, both rise together and reach their target values at the
same time. This is termed ratiometric start-up. For this case, the equation governing the values of tracking divider
resistors Rtrkb and Rtrkt is given by:
(4)
Equation 4 includes an offset voltage, of 200 mV, to ensure that the final value of the SS pin voltage exceeds the
reference voltage of the LMZ10503. This offset will cause the LMZ10503 output voltage to reach regulation
slightly before the master supply. A value of 33 kΩ1% is recommended for Rtrkt as a compromise between high
precision and low quiescent current through the divider while minimizing the effect of the 2-µA soft-start current
source.
For example, if the master supply voltage VOUT1 is 3.3 V and the LMZ10503 output voltage was 1.8 V, then the
value of Rtrkb needed to give the two supplies identical soft-start times would be 14.3 kΩ.Figure 19 shows an
example of tracking using the equal soft-start time.
Figure 19. Timing Diagram for Tracking Using Equal Soft-Start Time
VOLTAGE
TIME
SIMULTANEOUS STARTUP
VOUT2
EN
VOUT1
OUT2 OUT1
V 0.8 V u
trkb trkt
OUT2
0.8V
R R
V 0.8V
u
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Feature Description (continued)
7.3.7 Tracking - Equal Slew Rates
Alternatively, the tracking feature can be used to have similar output voltage ramp rates. This is referred to as
simultaneous start-up. In this case, the tracking resistors can be determined based on Equation 5:
(5)
and to ensure proper overdrive of the SS pin:
(6)
For the example case of VOUT1 =5VandVOUT2 = 2.5 V, with Rtrkt set to 33 kΩas before, Rtrkb is calculated from
the above equation to be 15.5 kΩ.Figure 20 shows an example of tracking using the equal slew rates.
Figure 20. Timing Diagram for Tracking Using Equal Slew Rates
7.3.8 Current Limit
When a current greater than the output current limit (IOCL) is sensed, the ON-time is immediately terminated and
the low-side MOSFET is activated. The low-side MOSFET stays on for the entire next four switching cycles.
During these skipped pulses, the voltage on the soft-start pin is reduced by discharging the soft-start capacitor by
a current sink on the soft-start pin of nominally 14 µA. Subsequent overcurrent events will drain more and more
charge from the soft-start capacitor, effectively decreasing the reference voltage as the output droops due to the
pulse skipping. Reactivation of the soft-start circuitry ensures that when the overcurrent situation is removed, the
part will resume normal operation smoothly.
7.3.9 Overtemperature Protection
When the LMZ10503 senses a junction temperature greater than 145°C (typical), both switching MOSFETs are
turned off and the part enters a standby state. Upon sensing a junction temperature below 135°C (typical), the
part will re-initiate the soft-start sequence and begin switching once again.
7.4 Device Functional Modes
7.4.1 Prebias Start-Up Capability
At start-up, the LMZ10503 is in a prebiased state when the output voltage is greater than zero. This often occurs
in many multi-rail applications such as when powering an ASIC, FPGA, or DSP. The output can be prebiased in
these applications through parasitic conduction paths from one supply rail to another. Even though the
LMZ10503 is a synchronous converter, it will not pull the output low when a prebias condition exists. The
LMZ10503 will not sink current during start-up until the soft-start voltage exceeds the voltage on the FB pin.
Because the device does not sink current it protects the load from damage that might otherwise occur if current
is conducted through the parasitic paths of the load.
VIN
EN
GND
FB
VOUT
LMZ10503
VIN VOUT
SS
Cin
CO
Rfbt
Rcomp Ccomp
Rfbb
CSS
1
2
34, EP
5
6, 7
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The LMZ10503 is a step-down DC-to-DC power module. It is typically used to convert a higher DC voltage to a
lower DC voltage with a maximum output current of 3 A. The following design procedure can be used to select
components for the LMZ10503. Alternately, the WEBENCH software may be used to generate complete designs.
When generating a design, the WEBENCH software uses iterative design procedure and accesses
comprehensive databases of components. Please go to www.ti.com for more details.
8.2 Typical Application
Figure 21. Typical Application Circuit
8.2.1 Design Requirements
For this example the following application parameters exist.
• VIN =5V
• VOUT = 2.5 V
• IOUT =3A
•ΔVOUT = 20 mVpk-pk
•ΔVo_tran = ±20 mVpk-pk
Table 1. Bill of Materials, VIN =3.3Vto5V,VOUT = 2.5 V, IOUT (MAX) = 3 A, Optimized for Electrolytic Input
and Output Capacitance
DESIGNATOR DESCRIPTION CASE SIZE MANUFACTURER MANUFACTURER P/N QUANTITY
U1 SIMPLE SWITCHER PFM-7 Texas Instruments LMZ10503 1
Cin1 150 µF, 6.3 V, 18 mΩC2, 6.0 x 3.2 x 1.8 mm Sanyo 6TPE150MIC2 1
CO1 330 µF, 6.3 V, 18 mΩD3L, 7.3 x 4.3 x 2.8
mm Sanyo 6TPE330MIL 1
Rfbt 100 kΩ0603 Vishay Dale CRCW0603100KFKEA 1
Rfbb 47.5 kΩ0603 Vishay Dale CRCW060347K5FKEA 1
Rcomp 15 kΩ0603 Vishay Dale CRCW060315K0FKEA 1
Ccomp 330 pF, ±5%, C0G, 50 V 0603 TDK C1608C0G1H331J 1
CSS 10 nF, ±10%, X7R, 16 V 0603 Murata GRM188R71C103KA01 1
15
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Table 2. Bill of Materials, VIN = 3.3 V, VOUT = 0.8 V, IOUT (MAX) = 3 A, Optimized for Solution Size and
Transient Response
DESIGNATOR DESCRIPTION CASE SIZE MANUFACTURER MANUFACTURER P/N QUANTITY
U1 SIMPLE SWITCHER PFM-7 Texas Instruments LMZ10503TZ 1
Cin1, CO1 47 µF, X5R, 6.3 V 1206 TDK C3216X5R0J476M 2
Rfbt 110 kΩ0402 Vishay Dale CRCW0402100KFKED 1
Rcomp 1.0 kΩ0402 Vishay Dale CRCW04021K00FKED 1
Ccomp 27 pF, ±5%, C0G, 50 V 0402 Murata GRM1555C1H270JZ01 1
CSS 10 nF, ±10%, X7R, 16 V 0402 Murata GRM155R71C103KA01 1
8.2.2 Detailed Design Procedure
LMZ10503 is fully supported by WEBENCH and offers the following: component selection, performance,
electrical, and thermal simulations as well as the Build-It board, for a reduced design time. On the other hand, all
external components can be calculated by following the design procedure below.
1. Determine the input voltage and output voltage. Also, make note of the ripple voltage and voltage transient
requirements.
2. Determine the necessary input and output capacitance.
3. Calculate the feedback resistor divider.
4. Select the optimized compensation component values.
5. Estimate the power dissipation and board thermal requirements.
6. Follow the PCB design guideline.
7. Learn about the LMZ10503 features such as enable, input UVLO, soft start, tracking, prebiased start-up,
current limit, and thermal shutdown.
8.2.2.1 Custom Design With WEBENCH® Tools
Click here to create a custom design using the LMZ10503 device with the WEBENCH® Power Designer.
1. Start by entering the input voltage (VIN), output voltage (VOUT), and output current (IOUT) requirements.
2. Optimize the design for key parameters such as efficiency, footprint, and cost using the optimizer dial.
3. Compare the generated design with other possible solutions from Texas Instruments.
The WEBENCH Power Designer provides a customized schematic along with a list of materials with real-time
pricing and component availability.
In most cases, these actions are available:
• Run electrical simulations to see important waveforms and circuit performance
• Run thermal simulations to understand board thermal performance
• Export customized schematic and layout into popular CAD formats
• Print PDF reports for the design, and share the design with colleagues
Get more information about WEBENCH tools at www.ti.com/WEBENCH.
IN OUT
Lsw
(V V ) D
iL f
u
'
u
> @
L
Osw OUT L ESR
i
C8 f V ( i R )
'
tu u ' ' u
Cin(RMS) 2.5V 2.5V
I 3A 1 1.5A
5V 5V
§ ·
u
¨ ¸
© ¹
Cin(RMS) OUT
I I D(1 D) u
in
2.5V 2.5V
3A 1
5V 5V
C 15 F
1 MHz 50mV
§ · § ·
u u
¨ ¸ ¨ ¸
© ¹ © ¹
t t P
u
OUT
IN
V
DV
OUT
in sw IN
I D (1 D)
Cf V
u u
t
u '
16
LMZ10503
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8.2.2.2 Input Capacitor Selection
A 22-µF or 47-µF, high-quality dielectric (X5R, X7R) ceramic capacitor rated at twice the maximum input voltage
is typically sufficient. The input capacitor must be placed as close as possible to the VIN pin and GND exposed
pad to substantially eliminate the parasitic effects of any stray inductance or resistance on the PCB and supply
lines.
Neglecting capacitor equivalent series resistance (ESR), the resultant input capacitor AC ripple voltage is a
triangular waveform. The minimum input capacitance for a given peak-to-peak value (ΔVIN) of VIN is specified as
follows:
where
• the PWM duty cycle, D, is given by Equation 8: (7)
(8)
If ΔVIN is 1% of VIN, this equals to 50 mV and fSW = 1 MHz.
(9)
A second criteria before finalizing the Cin bypass capacitor is the RMS current capability. The necessary RMS
current rating of the input capacitor to a buck regulator can be estimated by:
(10)
(11)
With this high AC current present in the input capacitor, the RMS current rating becomes an important
parameter. The maximum input capacitor ripple voltage and RMS current occur at 50% duty cycle. Select an
input capacitor rated for at least the maximum calculated ICin(RMS).
Additional bulk capacitance with higher ESR may be required to damp any resonance effects of the input
capacitance and parasitic inductance.
8.2.2.3 Output Capacitor Selection
In general, 22-µF to 100-µF, high-quality dielectric (X5R, X7R) ceramic capacitor rated at twice the maximum
output voltage is sufficient given the optimal high-frequency characteristics and low ESR of ceramic dielectrics.
Although, the output capacitor can also be of electrolytic chemistry for increased capacitance density.
Two output capacitance equations are required to determine the minimum output capacitance. One equation
determines the output capacitance (CO) based on PWM ripple voltage. The second equation determines CO
based on the load transient characteristics. Select the largest capacitance value of the two.
The minimum capacitance, given the maximum output voltage ripple (ΔVOUT) requirement, is determined by
Equation 12:
where
• the peak to peak inductor current ripple (ΔiL) is equal to Equation 13: (12)
(13)
fbt fbb
OUT fbb
R R
V 0.8V R
u
O
C 42 F t P
O2.4A 0.8V 2.2 H 5V
C4 2.5V (5V 2.5V) 20mV
u u P u
tu u u
step FB IN
OOUT IN OUT
I V L V
C4 V (V V ) Vo_tran
u u u
t
u u u '
O
C 4 F t P
O568 mA
C8 1 MHz 20 mV 568 mA 3 m
tª º
u u u :
¬ ¼
2.5V
5V
L(5V 2.2V)
i 568 mA
2.2 H 1 MHz
u
'
P u
17
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RESR is the total output capacitor ESR, L is the inductance value of the internal power inductor, where L = 2.2
µH, and fSW = 1 MHz. Therefore, per the design example:
(14)
The minimum output capacitance requirement due to the PWM ripple voltage is:
(15)
(16)
Three mΩis a typical RESR value for ceramic capacitors.
Equation 17 provides a good first pass capacitance requirement for a load transient:
where
• Istep is the peak-to-peak load step (for this example Istep = 10% to 90% of the maximum load)
• VFB = 0.8 V
• and ΔVo_tran is the maximum output voltage deviation, which is ±20 mV. (17)
Therefore the capacitance requirement for the given design parameters is:
(18)
(19)
In this particular design the output capacitance is determined by the load transient requirements.
Table 3 lists some examples of commercially available capacitors that can be used with the LMZ10503.
Table 3. Recommended Output Filter Capacitors
CO(µF) VOLTAGE (V), RESR (mΩ) MAKE MANUFACTURER PART NUMBER CASE SIZE
22 6.3, < 5 Ceramic, X5R TDK C3216X5R0J226M 1206
47 6.3, < 5 Ceramic, X5R TDK C3216X5R0J476M 1206
47 6.3, < 5 Ceramic, X5R TDK C3225X5R0J476M 1210
47 10.0, < 5 Ceramic, X5R TDK C3225X5R1A476M 1210
100 6.3, < 5 Ceramic, X5R TDK C3225X5R0J107M 1210
100 6.3, 50 Tantalum AVX TPSD157M006#0050 D, 7.5 x 4.3 x 2.9 mm
100 6.3, 25 Organic Polymer Sanyo 6TPE100MPB2 B2, 3.5 x 2.8 x 1.9 mm
150 6.3, 18 Organic Polymer Sanyo 6TPE150MIC2 C2, 6.0 x 3.2 x 1.8 mm
330 6.3, 18 Organic Polymer Sanyo 6TPE330MIL D3L, 7.3 x 4.3 x 2.8
mm
470 6.3, 23 Niobium Oxide AVX NOME37M006#0023 E, 7.3 x 4.3 x 4.1 mm
8.2.2.3.1 Output Voltage Setting
A resistor divider network from VOUT to the FB pin determines the desired output voltage as follows:
(20)
Rfbt is defined based on the voltage loop requirements and Rfbb is then selected for the desired output voltage.
Resistors are normally selected as 0.5% or 1% tolerance. Higher accuracy resistors such as 0.1% are also
available.
VIN
EN
GND
FB
LMZ10503 Rfbt Rcomp
Ccomp
Rfbb
VIN
VOUT
18
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(1) In the special case where the output voltage is 0.8 V, TI recommends to remove Rfbb and keep Rfbt, Rcomp, and Ccomp for a type III
compensation.
The feedback voltage (at VOUT = 2.5 V) is accurate to within –2.5% / +2.5% over temperature and over line and
load regulation. Additionally, the LMZ10503 contains error nulling circuitry to substantially eliminate the feedback
voltage variation over temperature as well as the long term aging effects of the internal amplifiers. In addition the
zero nulling circuit dramatically reduces the 1/f noise of the bandgap amplifier and reference. The manifestation
of this circuit action is that the duty cycle will have two slightly different but distinct operating points, each evident
every other switching cycle.
8.2.2.4 Loop Compensation
The LMZ10503 preserves flexibility by integrating the control components around the internal error amplifier while
using three small external compensation components from VOUT to FB. An integrated type II (two pole, one zero)
voltage-mode compensation network is featured. To ensure stability, an external resistor and small value
capacitor can be added across the upper feedback resistor as a pole-zero pair to complete a type III (three pole,
two zero) compensation network. The compensation components recommended in Table 4 provide type III
compensation at an optimal control loop performance. The typical phase margin is 45° with a bandwidth of 80
kHz. Calculated output capacitance values not listed in Table 4 should be verified before designing into
production. The detailed application note AN-2013 LMZ1050x/LMZ1050xEXT SIMPLE SWITCHER Power
Module (SNVA417) is available to provide verification support. In general, calculated output capacitance values
below the suggested value will have reduced phase margin and higher control loop bandwidth. Output
capacitance values above the suggested values will experience a lower bandwidth and increased phase margin.
Higher bandwidth is associated with faster system response to sudden changes such as load transients. Phase
margin changes the characteristics of the response. Lower phase margin is associated with underdamped ringing
and higher phase margin is associated with overdamped response. Losing all phase margin will cause the
system to be unstable; an optimized area of operation is 30° to 60° of phase margin, with a bandwidth of 100
kHz ±20 kHz.
Figure 22. Loop Compensation Control Components
Table 4. LMZ10503 Compensation Component Values
VIN (V) CO(µF) ESR (mΩ)Rfbt (kΩ)(1) Ccomp (pF)(1) Rcomp (kΩ)(1)
MIN MAX
5
22 2 20 150 47 1
47 2 20 100 100 4.53
100 1 10 71.5 180 2
150 1 5 56.2 270 0.499
150 10 25 100 180 4.53
150 26 50 182 100 8.25
220 15 30 133 160 4.99
220 31 60 200 100 6.98