Publication Order Number: © 2010 Semiconductor Components Industries, LLC.
December-2017, Rev. 3 FAN7930C/D
FAN7930C — Critical Conduction Mode PFC Controller
FAN7930C
Critical Conduction Mode PFC Controller
Features
PFC-Ready Signal
VIN-Absent Detection
Maximum Switching Frequency Limitation
Internal Soft-Start and Startup without Overshoot
Internal Total Harmonic Distortion (THD) Optimizer
Precise Adjustable Output Over-Voltage Protection
Open-Feedback Protection and Disable Function
Zero-Current Detector (ZCD)
150 μs Internal Startup Timer
MOSFET Over-Current Protection (OCP)
Under-Voltage Lockout with 3.5 V Hysteresis
Low Startup and Operating Current
Totem-Pole Output with High State Clamp
+500/-800 mA Peak Gate Drive Current
8-Pin, Small Outline Package (SOP)
Applications
Adapter
Ballast
LCD TV, CRT TV
SMPS
Description
The FAN7930C is an active power factor correction
(PFC) controller for boost PFC applications that operate
in critical conduction mode (CRM). It uses a voltage-
mode PWM that compares an internal ramp signal with
the error amplifier output to generate a MOSFET turn-off
signal. Because the voltage-mode CRM PFC controller
does not need rectified AC line voltage information, it
saves the power loss of an input voltage-sensing network
necessary for a current-mode CRM PFC controller.
FAN7930C provides over-voltage protection (OVP),
open-feedback protection, over-current protection
(OCP), input-voltage-absent detection, and under-
voltage lockout protection (UVLO). The PFC-ready pin
can be used to trigger other power stages when PFC
output voltage reaches the proper level with hysteresis.
The FAN7930C can be disabled if the INV pin voltage is
lower than 0.45 V and the operating current decreases
to a very low level. Using a new variable on-time control
method, total harmonic distortion (THD) is lower than in
conventional CRM boost PFC ICs.
Related Resources
AN-8035 — Design Consideration for Boundary
Conduction Mode PFC Using FAN7930
Ordering Information
Part Number
Operating
Temperature Range
Top Mark
Package
Packing
Method
FAN7930CMX-G
-40 to +125°C
7930C
8-Lead, Small Outline Package (SOP)
Tape & Reel
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FAN7930C — Critical Conduction Mode PFC Controller
Application Diagram
AC INPUT
DC OUTPUT
line filter
PFC
ready
1
7
6
8
5
34
2
FAN7930C
COMP INV
VCC Out
GND
ZCD CS
RDY
Vcc
Figure 1. Typical Boost PFC Application
Internal Block Diagram
Figure 2. Functional Block Diagram
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FAN7930C — Critical Conduction Mode PFC Controller
Pin Configuration
INV RDY CS
ZCD
FAN7930C
8-SOP
COMP
VCC OUT GND
Figure 3. Pin Configuration (Top View)
Pin Definitions
Pin #
Name
Description
1
INV
This pin is the inverting input of the error amplifier. The output voltage of the boost PFC converter
should be resistively divided to 2.5 V.
2
RDY
This pin is used to detect PFC output voltage reaching a pre-determined value. When output
voltage reaches 89% of rated output voltage, this pin is pulled HIGH, which is an (open-drain)
output type.
3
COMP
This pin is the output of the transconductance error amplifier. Components for the output voltage
compensation should be connected between this pin and GND.
4
CS
This pin is the input of the over-current protection comparator. The MOSFET current is sensed
using a sensing resistor and the resulting voltage is applied to this pin. An internal RC filter is
included to filter switching noise.
5
ZCD
This pin is the input of the zero-current detection (ZCD) block. If the voltage of this pin goes
higher than 1.5 V, then goes lower than 1.4 V, the MOSFET is turned on.
6
GND
This pin is used for the ground potential of all the pins. For proper operation, the signal ground
and the power ground should be separated.
7
OUT
This pin is the gate drive output. The peak sourcing and sinking current levels are +500 mA and
-800 mA, respectively. For proper operation, the stray inductance in the gate driving path must be
minimized.
8
VCC
This is the IC supply pin. IC current and MOSFET drive current are supplied using this pin.
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FAN7930C — Critical Conduction Mode PFC Controller
Absolute Maximum Ratings
Stresses exceeding the absolute maximum ratings may damage the device. The device may not function or be
operable above the recommended operating conditions and stressing the parts to these levels is not recommended.
In addition, extended exposure to stresses above the recommended operating conditions may affect device reliability.
The absolute maximum ratings are stress ratings only.
Symbol
Parameter
Min.
Max.
Unit
VCC
Supply Voltage
VZ
V
IOH, IOL
Peak Drive Output Current
-800
+500
mA
ICLAMP
Driver Output Clamping Diodes VO>VCC or VO<-0.3 V
-10
+10
mA
IDET
Detector Clamping Diodes
-10
+10
mA
VIN
RDY Pin(1)
VZ
V
Error Amplifier Input, Output and ZCD(1)
-0.3
8.0
CS Input Voltage(2)
-10.0
6.0
TJ
Operating Junction Temperature
+150
°C
TA
Operating Temperature Range
-40
+125
°C
TSTG
Storage Temperature Range
-65
+150
°C
ESD
Electrostatic Discharge
Capability
Human Body Model, JESD22-A114
2.5
kV
Charged Device Model, JESD22-C101
2.0
Notes:
1. When this pin is supplied by external power sources by accident, its maximum allowable current is 50 mA.
2. In case of DC input, the acceptable input range is -0.3 V~6 V: within 100 ns -10 V~6 V is acceptable, but
electrical specifications are not guaranteed during such a short time.
Thermal Impedance
Symbol
Parameter
Min.
Max.
Unit
JA
Thermal Resistance, Junction-to-Ambient(3)
150
°C/W
Note:
3. Regarding the test environment and PCB type, please refer to JESD51-2 and JESD51-10.
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FAN7930C — Critical Conduction Mode PFC Controller
Electrical Characteristics
VCC = 14 V and TA = -40°C~+125°C, unless otherwise specified.
Symbol
Parameter
Conditions
Min.
Typ.
Max.
Unit
VCC Section
VSTART
Start Threshold Voltage
VCC Increasing
11
12
13
V
VSTOP
Stop Threshold Voltage
VCC Decreasing
7.5
8.5
9.5
V
HYUVLO
UVLO Hysteresis
3.0
3.5
4.0
V
VZ
Zener Voltage
ICC=20 mA
20
22
24
V
VOP
Recommended Operating Range
13
20
V
Supply Current Section
ISTART
Startup Supply Current
VCC=VSTART-0.2 V
120
190
µA
IOP
Operating Supply Current
Output Not Switching
1.5
3.0
mA
IDOP
Dynamic Operating Supply Current
50 kHz, CI=1 nF
2.5
4.0
mA
IOPDIS
Operating Current at Disable
VINV=0 V
90
160
230
µA
Error Amplifier Section
VREF1
Voltage Feedback Input Threshold1
TA=25°C
2.465
2.500
2.535
V
VREF1
Line Regulation
VCC=14 V~20 V
0.1
10.0
mV
VREF2
Temperature Stability of VREF1(4)
20
mV
IEA,BS
Input Bias Current
VINV=1 V~4 V
-0.5
0.5
µA
IEAS,SR
Output Source Current
VINV=VREF -0.1 V
-12
µA
IEAS,SK
Output Sink Current
VINV=VREF +0.1 V
12
µA
VEAH
Output Upper Clamp Voltage
VINV=1 V, VCS=0 V
6.0
6.5
7.0
V
VEAZ
Zero-Duty Cycle Output Voltage
0.9
1.0
1.1
V
gm
Transconductance(4)
90
115
140
µmho
Maximum On-Time Section
tON,MAX1
Maximum On-Time Programming 1
TA=25°C, VZCD=1 V
35.5
41.5
47.5
µs
tON,MAX2
Maximum On-Time Programming 2
TA=25°C,
IZCD=0.469 mA
11.2
13.0
14.8
µs
Current-Sense Section
VCS
Current-Sense Input Threshold
Voltage Limit
0.7
0.8
0.9
V
ICS,BS
Input Bias Current
VCS=0 V~1 V
-1.0
-0.1
1.0
µA
tCS,D
Current-Sense Delay to Output(4)
dV/dt=1 V/100 ns,
from 0 V to 5 V
350
500
ns
Continued on the following page…
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FAN7930C — Critical Conduction Mode PFC Controller
Electrical Characteristics
VCC = 14 V and TA = -40°C~+125°C, unless otherwise specified.
Symbol
Parameter
Conditions
Min.
Typ.
Max.
Unit
Zero-Current Detect Section
VZCD
Input Voltage Threshold(4)
1.35
1.50
1.65
V
HYZCD
Detect Hysteresis(4)
0.05
0.10
0.15
V
VCLAMPH
Input High Clamp Voltage
IDET=3 mA
5.5
6.2
7.5
V
VCLAMPL
Input Low Clamp Voltage
IDET= -3 mA
0
0.65
1.00
V
IZCD,BS
Input Bias Current
VZCD=1 V~5 V
-1.0
-0.1
1.0
µA
IZCD,SR
Source Current Capability(4)
TA=25°C
-4
mA
IZCD,SK
Sink Current Capability(4)
TA=25°C
10
mA
tZCD,D
Maximum Delay From ZCD to Output
Turn-On(4)
dV/dt=-1 V/100 ns, from
5 V to 0 V
100
200
ns
Output Section
VOH
Output Voltage High
IO=-100 mA, TA=25°C
9.2
11.0
12.8
V
VOL
Output Voltage Low
IO=200 mA, TA=25°C
1.0
2.5
V
tRISE
Rising Time(4)
CIN=1 nF
50
100
ns
tFALL
Falling Time(4)
CIN=1 nF
50
100
ns
VO,MAX
Maximum Output Voltage
VCC=20 V, IO=100 µA
11.5
13.0
14.5
V
VO,UVLO
Output Voltage with UVLO Activated
VCC=5 V, IO=100 µA
1
V
Restart / Maximum Switching Frequency Limit Section
tRST
Restart Timer Delay
50
150
300
µs
fMAX
Maximum Switching Frequency(4)
250
300
350
kHz
RDY Pin
IRDY,SK
Output Sink Current
1
2
4
mA
VRDY,SAT
Output Saturation Voltage
IRDY,SK=2 mA
320
500
mV
IRDY,LK
Output Leakage Current
Output High Impedance
1
µA
Soft-Start Timer Section
tSS
Internal Soft-Soft(4)
3
5
7
ms
UVLO Section
VRDY
Output Ready Voltage
2.166
2.240
2.314
V
HYRDY
Output Ready Hysteresis
0.189
V
Protections
VOVP
OVP Threshold Voltage
TA=25°C
2.620
2.675
2.730
V
HYOVP
OVP Hysteresis
TA=25°C
0.120
0.175
0.230
V
VEN
Enable Threshold Voltage
0.40
0.45
0.50
V
HYEN
Enable Hysteresis
0.05
0.10
0.15
V
TSD
Thermal Shutdown Temperature(4)
125
140
155
°C
THYS
Hysteresis Temperature of TSD(4)
60
°C
Note:
4. These parameters, although guaranteed by design, are not production tested.
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FAN7930C — Critical Conduction Mode PFC Controller
Comparison of FAN7530 and FAN7930C
Function
FAN7530
FAN7930C
FAN7930C Advantages
PFC Ready Pin
None
Integrated
No External Circuit for PFC Output UVLO
Reduce Power Loss and BOM Cost Caused by
PFC Out UVLO Circuit
Versatile Open-Drain Pin
Frequency Limit
None
Integrated
Abnormal CCM Operation Prohibited
Abnormal Inductor Current Accumulation Can Be
Prohibited
VIN-Absent
Detection
None
Integrated
Increase System Reliability by Testing for Input
Supply Voltage
Guarantee Stable Operation at Short Electric
Power Failure
Soft-Start and
Startup without
Overshoot
None
Integrated
Reduce Voltage and Current Stress at Startup
Eliminate Audible Noise due to Unwanted OVP
Triggering
Control Range
Compensation
None
Integrated
Can Avoid Burst Operation at Light Load and High
Input Voltage
Reduce Probability of Audible Noise Due to Burst
Operation
THD Optimizer
External
Internal
No External Resistor Needed
TSD
None
140°C with
60°C Hysteresis
Stable and Reliable TSD Operation
Converter Temperature Range Limited Range
Comparison of FAN7930C and FAN7930B
Function
FAN7930C
FAN7930B
Remark
RDY Pin
Integrated
None
User Choice for the Use of Number #2 Pin
OVP Pin
None
Integrated
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FAN7930C — Critical Conduction Mode PFC Controller
Typical Performance Characteristics
Figure 4. Voltage Feedback Input Threshold 1 (VREF1)
vs. TA
Figure 5. Start Threshold Voltage (VSTART) vs. TA
Figure 6. Stop Threshold Voltage (VSTOP) vs. TA
Figure 7. Startup Supply Current (ISTART) vs. TA
Figure 8. Operating Supply Current (IOP) vs. TA
Figure 9. Output Upper Clamp Voltage (VEAH) vs. TA
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FAN7930C — Critical Conduction Mode PFC Controller
Typical Performance Characteristics
Figure 10. Zero Duty Cycle Output Voltage (VEAZ)
vs. TA
Figure 11. Maximum On-Time Program 1 (tON,MAX1)
vs. TA
Figure 12. Maximum On-Time Program 2 (tON,MAX2)
vs. TA
Figure 13. Current-Sense Input Threshold Voltage
Limit (VCS) vs. TA
Figure 14. Input High Clamp Voltage (VCLAMPH) vs. TA
Figure 15. Input Low Clamp Voltage (VCLAMPL) vs. TA
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FAN7930C — Critical Conduction Mode PFC Controller
Typical Performance Characteristics
Figure 16. Output Voltage High (VOH) vs. TA
Figure 17. Output Voltage Low (VOL) vs. TA
Figure 18. Restart Timer Delay (tRST) vs. TA
Figure 19. Output Ready Voltage (VRDY) vs. TA
Figure 20. Output Saturation Voltage (VRDY,SAT)
vs. TA
Figure 21. OVP Threshold Voltage (VOVP) vs. TA
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FAN7930C — Critical Conduction Mode PFC Controller
Applications Information
1. Startup: Normally, supply voltage (VCC) of a PFC
block is fed from the additional power supply, which can
be called standby power. Without this standby power,
auxiliary winding for zero current detection can be used
as a supply source. Once the supply voltage of the PFC
block exceeds 12 V, internal operation is enabled until
the voltage drops to 8.5 V. If VCC exceeds VZ, 20 mA
current is sinking from VCC.
VCC
VZ
+
-
VTH(S/S)
12
8.5
VCC’
2.5VREF
Internal
Bias
VBIAS
VREF
reset
H:open
20mA
PFC Inductor
Aux. Winding
VINPFC VOUTPFC
External VCC circuit
when no standby power exists
8
Figure 22. Startup Circuit
2. INV Block: Scaled-down voltage from the output is
the input for the INV pin. Many functions are embedded
based on the INV pin: transconductance amplifier,
output OVP comparator, disable comparator, and output
UVLO comparator.
For the output voltage control, a transconductance
amplifier is used instead of the conventional voltage
amplifier. The transconductance amplifier (voltage-
controlled current source) aids the implementation of
the OVP and disable functions. The output current of
the amplifier changes according to the voltage
difference of the inverting and non-inverting input of
the amplifier. To cancel down the line input voltage
effect on power factor correction, the effective control
response of the PFC block should be slower than the
line frequency and this conflicts w ith the transient
response of controller. Two-pole one-zero type
compensation can meet both requirements.
The OVP comparator shuts down the output drive block
when the voltage of the INV pin is higher than 2.675 V
and there is 0.175 V hysteresis. The disable comparator
disables operation when the voltage of the inverting input
is lower than 0.35 V and there is 100 mV hysteresis. An
external small-signal MOSFET can be used to disable the
IC, as shown in Figure 23. The IC operating current
decreases to reduce power consumption if the IC is
disabled. Figure 24 is the timing chart of the internal
circuit near the INV pin when rated PFC output voltage
is 390 VDC and VCC supply voltage is 15 V.
+
-
+
-
+
-
VOUTPFC
+
-
2.5V
0.45V/0.35V
INV open
2.675V/2.5V
OVP
2.240V/2.051V
UVLO
2.240
2.051
high
VCC’
disable
1INV
3COMP
2RDY
0.45
0.35
disable
2.675
2.5
disable
Figure 23. Circuit Around INV Pin
390Vdc
2.50V 2.65V
0.45V
Current sourcing Current sourcing
I sinking
0.35V
2.051V
2.24V 2.50V
2.0V
349V
413V 390V
320V
70V 55V
VOUTPFC
VINV
VCC
IOUTCOMP
Disable
VRDY
OVP
t
Voltage is decided by pull-up voltage.
Vcc<2V, internal logic is not alive.
- RDY pin is floating, so pull up voltage is shown.
- Internal signals are unknown.
15V
Figure 24. Timing Chart for INV Block
3. RDY Output: When the INV voltage is higher than
2.24 V, RDY output is triggered HIGH and lasts until the
INV voltage is lower than 2.051 V. When input AC
voltage is quite high, for example 240 VAC, PFC output
voltage is always higher than RDY threshold, regardless
of boost converter operation. In this case, the INV
voltage is already higher than 2.24 V before PFC VCC
touches VSTART; however, RDY output is not triggered to
HIGH until VCC touches VSTART. After boost converter
operation stops, RDY is not pulled LOW because the
INV voltage is higher than the RDY threshold. When VCC
of the PFC drops below 5 V, RDY is pulled LOW even
though PFC output voltage is higher than threshold. The
RDY pin output is open drain, so needs an external pull-
up resistor to supply the proper power source. The RDY
pin output remains floating until VCC is higher than 2 V.
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FAN7930C — Critical Conduction Mode PFC Controller
PFC operation
VCC
VSTART
VSTOP
5V
VINV(=VPFCOUT)
2.240V
2.051V
VRDY
2.500V
t
PFC operation
VCC
VSTART
VSTOP
5V
VINV(=VPFCOUT)
2.240V
2.051V
VRDY
2.500V
t
Figure 25. Two Cases of RDY Triggered HIGH
PFC operation
VCC
VSTART
VSTOP
5V
VINV(=VPFCOUT)
2.240V
2.051V
VRDY
2.500V
t
PFC operation
VCC
VSTART
VSTOP
5V
VINV(=VPFCOUT)
2.240V
2.051V
VRDY
2.500V
t
Figure 26. Two Cases of RDY Triggered LOW
4. Control Range Compensation: On time is controlled
by the output voltage compensator with FAN7930C.
Due to this when input voltage is high and load is light,
control range becomes narrow compared to when input
voltage is low. That control range decrease is inversely
proportional to the double square of the input voltage
(). Thus at high line,
unwanted burst operation easily happens at light load
and audible noise may be generated from the boost
inductor or inductor at input filter. Different from the
other converters, burst operation in PFC block is not
needed because the PFC block itself is normally
disabled during standby mode. To reduce unwanted
burst operation at light load, an internal control range
compensation function is implemented and shows no
burst operation until 5% load at high line.
5. Zero-Current Detection: Zero-current detection
(ZCD) generates the turn-on signal of the MOSFET
when the boost inductor current reaches zero using an
auxiliary winding coupled with the inductor. When the
power switch turns on, negative voltage is induced at the
auxiliary winding due to the opposite winding direction
(see Equation 1). Positive voltage is induced (see
Equation 2) when the power switch turns off.
AC
IND
AUX
AUX V
T
T
V
(1)
ACPFCOUT
IND
AUX
AUX VV
T
T
V
(2)
where:
VAUX is the auxiliary winding voltage;
TIND is boost inductor turns;
TIND auxiliary winding turns;
VAC is input voltage for PFC converter; and
VOUT_PFC is output voltage from the PFC converter.
PFC Inductor
Aux Winding
VINPFC VOUTPFC
ZCD
VTH(ZCD)
+
-
VCC
THD optimized
Sawtooth
Generator
Restart
Timer
gate
driver
RZCD
CZCD
Negative Clamp
Circuit
Positive Clamp
Circuit
5
S
Q
R
QfMAX
limit
optional
Figure 27. Circuit Near ZCD
Because auxiliary w inding voltage can sw ing from
negative to positive voltage, the internal block in ZCD
pin has both positive and negative voltage clamping
circuits. When the auxiliary voltage is negative, an
internal circuit clamps the negative voltage at the ZCD
pin around 0.65 V by sourcing current to the serial
resistor between the ZCD pin and the auxiliary
winding. When the auxiliary voltage is higher than
6.5 V, current is sinked through a resistor from the
auxiliary winding to the ZCD pin.
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FAN7930C — Critical Conduction Mode PFC Controller
ISW
VAUX & VZCD
VACIN
IMOSFET IDIODE
VAUX
VZCD
t
6.2V 0.65V
Figure 28. Auxiliary Voltage Depends on
MOSFET Switching
The auxiliary winding voltage is used to check the boost
inductor current zero instance. When boost inductor
current becomes zero, there is a resonance between
boost inductor and all capacitors at the MOSFET drain
pin: including COSS of the MOSFET; an external
capacitor at the D-S pin to reduce the voltage rising and
falling slope of the MOSFET; a parasitic capacitor at
inductor; and so on to improve performance. Resonated
voltage is reflected to the auxiliary w inding and can be
used for detecting zero current of boost inductor and
valley position of MOSFET voltage stress. For valley
detection, a minor delay by the resistor and capacitor is
needed. A capacitor increases the noise immunity at the
ZCD pin. If ZCD voltage is higher than 1.5 V, an internal
ZCD comparator output becomes HIGH and LOW when
the ZCD goes below 1.4 V. At the falling edge of
comparator output, internal logic turns on the MOSFET
VIN
VOUTPFC - VIN
1.5V
150ns Delay
1.4V
ON
ON
VOUTPFC - VIN
IMOSFET IDIODE
VZCD
t
IINDUCTOR
VDS
MOSFET gate
Figure 29. Auxiliary Voltage Threshold
When no ZCD signal is available, the PFC controller
cannot turn on the MOSFET, so the controller checks
every switching off time and forces MOSFET turn on
when the off time is longer than 150 μs. This restart
timer triggers MOSFET turn-on at startup and may be
used at the input voltage zero-cross period.
VOUT
VIN
VCC
tRESTART
MOSFET gate
ZCD after COMPARATOR
t
s150
Figure 30. Restart Timer at Startup
Because the MOSFET turn-on depends on the ZCD
input, switching frequency may increase to higher than
several megahertz due to the mis-triggering or noise on
the nearby ZCD pin. If the switching frequency is higher
than needed for critical conduction mode (CRM),
operation mode shifts to continuous conduction mode
(CCM). In CCM, unlike CRM where the boost inductor
current is reset to zero at the next switch on; inductor
current builds up at every switching cycle and can be
raised to very high current that exceeds the current
rating of the power switch or diode. This can seriously
damage the power switch. To avoid this, maximum
switching frequency limitation is embedded. If ZCD
signal is applied again within 3.3 μs after the previous
rising edge of gate signal, this signal is ignored
internally and FAN7930C waits for another ZCD signal.
This slightly degrades the power factor performance at
light load and high input voltage.
ZCD after COMPARATOR
MOSFET Gate
Max. fSW Limit
Inhibit Region
Error occurs!
Ignores ZCD noise
t
Figure 31. Maximum Switching Frequency
Limit Operation
6. Control: The scaled output is compared with the
internal reference voltage and sinking or sourcing
current is generated from the COMP pin by the
transconductance amplifier. The error amplifier output is
compared with the internal saw tooth waveform to give
proper turn-on time based on the controller.
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FAN7930C — Critical Conduction Mode PFC Controller
VOUTPFC
+
-
INV 1
COMP 3
Clamp
Circuit
+
-
VREF
Stair
Step
THD-Optimized
Sawtooth
Generator Sawtooth MOSFET Off
R1
C1
C2
1V
6.2V
Figure 32. Control Circuit
Unlike a conventional voltage-mode PWM controller,
FAN7930C turns on the MOSFET at the falling edge of
ZCD signal. The “ ON” instant is determined by the
external signal and the turn-on time lasts until the error
amplifier output (VCOMP) and sawtooth waveform meet.
When load is heavy, output voltage decreases, scaled
output decreases, COMP voltage increases to
compensate low output, turn-on time lengthens to give
more inductor turn-on time, and increased inductor
current raises the output voltage. This is how a PFC
negative feedback controller regulates output.
The maximum of VCOMP is limited to 6.5 V, which
dictates the maximum turn-on time. Switching stops
when VCOMP is lower than 1.0 V.
ZCD after COMPARATOR
VCOMP & Sawtooth
MOSFET gate
t
s/V155.0
Figure 33. Turn-On Time Determination
The roles of PFC controller are regulating output voltage
and input current shaping to increase power factor. Duty
control based on the output voltage should be fast
enough to compensate output voltage dip or overshoot.
For the power factor, however, the control loop must not
react to the fluctuating AC input voltage. These two
requirements conflict; therefore, when designing a
feedback loop, the feedback loop should be least ten
times slower than AC line frequency. That slow
response is made by C1 at the compensator. R1 makes
gain boost around operation region and C2 attenuates
gain at higher frequency. Boost gain by R1 helps raise
the response time and improves phase margin.
Freq.
C1
R1
Proportional
gain
C2
Integrator
High-Frequency
Noise Filter
Gain
Figure 34. Compensators Gain Curve
For the transconductance error amplifier side, gain
changes based on differential input. When the error is
large, gain is large to suppress the output dip or peak
quickly. When the error is small, low gain is used to
improve power factor performance.
ICOMP
SourcingSinking
Powering
Braking
2.5V
2.4V
2.6V
mho250
mho115
Figure 35. Gain Characteristic
7. Soft-Start: When VCC reaches VSTART, the internal
reference voltage is increased like a stair step for 5 ms.
As a result, VCOMP is also raised gradually and MOSFET
turn-on time increases smoothly. This reduces voltage
and current stress on the power switch during startup.
VREFSS
gM
VINV=0.4V
ISOURCECOMP
VCOMP ISOURCECOMP RCOMP=VCOMP
t
(VREFSS-VINV) gM=ISOURCECOMP
VREFEND=2.5V
5ms
VCC
VSTART=12V
Figure 36. Soft-Start Sequence
8. Startup without Overshoot: Feedback control speed
of PFC is quite slow. Due to the slow response, there is
a gap between output voltage and feedback control.
That is why over-voltage protection (OVP) is critical at
the PFC controller and voltage dip caused by fast load
changes from light to heavy is diminished by a bulk
capacitor. OVP is triggered during startup phase.
Operation on and off by OVP at startup may cause
audible noise and can increase voltage stress at startup,
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15
FAN7930C — Critical Conduction Mode PFC Controller
which is normally higher than in normal operation. This
operation is improved when soft-start time is very long.
However, too much startup time enlarges the output
voltage building time at light load. FAN7930C has
overshoot protection at startup. During startup, the
feedback loop is controlled by an internal proportional
gain controller and, when the output voltage reaches the
rated value, it switches to an external compensator after
a transition time of 30 ms. This internal proportional gain
controller eliminates overshoot at startup and an
external conventional compensator takes over
successfully afterward.
Depends on Load
VOUT
VCOMP
Startup Overshoot
Internal Controller
t
Conventional Controller
Startup Overshoot Control
Control Transition
Figure 37. Startup without Overshoot
9. THD Optimization: Total Harmonic Distortion (THD)
is the factor that dictates how closely input current
shape matches sinusoidal form. The turn-on time of the
PFC controller is almost constant over one AC line
period due to the extremely low feedback control
response. The turn-off time is determined by the current
decrease slope of the boost inductor made by the input
voltage and output voltage. Once inductor current
becomes zero, resonance between COSS and the boost
inductor makes oscillating waveforms at the drain pin
and auxiliary winding. By checking the auxiliary winding
voltage through the ZCD pin, the controller can check
the zero current of boost inductor. At the same time, a
minor delay is inserted to determine the valley position
of drain voltage. The input and output voltage difference
is at its maximum at the zero cross point of AC input
voltage. The current decrease slope is steep near the
zero cross region and more negative inductor current
flow s during a drain voltage valley detection time. Such
a negative inductor current cancels down the positive
current flows and input current becomes zero, called
“zero-cross distortion” in PFC.
1.5V
150ns
1.4V
ON
VZCD
t
IINDUCTOR
MOSFET gate
INEGATIVE
ON
IIN
IMOSFET IDIODE
Figure 38. Input and Output Current Near Input
Voltage Peak
1.5V
150ns
1.4V
ON
ON
VZCD
t
IINDUCTOR
MOSFET gate
INEGATIVE
ON ON
IIN
Figure 39. Input and Output Current Near Input
Voltage Peak Zero Cross
To improve this, lengthened turn-on time near the zero
cross region is a well-known technique, though the
method may vary and may be proprietary. FAN7930C
optimizes this by sourcing current through the ZCD pin.
Auxiliary winding voltage becomes negative when the
MOSFET turns on and is proportional to input voltage.
The negative clamping circuit of ZCD outputs the
current to maintain the ZCD voltage at a fixed value.
The sourcing current from the ZCD is directly
proportional to the input voltage. Some portion of this
current is applied to the internal saw tooth generator,
together with a fixed-current source. Theoretically, the
fixed-current source and the capacitor at sawtooth
generator determine the maximum turn-on time when no
current is sourcing at ZCD clamp circuit and available
turn-on time gets shorter proportional to the ZCD
sourcing current.
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16
FAN7930C — Critical Conduction Mode PFC Controller
RZCD
VAUX
ZCD
Zero-Current
Detect
5
Vcc
N
1
VREF
IMOT
reset
Sawtooth Generator
CMOT
THD Optimizer
Figure 40. Circuit of THD Optimizer
VZCD
tON
t
VZCD at FET on
tON get shorter
tON not shorter
tON is typically constant over 1 AC line frequency,
but tON is changed by ZCD voltage.
Figure 41. Effect of THD Optimizer
By THD optimizer, turn-on time over one AC line period
is proportionally changed, depending on input voltage.
Near zero cross, lengthened turn-on time improves THD
performance.
10. VIN-Absent Detection: To save power loss caused
by input voltage sensing resistors and to optimize THD,
the FAN7930C omits AC input voltage detection.
Therefore, no information about AC input is available
from the internal controller. In many cases, the VCC of
PFC controller is supplied by an independent power
source, like standby power. In this scheme, some
mismatch may exist. For example, when the electric
power is suddenly interrupted during two or three AC
line periods; VCC is still live during that time, but output
voltage drops because there is no input power source.
Consequently, the control loop tries to compensate for
the output voltage drop and VCOMP reaches its
maximum. This lasts until AC input voltage is live again.
When AC input voltage is live again, high VCOMP allows
high switching current and more stress is put on the
MOSFET and diode. To protect against this, FAN7930C
checks if the input AC voltage exists. If input does not
exist, soft-start is reset and waits until AC input is live
again. Soft-start manages the turn-on time for smooth
operation when it detects AC input is applied again and
applies less voltage and current stress on startup.
VIN
t
VOUT
VAUX
MOSFET gate
IDS
fMIN DMAX
High drain
current!
VCOMP
Though VIN is
eliminated, operation of
controller is normal due
to the large bypass
capacitor.
Figure 42. Without VIN-Absent Circuit
VIN
t
VOUT
VAUX
MOSFET gate
IDS
fMIN
DMAX
VIN Absence Detected
NewVCOMP
Though VIN is
eliminated, operation of
controller is normal due
to the large bypass
capacitor.
fMIN DMIN
Smooth
Soft-Start
Figure 43. With VIN-Absent Circuit
11. Current Sense: The MOSFET current is sensed
using an external sensing resistor for over-current
protection. If the CS pin voltage is higher than 0.8 V, the
over-current protection comparator generates a
protection signal. An internal RC filter of 40 kΩ and 8 pF
is included to filter switching noise.
12. Gate Driver Output: FAN7930C contains a single
totem-pole output stage designed for a direct drive of
the power MOSFET. The drive output is capable of up
to +500 / -800 mA peak current with a typical rise and
fall time of 50 ns with 1 nF load. The output voltage is
clamped to 13 V to protect the MOSFET gate even if the
VCC voltage is higher than 13 V.
www.onsemi.com
17
FAN7930C — Critical Conduction Mode PFC Controller
PCB Layout Guide
PFC block normally handles high switching current and
the voltage low energy signal path can be affected by
the high energy path. Cautious PCB layout is mandatory
for stable operation.
1. The gate drive path should be as short as possible.
The closed-loop that starts from the gate driver,
MOSFET gate, and MOSFET source to ground of
PFC controller should be as close as possible. This
is also crossing point between power ground and
signal ground. Power ground path from the bridge
diode to the output bulk capacitor should be short
and wide. The sharing position between power
ground and signal ground should be only at one
position to avoid ground loop noise. Signal path of
the PFC controller should be short and wide for
external components to contact.
2. The PFC output voltage sensing resistor is normally
high to reduce current consumption. This path can
be affected by external noise. To reduce noise
potential at the INV pin, a shorter path for output
sensing is recommended. If a shorter path is not
possible, place some dividing resistors between
PFC output and the INV pin — closer to the INV pin
is better. Relative high voltage close to the INV pin
can be helpful.
3. The ZCD path is recommended close to auxiliary
winding from boost inductor and to the ZCD pin. If
that is difficult, place a small capacitor (below
50 pF) to reduce noise.
4. The switching current sense path should not share
with another path to avoid interference. Some
additional components may be needed to reduce
the noise level applied to the CS pin.
5. A stabilizing capacitor for VCC is recommended as
close as possible to the VCC and ground pins. If it is
difficult, place the SMD capacitor as close to the
corresponding pins as possible.
Figure 44. Recommended PCB Layout
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18
FAN7930C — Critical Conduction Mode PFC Controller
Typical Application Circuit
Application
Device
Input Voltage
Range
Rated Output
Power
Output Voltage
(Maximum Current)
LCD TV Power Supply
FAN7930C
90-265 VAC
195 W
390 V (0.5 A)
Features
Average efficiency of 25%, 50%, 75%, and 100% load conditions is higher than 95% at universal input.
Power factor at rated load is higher than 0.98 at universal input.
Total Harmonic Distortion (THD) at rated load is lower than 15% at universal input.
Key Design Notes
When auxiliary VCC supply is not available, VCC power can be supplied through Zero Current Detect (ZCD)
winding. The power consumption of R103 is quite high, so its power rating needs checking.
Because the input bias current of INV pin is almost zero, output voltage sensing resistors (R112~R115) should
be as high as possible. However, too-high resistance makes the node susceptible to noise. Resistor values need
to strike a balance between power consumption and noise immunity.
Quick charge diode (D106) can be eliminated if output diode inrush current capability is sufficient. Even without
D106, system operation is normal due to the controller’s highly reliable protection features.
Schematic
ZNR101
,10D471
194µH, 39:5 D105
600V 8A
VAUX
DC OUTPUT
Q101
FCPF
20N60
D106
600V 3A
FS101,
250V,5
A
R101,1M-
J
C101,
220nF
C114
,2.2n
F
LF101
,23mH
C102,
680nF
TH101
,5D15
BD101,
600V,15A
C1030,68m
F,630Vdc
C107
,33m
F
C105, 100nF
R107
,10k C108,
220nF
C109
,47n
F
R110,10k
R109
47
R108
4.7 D103,1N414
8
D104,1N414
8
C112,470p
F
R111
0.08, 5W
C110,1n
F
R115
75k
R112
3.9M
C111
220mF, 450V
LP101,EER3019N
R113
3.9M R114
3.9M
R104,
30k
1
7
6
8
5
2Comp INV
VCC Out
GND
ZCD CS
RDY
4
3
C115
,2.2n
F
R103,
10k,1W
D102,
UF4004
C104,
12nF
D101,1N474
6
R102,
330k
Circuit for VCC. If external VCC is used, this circuit is not needed.
VCC for another power stage
Circuit for VCC for another power stage thus components structure and values may vary.
Optional
Figure 45. Demonstration Circuit
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19
FAN7930C — Critical Conduction Mode PFC Controller
Transformer
1,2
Np
Naux 9,10 6,7
3,4
EER3019N
9,10
6,7
1,2
3,4
NP
Naux
Figure 46. Transformer Schematic Diagram
Winding Specification
Position
No
Pin (S → F)
Wire
Turns
Winding Method
Bottom
Np
3, 4 → 1, 2
0.1φ×50
39
Solenoid Winding
Insulation: Polyester Tape t = 0.05mm, 3 Layers
Top
NAUX
9,10 → 6,7
0.3φ
5
Solenoid Winding
Insulation: Polyester Tape t = 0.05 mm, 4 Layers
Electrical Characteristics
Pin
Specification
Remark
Inductance
3, 4 → 1, 2
194 H ±5%
100 kHz, 1 V
Core & Bobbin
Core: EER3019, Samhwa (PL-7) (Ae=137.0mm2)
Bobbin: EER3019
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20
FAN7930C — Critical Conduction Mode PFC Controller
Bill of Materials
Part #
Value
Note
Part #
Value
Note
Resistor
Switch
R101
1 MΩ
1W
Q101
FCPF20N60
20 A, 600 V, SuperFET®
R102
330 kΩ
1/2W
Diode
R103
10 kΩ
1W
D101
1N4746
1 W, 18 V, Zener Diode
R104
30 kΩ
1/4W
D102
UF4004
1 A, 400 V Glass Passivated
High-Efficiency Rectifier
R107
10 kΩ
1/4W
D103
1N4148
1 A, 100 V Small-Signal Diode
R108
4.7 kΩ
1/4W
D104
1N4148
1 A, 100 V Small-Signal Diode
R109
47 kΩ
1/4W
D105
8 A, 600 V, General-Purpose
Rectifier
R110
10 kΩ
1/4W
D106
3 A, 600 V, General-Purpose
Rectifier
R111
0.80 kΩ
5W
R112,
113, 114
3.9 kΩ
1/4W
IC101
FAN7930C
CRM PFC Controller
R115
75 kΩ
1/4W
Capacitor
Fuse
C101
220 nF / 275 VAC
Box Capacitor
FS101
5 A / 250 V
C102
680 nF / 275 VAC
Box Capacitor
NTC
C103
0.68 µF / 630 V
Box Capacitor
TH101
5D-15
C104
12 nF / 50 V
Ceramic Capacitor
Bridge Diode
C105
100 nF / 50 V
SMD (1206)
BD101
15 A, 600 V
C107
33 µF / 50 V
Electrolytic
Capacitor
Line Filter
C108
220 nF / 50 V
Ceramic Capacitor
LF101
23 mH
C109
47 nF / 50 V
Ceramic Capacitor
Transformer
C110
1 nF / 50 V
Ceramic Capacitor
T1
EER3019
Ae=137.0 mm2
C112
47 nF / 50 V
Ceramic Capacitor
ZNR
C111
220 µF / 450 V
Electrolytic
Capacitor
ZNR101
10D471
C114
2.2 nF / 450 V
Box Capacitor
C115
2.2 nF / 450 V
Box Capacitor
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21
FAN7930C — Critical Conduction Mode PFC Controller
Physical Dimensions
Figure 47. 8-Lead, Small Outline Package (SOP)
Package drawings are provided as a service to customers considering ON Semiconductor components. Drawings may change in
any manner without notice. Please note the revision and/or date on the drawing and contact a ON Semiconductor representative to
verify or obtain the most recent revision. Package specifications do not expand the terms of ON Semiconductor’s worldwide terms
and conditions, specifically the warranty therein, which covers ON Semiconductor products.
8°
0°
SEE DETAIL A
NOTES: UNLESS OTHERWISE SPECIFIED
A) THIS PACKAGE CONFORMS TO JEDEC
MS-012, VARIATION AA.
B) ALL DIMENSIONS ARE IN MILLIMETERS.
C) DIMENSIONS DO NOT INCLUDE MOLD
FLASH OR BURRS.
D) LANDPATTERN STANDARD: SOIC127P600X175-8M.
E) DRAWING FILENAME: M08Arev14
F) FAIRCHILD SEMICONDUCTOR.
LAND PATTERN RECOMMENDATION
SEATING PLANE
C
GAGE PLANE
x 45°
DETAIL A
SCALE: 2:1
PIN ONE
INDICATOR 4
8
1
B
5
A
5.60
0.65
1.75
1.27
6.20
5.80
3.81
4.00
3.80
5.00
4.80
(0.33) 1.27
0.51
0.33
0.25
0.10
1.75 MAX 0.25
0.19
0.36
0.50
0.25
R0.10
R0.10
0.90
0.40 (1.04)
OPTION A - BEVEL EDGE
OPTION B - NO BEVEL EDGE
0.25 C B A
0.10
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22
FAN7930C — Critical Conduction Mode PFC Controller
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