TDA46053HKLA1 - INFINEON TECHNOLOGIES AG

PWM-QR IC

TDA4605-3

Control IC for Switched-Mode

Power Supplies using

MOS-Transistors

Never stop thinking.

Power Management & Supply

Datasheet, V2.0, 1 Jul 2002

Edition 2002-07-01

Published by Infineon Technologies AG,

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D-81541 München

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TDA4605-3

Revision History: 2002-07-01 Datasheet

Previous Version:

Page Subjects (major changes since last revision)

The IC TDA 4605-3 controls the MOS-power transistor and performs all necessary control and

protection functions in free running flyback converters. Because of the fact that a wide load range

is achieved, this IC is applicable for consumer as well as industrial power supplies.

The serial circuit and primary winding of the flyback transformer are connected in series to the input

voltage. During the switch-on period of the transistor, energy is stored in the transformer. During the

switch-off period the energy is fed to the load via the secondary winding. By varying switch-on time

of the power transistor, the IC controls each portion of energy transferred to the secondary side

such that the output voltage remains nearly independent of load variations. The required control

information is taken from the input voltage during the switch-on period and from a regulation winding

during the switch-off period. A new cycle will start if the transformer has transferred the stored

energy completely into the load.

Type Ordering Code Package

TDA 4605-3 Q67000-A5066 P-DIP-8-1

Control IC for Switched-Mode Power Supplies

using MOS-Transistor

Bipolar IC

TDA 4605-3

P-DIP-8-1

Features

●Fold-back characteristics provides overload protection for

external components

●Burst operation under secondary short-circuit condition

implemented

●Protection against open or a short of the control loop

●Switch-off if line voltage is too low (undervoltage switch-off)

●Line voltage depending compensation of fold-back point

●Soft-start for quiet start-up without noise generated by the

transformer

●Chip-over temperature protection implemented (thermal

shutdown)

●On-chip ringing suppression circuit against parasitic

oscillations of the transformer

●AGC-voltage reduction at low load

Version 2.0 3 1 Jul 2002

Version 2.0 4 1 Jul 2002

TDA 4605-3

In the different load ranges the switched-mode power supply (SMPS) behaves as follows:

No load operation

The power supply is operating in the burst mode at typical 20 to 40 kHz. The output voltage can be

a little bit higher or lower than the nominal value depending of the design of the transformer and the

resistors of the control voltage divider.

Nominal operation

The switching frequency is reduced with increasing load and decreasing AC-voltage.

The output voltage is only dependent on the load.

Overload point

Maximal output power is available at this point of the output characteristic.

Overload

The energy transferred per operation cycle is limited at the top. Therefore the output voltages

declines by secondary overloading.

Version 2.0 5 1 Jul 2002

TDA 4605-3

Pin Definitions and Functions

Pin No. Function

1Information Input Concerning Secondary Voltage. By comparing the

regulating voltage - obtained trom the regulating winding of the transformer - with

the internal reference voltage, the output impulse width on pin 5 is adjusted to the

load of the secondary side (normal, overload, short-circuit, no load).

2Information Input Regarding the Primary Current. The primary current rise in

the primary winding is simulated at pin 2 as a voltage rise by means of external

RC-element. When a voltage level is reached thats derived from the regulating

voltage at pin 1, the output impulse at pin 5 is terminated. The RC-element serves

to set the maximum power at the overload point set.

3Input for Primary Voltage Monitoring: In the normal operation V3 is moving

between the thresholds V3H and V3L (V3H > V3 > V3L).

V3<V3L: SMPS is switched OFF (line voltage too low).

V3 > V3H : Compensation of the overload point regulation (controlled by pin 2)

starts at V3H :V3L = 1.7.

4Ground

5Output: Push-pull output provides ±1 A for rapid charge and discharge of the

gate capacitance of the power MOS-transistor.

6Supply Voltage Input: A stable internal reference voltage VREF is derived from

the supply voltage also the switching thresholds V6A ,V6E ,V6 max and V6 min for

the supply voltage detector. If V6 > V6E then VREF is switched on and swiched off

when V6<V6A . In addition the logic is only enable for V6 min <V6<V6 max.

7Input for Soft-Start. Start-up will begin with short pulses by connecting a

capacitor from pin 7 to ground.

8Input for the Oscillation Feedback. After starting oscillation, every zero

transition of the feedback voltage (falling edge) through zero (falling edge)

triggers an output pulse at pin 5. The trigger threshold is at + 50 mV typical.

Version 2.0 6 1 Jul 2002

TDA 4605-3

Block Diagram

Version 2.0 7 1 Jul 2002

TDA 4605-3

Circuit Description

Application Circuit

The application circuit shows a flyback converter for video recorders with an output power rating of

70 W. The circuit is designed as a wide-range power supply for AC-line voltages of 180 to 264 V.

The AC-input voltage is rectified by the bridge rectifier GR1 and smoothed by C1. The NTC limits

the rush-in current.

In the period before the switch-on threshold is reached the IC is suppled via resistorR1; during the

start-up phase it uses the energy stored in C2, under steady state conditions the IC receives its

supply voltage from transformer winding n1 via diode D1. The switching transistor T1 is a BUZ 90.

The parallel connected capacitor C3 and the inductance of primary winding n2 determine the

system resonance frequency. The R2-C4-D2 circuitry limits overshoot peaks, and R3 protects the

gate of T1 against static charges.

During the conductive phase of the power transistor T1 the current rise in the primary winding

depends on the winding inductance and the mains voltage. The network consisting ofR4-C5 is used

to create a model of the sawtooth shaped rise of the collector current. The resulting control voltage

is fed into pin 2 of the IC. The RC-time constant given by R4-C5 must be designed that way that

driving the transistor core into saturation is avoided.

The ratio of the voltage divider R10/R11 is fixing a voltage level threshold. Below this threshold the

switching power supply shall stop operation because of the low mains voltage. The control voltage

present at pin 3 also determines the correction current for the fold-back point. This current added to

the current flowing throughR4 and represents an additional charge toC5 in order to reduce the turn-

on phase of T1. This is done to stabilize the fold-back point even under higher mains voltages.

Regulation of the switched-mode power supplies via pin 1. The control voltage of winding n1 during

the off period of T1 is rectified by D3, smoothed by C6 and stepped down at an adjustable ratio by

R5,R6 and R7. The R8-C7 network suppresses parasitic overshoots (transformer oscillation). The

peak voltage at pin 2, and thus the primary peak current, is adjusted by the IC so that the voltage

applied across the control winding, and hence the output voltages, are at the desired level.

When the transformer has supplied its energy to the load, the control voltage passes through zero.

The IC detects the zero crossing via series resistors R9 connected to pin 8. But zero crossings are

also produced by transformer oscillation after T1 has turned off if output is short-circuited. Therefore

the IC ignores zero crossings occurring within a specified period of time after T1 turn-off.

The capacitor C8 connected to pin 7 causes the power supply to be started with shorter pulses to

keep the operating frequency outside the audible range during start-up.

On the secondary side, five output voltages are produced across winding n3 to n7 rectified by D4 to

D8 and smoothed by C9 to C13 . Resistors R12 ,R14 and R19 to R21 are used as bleeder resistors.

Fusable resistors R15 to R18 protect the rectifiers against short circuits in the output circuits, which

are designed to supply only small loads.

Version 2.0 8 1 Jul 2002

TDA 4605-3

Block Diagram

Pin 1

The regulating voltage forwarded to this pin is compared with a stable internal reference voltage VR

in the regulating and overload amplifier. The output of this stage is fed to the stop comparator. If

the control voltage is rather small at pin 1 an additional current is added by means of current source

which is controlled according the level at pin 7. This additional current is virtually reducing the

control voltage present at pin 1.

Pin 2

A voltage proportional to the drain current of the switching transistor is generated there by the

external RC-combination in conjunction with the primary current transducer. The output of this

transducer is controlled by the logic and referenced to the internal stable voltageV2B . If the voltage

V2 exceeds the output voltage of the regulations amplifier, the logic is reset by the stop comparator

and consequently the output of pin 5 is switched to low potential. Further inputs for the logic stage

are the output for the start impulse generator with the stable reference potential VST and the

supply voltage motor.

Pin 3

The down divided primary voltage applied there stabilizes the overload point. In addition the logic is

disabled in the event of low voltage by comparison with the internal stable voltageVV in theprimary

voltage monitor block.

Pin 4

Ground

Pin 5

In the output stage the output signals produced by the logic are shifted to a level suitable for MOS-

power transistors.

Pin 6

From the supply voltage V6 are derived a stable internal references VREF and the switching

threshold V6A ,V6E ,V6 max and V6 min for the supply voltage monitor. All references values (VR,

V2B ,VST) are derived from VREF . If V6 > VVE , the VREF is switched on and switched off when V6 <

V6A . In addition, the logic is released only for V6 min < V6 < V6 max .

Pin 7

The output of the overload amplifier is connected to pin 7. A load on this output causes a reduction

in maximal impulse duration. This function can be used to implement a soft start, when pin 7 is

connected to ground by a capacitor.

Version 2.0 9 1 Jul 2002

TDA 4605-3

Pin 8

The zero detector controlling the logic block recognizes the transformer being discharged by

positive to negative zero crossing of pin 8 voltage and enables the logic for a new pulse. Parasitic

oscillations occurring at the end of a pulse cannot lead to a new pulse (double pulsing), because an

internal circuit inhibits the zero detector for a finite time tUL after the end of each pulse.

Start-Up Behaviour

The start-up behaviour of the application circuit per sheet 88 is represented an sheet 90 for a line

voltage barely above the lower acceptable limit time t0 the following voltages built up:

–V6 corresponding to the half-wave charge current over R1

–V2 to V2 max (typically 6.6 V)

–V3 to the value determined by the divider R10/R11 .

The current drawn by the IC in this case is less than 1.6 mA.

If V6 reaches the thresholdV6E (time pointt1), the IC switches on the internal reference voltage. The

current draw max. rises to 12 mA. The primary current- voltage reproducer regulatesV2 down toV2B

and the starting impulse generator generates the starting impulses from time point t5 to t6. The

feedback to pin 8 starts the next impulse and so on. All impulses including the starting impulse are

controlled in width by regulating voltage of pin 1. When switching on this corresponds to a short-

circuit event, i.e. V1 = 0. Hence the IC starts up with "short-circuit impulses" to assume a width

depending on the regulating voltage feedback (the IC operates in the overload range). The IC

operates at the overload point. Thereafter the peak values of V2 decrease rapidly, as the starting

attempt is aborted (pin 5 is switched to low). As the IC remains switched on, V6 further decreases

to V6. The IC switches off; V6 can rise again (time point t4) and a new start-up attempt begins at

time point t1. If the rectified alternating Iine voltage (primary voltage) collapses during load, V3 can

fall below V3A , as is happening at time point t3 (switch-on attempt when voltage is too low). The

primary voltage monitor then clamps V3 to V3S until the IC switches off (V6 < V6A). Then a new start-

up attempt begins at time point t1.

Version 2.0 10 1 Jul 2002

TDA 4605-3

Regulation, Overload and No-Load Behaviour

When the IC has started up, it is operating in the regulation range. The potential at pin 1 typically is

400 mV. If the output is loaded, the regulation amplifier allows broader impulses ( V5= H). The peak

voltage value at pin 2 increases up to V2S max . If the secondary load is further increased, the

overload amplifier begins to regulate the pulse width downward. This point is referred to as the

overload point of the power supply. As the IC-supply voltage V6 is directly proportional to the

secondary voltage, it goes down in accordance with the overload regulation behaviour. If V6 falls

below the value V6 min , the IC goes into burst operation. As the time constant of the half-wave

charge-up is relatively large, the short-circuit power remains small. The overload amplifier cuts back

to the pulse width tpk . This pulse width must remain possible, in order to permit the IC to start-up

without problems from the virtual short-circuit, which every switching on with V1= 0 represents. If

the secondary side is unloaded, the loading impulses (V5= H) become shorter. The frequency

increases up to the resonance frequency of the system. If the load is further reduced, the secondary

voltages and V6 increase. When V6=V6 max the logic is blocked. The IC converts to burst

operation.This renders the circuit absolutely safe under no-load conditions.

Behaviour when Temperature Exceeds Limit

An integrated temperature protection disables the logic when the chip temperature becomes too

high. The IC automatically interrogates the temperature and starts as soon as the temperature

decreases to permissible values.

Version 2.0 11 1 Jul 2002

TDA 4605-3

*) tp= pulse width

v= duty circle

Absolute Maximum Ratings

TA = – 20 to 85 ˚C

Parameter Symbol Limit Values Unit Remarks

min. max.

Voltages pin 1

pin 2

pin 3

pin 5

pin 6

pin 7

V1

V2

V3

V5

V6

V7

– 0.3

3

V6

20

V

VSupply voltage

Currents pin 1

pin 2

pin 3

pin 4

pin 5

pin 6

pin 7

pin 8

I1

I2

I3

I4

I5

I6

I7

I8

– 1.5

– 0.5

– 5

3

1.5

0.5

3

mA

A

mA

tp≤ 50 µs; v ≤ 0.1*)

tp≤ 50 µs; v ≤ 0.1

Junction temperature Tj125 ˚C

Storage temperature Tstg – 40 125 ˚C

Operating Range

Supply voltage V67.5 15.5 V IC "on"

Ambient temperature TA– 20 85 ˚C

Heat resistance

Junction to environment Rth JE 100 K/W

Junction case Rth JC 70 K/W measured at pin 4

Version 2.0 12 1 Jul 2002

TDA 4605-3

Characteristics

TA = 25 ˚C; VS = 10 V

Parameter Symbol Limit Values Unit Test Condition Test

Circuit

min. typ. max.

Start-Up Hysteresis

Start-up current drain I6E0 0.6 0.8 mA V6 = V6E 1

Switch-on voltage V6E 11 12 13 V 1

Switch-off voltage V6A 4.5 5 5.5 V 1

Switch-on current I6E1 7 1114mAV

6

= V6E 1

Switch-off current I6A1 5 1013mAV

6

= V6A 1

Voltage Clamp (V6 = 10 V, IC switched off)

At pin 2 (V6≤V6E)

At pin 3 (V6≤V6E)V2 max

V3 max

5.6

5.6 6.6

7.7 8

8.3 V

VI2 = 1 mA

I3 = 1 mA 1

1

Control Range

Control input voltage V1R 390 400 410 mV 2

Voltage gain of the

control circuit in the

control range

–VR30 43 60 dB VR = d

(V2S – V2B) / – dV1

f = 1 kHz

2

Primary Current Simulation Voltage

Basic value V2B 0.97 1.00 1.03 V 2

Overload Range and Short-Circuit Operation

Peak value in the

range of secondary

overload

V2B 2.9 3.0 3.1 V V1 = V1R – 10 mV 2

Peak value in the

range of secondary

short-circuit operation

V2K 2.2 2.4 2.6 V V1 = 0 V 2

Fold-Back Point Correction

Fold-back point

correction current –I2300 500 650 µAV3 = 3.7 V 1

Version 2.0 13 1 Jul 2002

TDA 4605-3

Generally Valid Data (V6 = 10 V)

Voltage of the Zero Transition Detector

Positive clamping

voltage V8P 0.7 0.75 0.82 V I8 = 1 mA 2

Negative clamping

voltage V8N – 0.25 – 0.2 – 0.15 V I8 = – 1 mA 2

Threshold value V8S 40 50 76 mV 2

Suppression of

transformer ringing tUL 3.0 3.5 3.8 µs2

Input current – I804µAV

8

= 0 2

Push-Pull Output Stage

Saturation voltages

Pin 5 sourcing

Pin 5 sinking

VSat0

VSatV

1.5

1.0

1.4

2.0

1.2

1.8

V

I5 = – 0.1 A

I5 = + 0.1 A

I5 = + 0.5 A

1

Output Slew Rate

Rising edge + dV5/dt70 V/µs2

Falling edge + dV5/dt100 V/µs2

Reduction of Control Voltage

Current to reduce the

control voltage –I150 130 µAV7 = 1.1 V,V1 = 0.4 V

Characteristics (cont’d)

TA = 25 ˚C; VS = 10 V

Parameter Symbol Limit Values Unit Test Condition Test

Circuit

min. typ. max.

Version 2.0 14 1 Jul 2002

TDA 4605-3

Protection Circuit

Undervoltage

protection

for V6: voltage at

pin 5 = V5 min

if V6 < V5 min V6 min 7.0 7.25 7.5 V 2

Undervoltage

protection for V6:

voltage at

pin 5 = V5 min

if V6 > V6 max V6 max 15.5 16 16.5 V 2

Undervoltage

protection for VAC :

voltage at

pin 4 = V5 min

if V3 < V3A V3A 985 1000 1015 mV V2 = 0 V 1

Over temperature at

the given chip

temperature the IC

will switch V5 toV5 min Tj150 ˚C 2

Voltage at pin 3 if one

of the protection

function was

triggered;

(V3 will be clamped

until V6 < V6A)V3Sat 0.4 0.8 V I3 = 750 µA1

Current drain during

burst operation I68mAV

3

= V2 = 0 V 1

Characteristics (cont’d)

TA = 25 ˚C; VS = 10 V

Parameter Symbol Limit Values Unit Test Condition Test

Circuit

min. typ. max.

Version 2.0 15 1 Jul 2002

TDA 4605-3

Test Circuit 1

Test Circuit 2

Version 2.0 16 1 Jul 2002

TDA 4605-3

Application Circuit

Version 2.0 17 1 Jul 2002

TDA 4605-3

Diagrams

Version 2.0 18 1 Jul 2002

TDA 4605-3

Version 2.0 19 1 Jul 2002

TDA 4605-3

Start-Up Hysteresis

Version 2.0 20 1 Jul 2002

TDA 4605-3

Operation in Test Circuit 2

Version 2.0 21 1 Jul 2002

TDA 4605-3

Start-Up Current as a Function of the

Ambient Temperature Overload Point Correction as a Function of

the Voltage at Pin 3

Version 2.0 22 1 Jul 2002

TDA 4605-3

Recommended Heat Sink by 60 ˚C Ambient Temperature

Narrow Range 180 V ... 120 V ~

Narrow Range 90 V ... 270 V ~

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