LT4356-1/LT4356-2
1
Rev. C
For more information www.analog.com
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APPLICATIONS
FEATURES DESCRIPTION
Surge Stopper
The LT
®
4356 surge stopper protects loads from high voltage
transients. It regulates the output during an overvoltage
event, such as load dump in automobiles, by controlling
the gate of an external N-channel MOSFET. The output is
limited to a safe value thereby allowing the loads to con-
tinue functioning. The LT4356 also monitors the voltage
drop between the VCC and SNS pins to protect against
overcurrent faults. An internal amplifier limits the current
sense voltage to 50mV. In either fault condition, a timer
is started inversely proportional to MOSFET stress. If the
timer expires, the F LT pin pulls low to warn of an impend-
ing power down. If the condition persists, the MOSFET is
turned off. After a cool down period, the GATE pin pulls
up turning on the MOSFET again.
The auxiliary amplifier may be used as a voltage detection
comparator or as a linear regulator controller driving an
external PNP pass transistor.
Back-to-back FETs can be used in lieu of a Schottky diode
for reverse input protection, reducing voltage drop and
power loss. A shutdown pin reduces the quiescent current
to less than 7µA for the LT4356-1 during shutdown. The
LT4356-2 differs from the LT4356-1 during shutdown by
reducing the quiescent current to 60µA and keeping alive
the auxiliary amplifier for uses such as an undervoltage
lockout or always-on regulator.
n Automotive/Avionic Surge Protection
n Hot Swap/Live Insertion
n High Side Switch for Battery Powered Systems
n Intrinsic Safety Applications
n Stops High Voltage Surges
n Adjustable Output Clamp Voltage
n Overcurrent Protection
n Wide Operation Range: 4V to 80V
n Reverse Input Protection to –60V
n Low 7µA Shutdown Current (LT4356-1)
n Auxiliary Amplifier for Level Detection Comparator
or Linear Regulator Controller (LT4356-2)
n Adjustable Fault Timer
n Controls N-channel MOSFET
n Shutdown Pin Withstands –60V to 100V
n Fault Output Indication
n Guaranteed Operation to 125°C
n Available in (4mm × 3mm) 12-Pin DFN,
10-Pin MSOP or 16-Pin SO Packages
4A, 12V Overvoltage Output Regulator Overvoltage Protector Regulates Output at
27V During Transient
0.1µF
10Ω
10mΩ
IRLR2908
VIN
12V
4356 TA01
LT4356DE
GND TMR
OUTGATESNS
IN+
SHDN
AOUT FAULT
VOUT
EN
FLTUNDERVOLTAGE
FB
VCC
DC-DC
CONVERTER
GND
SHDN
VCC
4.99k
383k
100k
102k
100ms/DIV 4356 TA01b
VIN
20V/DIV
VOUT
20V/DIV
80V INPUT SURGE CTMR = 6.8µF
ILOAD = 500mA
27V ADJUSTABLE CLAMP
12V
12V
TYPICAL APPLICATION
All registered trademarks and trademarks are the property of their respective owners. Protected
by U.S. patents, including XXXXX, XXXXX.
LT4356-1/LT4356-2
2
Rev. C
For more information www.analog.com
VCC, SHDN ................................................ –60V to 100V
SNS ............................. VCC – 30V or –60V to VCC + 0.3V
OUT, AOUT, F LT , EN ..................................... –0.3V to 80V
GATE (Note 3) .................................–0.3V to VOUT + 10V
FB, TMR, IN+ ................................................ –0.3V to 6V
AOUT, EN, F LT , IN+ ..................................................–3mA
Operating Temperature Range
LT4356C ................................................... 0°C to 70°C
LT4356I ................................................ –40°C to 85°C
LT4356H ............................................ –40°C to 125°C
12
11
10
9
8
7
13
1
2
3
4
5
6
IN+
AOUT
GND
EN
FLT
SHDN
TMR
FB
OUT
GATE
SNS
VCC
TOP VIEW
DE PACKAGE
12-LEAD (4mm × 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 43°C/W
EXPOSED PAD (PIN 13) PCB GND CONNECTION OPTIONAL
1
2
3
4
5
FB
OUT
GATE
SNS
VCC
10
9
8
7
6
TMR
GND
EN
FLT
SHDN
TOP VIEW
MS PACKAGE
10-LEAD PLASTIC MSOP
TJMAX = 125°C, θJA = 120°C/W
TOP VIEW
S PACKAGE
16-LEAD PLASTIC SO
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
TMR
FB
NC
OUT
GATE
NC
SNS
VCC
IN+
NC
AOUT
NC
GND
EN
FLT
SHDN
TJMAX = 150°C, θJA = 100°C/W
Storage Temperature Range
DE12 .................................................. –65°C to 125°C
MS, SO .............................................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec)
MS, SO ............................................................. 300°C
ABSOLUTE MAXIMUM RATINGS
PIN CONFIGURATION
(Notes 1 and 2)
LT4356-1/LT4356-2
3
Rev. C
For more information www.analog.com
TUBE TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE
LT4356CDE-1#PBF LT4356CDE-1#TRPBF 43561 12-Lead (4mm × 3mm) Plastic DFN 0°C to 70°C
LT4356IDE-1#PBF LT4356IDE-1#TRPBF 43561 12-Lead (4mm × 3mm) Plastic DFN –40°C to 85°C
LT4356HDE-1#PBF LT4356HDE-1#TRPBF 43561 12-Lead (4mm × 3mm) Plastic DFN –40°C to 125°C
LT4356CDE-2#PBF LT4356CDE-2#TRPBF 43562 12-Lead (4mm × 3mm) Plastic DFN 0°C to 70°C
LT4356IDE-2#PBF LT4356IDE-2#TRPBF 43562 12-Lead (4mm × 3mm) Plastic DFN –40°C to 85°C
LT4356HDE-2#PBF LT4356HDE-2#TRPBF 43562 12-Lead (4mm × 3mm) Plastic DFN –40°C to 125°C
LT4356CMS-1#PBF LT4356CMS-1#TRPBF LTCNS 10-Lead Plastic MSOP 0°C to 70°C
LT4356IMS-1#PBF LT4356IMS-1#TRPBF LTCNS 10-Lead Plastic MSOP –40°C to 85°C
LT4356HMS-1#PBF LT4356HMS-1#TRPBF LTCNS 10-Lead Plastic MSOP –40°C to 125°C
LT4356CS-1#PBF LT4356CS-1#TRPBF LT4356S-1 16-Lead Plastic SO 0°C to 70°C
LT4356IS-1#PBF LT4356IS-1#TRPBF LT4356S-1 16-Lead Plastic SO –40°C to 85°C
LT4356HS-1#PBF LT4356HS-1#TRPBF LT4356S-1 16-Lead Plastic SO –40°C to 125°C
LT4356CS-2#PBF LT4356CS-2#TRPBF LT4356S-2 16-Lead Plastic SO 0°C to 70°C
LT4356IS-2#PBF LT4356IS-2#TRPBF LT4356S-2 16-Lead Plastic SO –40°C to 85°C
LT4356HS-2#PBF LT4356HS-2#TRPBF LT4356S-2 16-Lead Plastic SO –40°C to 125°C
LT4356CDE-1 LT4356CDE-1#TR 43561 12-Lead (4mm × 3mm) Plastic DFN 0°C to 70°C
LT4356IDE-1 LT4356IDE-1#TR 43561 12-Lead (4mm × 3mm) Plastic DFN –40°C to 85°C
LT4356HDE-1 LT4356HDE-1#TR 43561 12-Lead (4mm × 3mm) Plastic DFN –40°C to 125°C
LT4356CDE-2 LT4356CDE-2#TR 43562 12-Lead (4mm × 3mm) Plastic DFN 0°C to 70°C
LT4356IDE-2 LT4356IDE-2#TR 43562 12-Lead (4mm × 3mm) Plastic DFN –40°C to 85°C
LT4356HDE-2 LT4356HDE-2#TR 43562 12-Lead (4mm × 3mm) Plastic DFN –40°C to 125°C
LT4356CMS-1 LT4356CMS-1#TR LTCNS 10-Lead Plastic MSOP 0°C to 70°C
LT4356IMS-1 LT4356IMS-1#TR LTCNS 10-Lead Plastic MSOP –40°C to 85°C
LT4356HMS-1 LT4356HMS-1#TR LTCNS 10-Lead Plastic MSOP –40°C to 125°C
LT4356CS-1 LT4356CS-1#TR LT4356S-1 16-Lead Plastic SO 0°C to 70°C
LT4356IS-1 LT4356CS-1#TR LT4356S-1 16-Lead Plastic SO –40°C to 85°C
LT4356HS-1 LT4356HS-1#TR LT4356S-1 16-Lead Plastic SO –40°C to 125°C
LT4356CS-2 LT4356CS-2#TR LT4356S-2 16-Lead Plastic SO 0°C to 70°C
LT4356IS-2 LT4356IS-2#TR LT4356S-2 16-Lead Plastic SO –40°C to 85°C
LT4356HS-2 LT4356HS-2#TR LT4356S-2 16-Lead Plastic SO –40°C to 125°C
Contact the factory for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
Tape and reel specifications. Some packages are available in 500 unit reels through designated sales channels with #TRMPBF suffix.
ORDER INFORMATION
LT4356-1/LT4356-2
4
Rev. C
For more information www.analog.com
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VCC = 12V unless otherwise noted.
ELECTRICAL CHARACTERISTICS
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VCC Operating Voltage Range l4 80 V
ICC VCC Supply Current VSHDN = Float l1 1.5 mA
VSHDN = 0V, IN+ = 1.3V, LT4356-1
LT4356I-1, LT4356C-1
LT4356H-1
l
l
7
7
7
25
30
40
µA
µA
µA
VSHDN = 0V, IN+ = 1.3V, LT4356-2
LT4356I-2, LT4356C-2
LT4356H-2
l
l
60
60
60
70
100
250
µA
µA
µA
IRReverse Input Current VSNS = VCC = –30V, SHDN Open
VSNS = VCC = VSHDN = –30V
l
l
0.3
0.8
1
2
mA
mA
ΔVGATE GATE Pin Output High Voltage VCC = 4V; (VGATE – VOUT)
80V ≥ VCC ≥ 8V; (VGATE – VOUT)
l
l
4.5
10
8
16
V
V
IGATE(UP) GATE Pin Pull-Up Current VGATE = 12V; VCC = 12V
VGATE = 48V; VCC = 48V
l
l
–4
–4.5
–23
–30
–36
–50
µA
µA
IGATE(DN) GATE Pin Pull-Down Current Overvoltage, VFB = 1.4V, VGATE = 12V
Overcurrent, VCC – VSNS = 120mV, VGATE = 12V
Shutdown Mode, VSHDN = 0V, VGATE = 12V
l
l
l
75
5
1.5
150
10
5
mA
mA
mA
VFB FB Pin Servo Voltage VGATE = 12V; VOUT = 12V, LT4356I, LT4356C
VGATE = 12V; VOUT = 12V, LT4356H
l
l
1.225
1.215
1.25
1.25
1.275
1.275
V
V
IFB FB Pin Input Current VFB = 1.25V l0.3 1 µA
ΔVSNS Overcurrent Fault Threshold ΔVSNS = (VCC – VSNS), VCC = 12V, LT4356I, LT4356C
ΔVSNS = (VCC – VSNS), VCC = 12V, LT4356H
ΔVSNS = (VCC – VSNS), VCC = 48V, LT4356I, LT4356C
ΔVSNS = (VCC – VSNS), VCC = 48V, LT4356H
l
l
l
l
45
42.5
46
43
50
50
51
51
55
55
56
56
mV
mV
mV
mV
ISNS SNS Pin Input Current VSNS = VCC = 12V to 48V l5 10 22 µA
ILEAK F LT , EN Pins Leakage Current
AOUT Pin Leakage Current
F LT , EN = 80V
AOUT = 80V
l2.5
4.5
µA
µA
ITMR TMR Pin Pull-up Current VTMR = 1V, VFB = 1.5V, (VCC – VOUT) = 0.5V
VTMR = 1V, VFB = 1.5V, (VCC – VOUT) = 75V
VTMR = 1.3V, VFB = 1.5V
VTMR = 1V, ΔVSNS = 60mV, (VCC – VOUT) = 0.5V
VTMR = 1V, ΔVSNS = 60mV, (VCC – VOUT) = 80V
l
l
l
l
l
–1.5
–44
–3.5
–2.5
–195
–2.5
–50
–5.5
–4.5
–260
–4
–56
–8.5
–6.5
–315
µA
µA
µA
µA
µA
TMR Pin Pull-down Current VTMR = 1V, VFB = 1V, ΔVSNS = 0V l1.5 2.2 2.7 µA
VTMR TMR Pin Thresholds FLT From High to Low, VCC = 5V to 80V
VGATE From Low to High, VCC = 5V to 80V
l
l
1.22
0.48
1.25
0.5
1.28
0.52
V
V
ΔVTMR Early Warning Period From F LT going Low to GATE going Low, VCC = 5V to 80V l80 100 120 mV
VIN+IN+ Pin Threshold l1.22 1.25 1.28 V
IIN+IN+ Pin Input Current VIN+ = 1.25V l0.3 1 µA
VOL F LT , EN Pins Output Low ISINK = 2mA
ISINK = 0.1mA
l
l
2
300
8
800
V
mV
AOUT Pin Output Low ISINK = 2mA
ISINK = 0.1mA
l
l
2
200
8
400
V
mV
IOUT OUT Pin Input Current VOUT = VCC = 12V
VOUT = VCC = 12V, VSHDN = 0V
l
l
200
6
300
14
µA
mA
ΔVOUT OUT Pin High Threshold ΔVOUT = VCC – VOUT; EN From Low to High l0.25 0.5 0.7 V
VSHDN SHDN Pin Threshold VCC = 12V to 48V
l
0.6
0.4
1.7
2.1
V
V
LT4356-1/LT4356-2
5
Rev. C
For more information www.analog.com
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VCC = 12V unless otherwise noted.
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: All currents into device pins are positive; all currents out of device
pins are negative. All voltages are referenced to GND unless otherwise
specified.
Note 3: An internal clamp limits the GATE pin to a minimum of 10V above
the OUT pin. Driving this pin to voltages beyond the clamp may damage
the device.
Note 4: Resting voltage after turn-on.
ELECTRICAL CHARACTERISTICS
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VSHDN(FLT) SHDN Pin Resting Voltage VCC = 12V to 48V, Note 4 l0.6 2.1 V
ISHDN SHDN Pin Current VSHDN = 0V l–1 –4 –8 µA
tOFF(OC) Overcurrent Turn Off Delay Time GATE From High to Low, ΔVSNS = 0 → 120mV l2 4 µs
tOFF(OV) Overvoltage Turn Off Delay Time GATE From High to Low, VFB = 0 → 1.5V l0.25 1 µs
TYPICAL PERFORMANCE CHARACTERISTICS
ICC (Shutdown) vs VCC
ICC vs VCC
VCC (V)
0
0
I
CC
(µA)
10
20
30
40
20 40 60 80
4356 G01
50
60
10 30 50 70
LT4356-1
VCC (V)
0
0
I
CC
(µA)
200
400
600
20 40 60 80
4356 G02
800
1000
10 30 50 70
Specifications are at VCC = 12V, TA = 25°C unless otherwise noted.
ICC (Shutdown) vs VCC
VCC (V)
0
0
I
CC
(µA)
20
40
20 40 60
80
4356 G20
120
LT4356-2
IN+ = 1.3V
60
80
100
10 30 50 70
TEMPERATURE (°C)
–50
0
I
CC
(µA)
50
100
150
200
0 50 100
125
4356 G21
250
300
–25 25 75
LT4356-2
ICC (Shutdown) vs Temperature
ICC (Shutdown) vs Temperature
TEMPERATURE (°C)
–50
0
I
CC
(µA)
5
10
15
20
0 50 100 125
4356 G03
25
35
30
–25 25 75
LT4356-1
LT4356-1/LT4356-2
6
Rev. C
For more information www.analog.com
SHDN Current vs Temperature
GATE Pull-Up Current vs VCC
GATE Pull-Up Current vs
Temperature
GATE Pull-Down Current vs
Temperature
GATE Pull-Down Current vs
Temperature
ΔVGATE vs IGATE
TEMPERATURE (°C)
–50
0
ISHDN (µA)
1
2
3
0 50 100 125
4356 G04
4
6
5
–25 25 75
VSHDN = 0V
VCC (V)
0
0
IGATE (µA)
10
20
30
5
15
25
35
20 40 60 80
4356 G05
40
10 30 50 70
TEMPERATURE (°C)
–50
0
IGATE (µA)
5
10
15
20
0 50 100 125
4356 G06
25
35
30
–25 25 75
VGATE = VOUT = 12V
TEMPERATURE (°C)
–50
100
IGATE(DOWN) (mA)
120
140
160
0 50 100 125
4356 G07
180
220
200
–25 25 75
OVERVOLTAGE CONDITION
VFB = 1.5V
TEMPERATURE (°C)
–50
0
IGATE(DOWN) (mA)
2
4
6
0 50 100 125
4356 G08
8
12
10
–25 25 75
OVERCURRENT CONDITION
∆VSNS = 120mV
IGATE (µA)
0
0
∆V
GATE
(V)
4
2
6
8
10
4 8 12 16
4356 G09
12
14
2 6 10 14
VOUT = 12V
TYPICAL PERFORMANCE CHARACTERISTICS
Specifications are at VCC = 12V, TA = 25°C unless otherwise noted.
ΔVGATE vs Temperature
ΔVGATE vs VCC
Overvoltage TMR Current vs
(VCC – VOUT)
TEMPERATURE (°C)
–50 0 50 100 125
–25 25 75
0
∆V
GATE
(V)
4
2
6
8
10
4356 G10
12
14 IGATE = –1µA
VCC = 8V
VCC = 4V
VCC (V)
0 20 40 60 80
4356 G11
10 30 50 70
0
∆V
GATE
(V)
4
2
6
8
10
12
16
14
IGATE = –1µA
VOUT = VCC
TA = –45°C
TA = 25°C
TA = 130°C
VCC – VOUT (V)
0
0
ITMR (µA)
8
16
24
32
20 40 60 80
4356 G12
40
48
10 30 50 70
OVERVOLTAGE CONDITION
VOUT = 5V
VTMR = 1V
LT4356-1/LT4356-2
7
Rev. C
For more information www.analog.com
Overcurrent TMR Current vs
(VCC – VOUT)
Warning Period
TMR Current vs VCC
TMR Pull-Down Current vs
Temperature
Output Low Voltage vs Current
Overvoltage Turn-Off Time vs
Temperature
Overcurrent Turn-Off Time vs
Temperature
VCC – VOUT (V)
0
0
ITMR (µA)
40
80
120
160
20 40 60 80
4356 G13
200
280
240
10 30 50 70
OVERCURRENT CONDITION
VOUT = 0V
VTMR = 1V
VCC (V)
0 20 40 60 80
4356 G14
10 30 50 70
0
ITMR (µA)
4
2
6
8
10
12
14 OVERVOLTAGE, EARLY
WARNING PERIOD
VFB = 1.5V
VTMR = 1.3V
TEMPERATURE (°C)
–50
0
ITMR (µA)
0 50 100 125
4356 G15
3.0
2.5
2.0
1.5
1.0
0.5
–25 25 75
VTMR = 1V
CURRENT (mA)
0
0
V
OL
(V)
1.0
2.0
3.0
0.5
1.5
2.5
3.5
2.0 3.0
4356 G16
4.0
1.00.5 2.51.5
AOUT
EN
FLT
TEMPERATURE (°C)
–50
0
100
tOFF (ns)
0 50 100 125
4356 G17
500
400
300
200
–25 25 75
OVERVOLTAGE CONDITION
VFB = 1.5V
TEMPERATURE (°C)
–50
1.0
1.5
tOFF (µs)
0 50 100 125
4356 G18
4.0
3.5
3.0
2.5
2.0
–25 25 75
OVERCURRENT CONDITION
∆VSNS = 120mV
TYPICAL PERFORMANCE CHARACTERISTICS
Specifications are at VCC = 12V, TA = 25°C unless otherwise noted.
VCC (V)
0
I
CC
(mA)
–10
–15
–80
4356 G19
–5
0–20 –40 –60
–20 VCC = SNS
Reverse Current vs Reverse
Voltage
LT4356-1/LT4356-2
8
Rev. C
For more information www.analog.com
PIN FUNCTIONS
AOUT (DFN and SO Packages Only): Amplifier Output.
Open collector output of the auxiliary amplifier. It is capable
of sinking up to 2mA from 80V. The negative input of the
amplifier is internally connected to a 1.25V reference.
EN: Open-Collector Enable Output. The EN pin goes high
impedance when the voltage at the OUT pin is above (VCC
– 0.7V), indicating the external MOSFET is fully on. The
state of the pin is latched until the OUT pin voltage resets
at below 0.5V and goes back up above 2V. The internal
NPN is capable of sinking up to 3mA of current from 80V
to drive an LED or opto-coupler.
Exposed Pad (DFN Package Only): Exposed pad may be
left open or connected to device ground (GND).
FB: Voltage Regulator Feedback Input. Connect this pin
to the center tap of the output resistive divider connected
between the OUT pin and ground. During an overvoltage
condition, the GATE pin is servoed to maintain a 1.25V
threshold at the FB pin. This pin is clamped internally to
7V. Tie to GND to disable the OV clamp.
F LT : Open-Collector Fault Output. This pin pulls low after the
voltage at the TMR pin has reached the fault threshold of 1.25V.
It indicates the pass transistor is about to turn off because
either the supply voltage has stayed at an elevated level for an
extended period of time (voltage fault) or the device is in an
overcurrent condition (current fault). The internal NPN is capa-
ble of sinking up to 3mA of current from 80V to drive an LED or
opto-coupler.
GATE: N-Channel MOSFET Gate Drive Output. The GATE
pin is pulled up by an internal charge pump current source
and clamped to 14V above the OUT pin. Both voltage and
current amplifiers control the GATE pin to regulate the
output voltage and limit the current through the MOSFET.
GND: Device Ground.
IN+ (DFN and SO Packages Only): Positive Input of the
Auxiliary Amplifier. This amplifier can be used as a level
detection comparator with external hysteresis or linear
regulator controlling an external PNP transistor. This pin
is clamped internally to 7V. Connect to ground if unused.
OUT: Output Voltage Sense Input. This pin senses the
voltage at the source of the N-channel MOSFET and sets
the fault timer current. When the OUT pin voltage reaches
0.7V away from VCC, the EN pin goes high impedance.
SHDN: Shutdown Control Input. Pulling the SHDN pin low
shuts the part down to a low current mode. All functions
are turned off for the LT4356-1 while the internal reference
and the auxiliary amplifier stay active for the LT4356-2.
The SHDN input threshold is similar to a TTL input. If the
SHDN voltage goes below 2.1V, the voltage must go below
0.4V for 100μs to properly shut down the part. To turn
the part back on, the SHDN voltage must transition from
below 0.4V to greater than 2.1V with a slew rate faster
than 10V/ms. An internal, 4μA current source is provided
to pull the SHDN pin up. An external pull-up device should
be used if the leakage current to ground might exceed 1μA.
The SHDN pin can be pulled up to 100V or below GND by
60V without damage.
SNS: Current Sense Input. Connect this pin to the output of
the current sense resistor. The current limit circuit controls
the GATE pin to limit the sense voltage between VCC and
SNS pins to 50mV. At the same time the sense amplifier
also starts a current source to charge up the TMR pin.
This pin can be pulled below GND by up to 60V, though
the voltage difference with the VCC pin must be limited to
less than 30V. Connect to VCC if unused.
TMR: Fault Timer Input. Connect a capacitor between this
pin and ground to set the times for early warning, fault
and cool down periods. The current charging up this pin
during fault conditions depends on the voltage difference
between the VCC and OUT pins. When VTMR reaches 1.25V,
the F LT pin pulls low to indicate the detection of a fault
condition. If the condition persists, the pass transistor turns
off when VTMR reaches the threshold of 1.35V. As soon as
the fault condition disappears, the pull up current stops
and a 2µA current starts to pull the TMR pin down. When
VTMR reaches the retry threshold of 0.5V, the GATE pin pulls
high turning back on the pass transistor. A minimum of
10nF capacitor is needed to compensate the loop. A 10V
rated X7R capacitor is recommended for CTMR.
VCC: Positive Supply Voltage Input. The positive supply
input ranges from 4V to 80V for normal operation. It
can also be pulled below ground potential by up to 60V
during a reverse battery condition, without damaging the
part. The supply current is reduced to 7µA with all the
functional blocks off.
LT4356-1/LT4356-2
10
Rev. C
For more information www.analog.com
Some power systems must cope with high voltage surges
of short duration such as those in automobiles. Load
circuitry must be protected from these transients, yet
high availability systems must continue operating during
these events.
The LT4356 is an overvoltage protection regulator that
drives an external N-channel MOSFET as the pass transistor.
It operates from a wide supply voltage range of 4V to 80V.
It can also be pulled below ground potential by up to 60V
without damage. The low power supply requirement of 4V
allows it to operate even during cold cranking conditions
in automotive applications. The internal charge pump
turns on the N-channel MOSFET to supply current to the
loads with very little power loss. Two MOSFETs can be
connected back to back to replace an inline Schottky diode
for reverse input protection. This improves the efficiency
and increases the available supply voltage level to the load
circuitry during cold crank.
Normally, the pass transistor is fully on, powering the loads
with very little voltage drop. When the supply voltage surges
too high, the voltage amplifier (VA) controls the gate of
the MOSFET and regulates the voltage at the source pin
to a level that is set by the external resistive divider from
the OUT pin to ground and the internal 1.25V reference. A
current source starts charging up the capacitor connected
at the TMR pin to ground. If the voltage at the TMR pin,
VTMR, reaches 1.25V, the F LT pin pulls low to indicate
impending turn-off due to the overvoltage condition. The
pass transistor stays on until the TMR pin reaches 1.35V, at
which point the GATE pin pulls low turning off the MOSFET.
The potential at the TMR pin starts decreasing as soon
as the output voltage is not being servoed, indicating the
overvoltage condition has disappeared. When the voltage
at the TMR pin reaches 0.5V the GATE pin begins rising,
turning on the MOSFET. The FLT pin will then go to a high
impedance state.
The fault timer allows the load to continue functioning
during short transient events while protecting the MOSFET
from being damaged by a long period of supply overvolt-
age, such as a load dump in automobiles. The timer period
varies with the voltage across the MOSFET
. A higher voltage
corresponds to a shorter fault timer period, ensuring the
MOSFET operates within its safe operating area (SOA).
The LT4356 senses an overcurrent condition by monitor-
ing the voltage across an optional sense resistor placed
between the VCC and SNS pins. An active current limit
circuit (IA) controls the GATE pin to limit the sense voltage
to 50mV. A current is also generated to start charging up
the TMR pin. This current is about 5 times the current
generated during an overvoltage event. The FLT pin pulls
low when the voltage at the TMR pin reaches 1.25V and
the MOSFET is turned off when it reaches 1.35V.
An auxiliary amplifier is provided with the negative input
connected to an internal 1.25V reference. The output pull
down device is capable of sinking up to 2mA of current
allowing it to drive an LED or opto coupler. This amplifier
can be configured as a linear regulator controller driving
an external PNP transistor or a comparator function to
monitor voltages.
A shutdown pin turns off the pass transistor and reduces
the supply current to less than 7µA for the LT4356-1. The
supply current drops down to 60µA while keeping the
internal reference and the auxiliary amplifier active for the
LT4356-2 version during shutdown.
OPERATION
LT4356-1/LT4356-2
11
Rev. C
For more information www.analog.com
The LT4356 can limit the voltage and current to the load
circuitry during supply transients or overcurrent events.
The total fault timer period should be set to ride through
short overvoltage transients while not causing damage
to the pass transistor. The selection of this N-channel
MOSFET pass transistor is critical for this application.
It must stay on and provide a low impedance path from
the input supply to the load during normal operation and
then dissipate power during overvoltage or overcurrent
conditions.
The following sections describe the overcurrent and the
overvoltage faults, and the selection of the timer capacitor
value based on the required warning time. The selection
of the N-channel MOSFET pass transistor is discussed
next. Auxiliary amplifier, reverse input, and the shutdown
functions are covered after the MOSFET selection. External
component selection is discussed in detail in the Design
Example section.
Overvoltage Fault
The LTC4356 limits the voltage at the OUT pin during an
overvoltage situation. An internal voltage amplifier regu-
lates the GATE pin voltage to maintain a 1.25V threshold at
the FB pin. During this period of time, the power MOSFET
is still on and continues to supply current to the load. This
allows uninterrupted operation during short overvoltage
transient events.
When the voltage regulation loop is engaged for longer
than the time-out period, set by the timer capacitor con-
nected from the TMR pin to ground, an overvoltage fault is
detected. The GATE pin is pulled down to the OUT pin by a
150mA current. After the fault condition has disappeared
and a cool down period has transpired, the GATE pin starts
to pull high again. This prevents the power MOSFET from
being damaged during a long period of overvoltage, such
as during load dump in automobiles.
Overcurrent Fault
The LT4356 features an adjustable current limit that
protects against short circuits or excessive load current.
During an overcurrent event, the GATE pin is regulated to
limit the current sense voltage across the VCC and SNS
pins to 50mV.
An overcurrent fault occurs when the current limit circuitry
has been engaged for longer than the time-out delay set
by the timer capacitor. The GATE pin is then immediately
pulled low by a 10mA current to GND turning off the
MOSFET. After the fault condition has disappeared and a
cool down period has transpired, the GATE pin is allowed
to pull back up and turn on the pass transistor.
Fault Timer
The LT4356 includes an adjustable fault timer pin. Con-
necting a capacitor from the TMR pin to ground sets the
delay timer period before the MOSFET is turned off. The
same capacitor also sets the cool down period before the
MOSFET is allowed to turn back on after the fault condition
has disappeared.
Once a fault condition, either overvoltage or overcurrent,
is detected, a current source charges up the TMR pin. The
current level varies depending on the voltage drop across
the drain and source terminals of the power MOSFET(-
VDS), which is typically from the VCC pin to the OUT pin.
This scheme takes better advantage of the available Safe
Operating Area (SOA) of the MOSFET than would a fixed
timer current. The timer function operates down to VCC =
5V across the whole temperature range.
APPLICATIONS INFORMATION
LT4356-1/LT4356-2
12
Rev. C
For more information www.analog.com
Fault Timer Current
The timer current starts at around 2µA with 0.5V or less of
VDS, increasing linearly to 50µA with 75V of VDS during an
overvoltage fault (Figure1). During an overcurrent fault,
it starts at 4µA with 0.5V or less of VDS but increases
to 260µA with 80V across the MOSFET (Figure2). This
arrangement allows the pass transistor to turn off faster
during an overcurrent event, since more power is dissipated
during this condition. Refer to the Typical Performance
Characteristics section for the timer current at different
VDS in both overvoltage and overcurrent events.
When the voltage at the TMR pin, VTMR, reaches the 1.25V
threshold, the F LT pin pulls low to indicate the detection
of a fault condition and provide warning to the load of the
impending power loss. In the case of an overvoltage fault,
the timer current then switches to a fixed 5µA. The interval
between FLT asserting low and the MOSFET turning off
is given by:
tWARNING = CTMR • 100mV
5µA
APPLICATIONS INFORMATION
Figure1. Overvoltage Fault Timer Current
Figure2. Overcurrent Fault Timer Current
tFLT
= 15ms/µF
TOTAL FAULT TIMER = tFLT + tWARNING
tWARNING
= 20ms/µF
tFLT = 93.75ms/µF tWARNING
= 20ms/µF
VTMR(V)
ITMR = 5µA ITMR = 5µA
VDS = 75V
(ITMR = 50µA)
VDS = 10V
(ITMR = 8µA)
1.35
1.25
TIME
4356 F01
0.50
tFLT
= 2.88ms/µF
TOTAL FAULT TIMER = tFLT + tWARNING
tFLT = 21.43ms/µF tWARNING
= 2.86ms/µF
tWARNING
= 0.38ms/µF
VTMR(V)
VDS = 10V
(ITMR = 35µA)
1.35
1.25
0.50 TIME
4356 F02
VDS = 80V
(ITMR = 260µA)
LT4356-1/LT4356-2
13
Rev. C
For more information www.analog.com
voltage N-channel MOSFETs. For systems with VCC less
than 8V, a logic level MOSFET is required since the gate
drive can be as low as 4.5V.
The SOA of the MOSFET must encompass all fault con-
ditions. In normal operation the pass transistor is fully
on, dissipating very little power. But during either over-
voltage or overcurrent faults, the GATE pin is servoed to
regulate either the output voltage or the current through
the MOSFET
. Large current and high voltage drop across
the MOSFET can coexist in these cases. The SOA curves
of the MOSFET must be considered carefully along with
the selection of the fault timer capacitor.
Transient Stress in the MOSFET
During an overvoltage event, the LT4356 drives a series
pass MOSFET to regulate the output voltage at an acceptable
level. The load circuitry may continue operating throughout
this interval, but only at the expense of dissipation in the
MOSFET pass device. MOSFET dissipation or stress is a
function of the input voltage waveform, regulation voltage
and load current. The MOSFET must be sized to survive
this stress.
Most transient event specifications use the model shown
in Figure3. The idealized waveform comprises a linear
ramp of rise time tr, reaching a peak voltage of VPK and
exponentially decaying back to VIN with a time constant
of t. A common automotive transient specification has
constants of tr = 10µs, VPK = 80V and t = 1ms. A surge
condition known as “load dump” has constants of tr =
5ms, VPK = 60V and t = 200ms.
This fixed early warning period allows the systems to per-
form necessary backup or house-keeping functions before
the power supply is cut off. After VTMR crosses the 1.35V
threshold, the pass transistor turns off immediately. Note
that during an overcurrent event, the timer current is not
reduced to 5µA after VTMR has reached 1.25V threshold,
since it would lengthen the overall fault timer period and
cause more stress on the power MOSFET.
As soon as the fault condition has disappeared, a 2µA
current starts to discharge the timer capacitor to ground.
When VTMR reaches the 0.5V threshold, the internal charge
pump starts to pull the GATE pin high, turning on the
MOSFET. The TMR pin is then actively regulated to 0.5V
until the next fault condition appears. The total cool down
timer period is given by:
tCOOL = CTMR • 0.85V
2µA
MOSFET Selection
The LT4356 drives an N-channel MOSFET to conduct the
load current. The important features of the MOSFET are
on-resistance RDS(ON), the maximum drain-source voltage
V(BR)DSS, the threshold voltage, and the SOA.
The maximum allowable drain-source voltage must be
higher than the supply voltage. If the output is shorted
to ground or during an overvoltage event, the full supply
voltage will appear across the MOSFET.
The gate drive for the MOSFET is guaranteed to be more
than 10V and less than 16V for those applications with VCC
higher than 8V. This allows the use of standard threshold
APPLICATIONS INFORMATION
Figure3. Prototypical Transient Waveform
VPK
τ
VIN
4356 F03
tr
LT4356-1/LT4356-2
14
Rev. C
For more information www.analog.com
APPLICATIONS INFORMATION
MOSFET stress is the result of power dissipated within
the device. For long duration surges of 100ms or more,
stress is increasingly dominated by heat transfer; this is
a matter of device packaging and mounting, and heatsink
thermal mass. This is analyzed by simulation, using the
MOSFET thermal model.
For short duration transients of less than 100ms, MOSFET
survival is increasingly a matter of safe operating area
(SOA), an intrinsic property of the MOSFET. SOA quantifies
the time required at any given condition of VDS and ID to
raise the junction temperature of the MOSFET to its rated
maximum. MOSFET SOA is expressed in units of watt-
squared-seconds (P2t). This figure is essentially constant
for intervals of less than 100ms for any given device
type, and rises to infinity under DC operating conditions.
Destruction mechanisms other than bulk die temperature
distort the lines of an accurately drawn SOA graph so that
P2t is not the same for all combinations of ID and VDS.
In particular P2t tends to degrade as VDS approaches the
maximum rating, rendering some devices useless for
absorbing energy above a certain voltage.
Calculating Transient Stress
To select a MOSFET suitable for any given application, the
SOA stress must be calculated for each input transient
which shall not interrupt operation. It is then a simple matter
to chose a device which has adequate SOA to survive the
maximum calculated stress. P2t for a prototypical transient
waveform is calculated as follows (Figure4).
Let
a = VREG – VIN
b = VPK – VIN
(VIN = Nominal Input Voltage)
Then
P
2t = ILOAD21
3tr b−a
(
)
3
b+1
2t2a2ln b
a+3a2+b2−4ab
⎛
⎝
⎜⎞
⎠
⎟
⎡
⎣
⎢
⎢
⎤
⎦
⎥
⎥
Typically VREG ≈ VIN and t >> t r simplifying the above to
P2t = 1
2
ILOAD2VPK – VREG
( )
2t(W 2s
)
For the transient conditions of VPK = 80V, VIN = 12V, VREG
= 16V, tr = 10µs and t = 1ms, and a load current of 3A,
P2t is 18.4W2s—easily handled by a MOSFET in a D-pak
package. The P2t of other transient waveshapes is evaluated
by integrating the square of MOSFET power versus time.
Calculating Short-Circuit Stress
SOA stress must also be calculated for short-circuit con-
ditions. Short-circuit P2t is given by:
P2t = (VIN • ΔVSNS/RSNS)2 • tTMR (W2s)
where, ΔVSNS is the SENSE pin threshold, and tTMR is the
overcurrent timer interval.
For VIN = 14.7V, VSNS = 50mV, RSNS = 12mΩ and CTMR
= 100nF, P2t is 6.6W2s—less than the transient SOA
calculated in the previous example. Nevertheless, to
account for circuit tolerances this figure should be doubled
to 13.2W2s.
Limiting Inrush Current and GATE Pin Compensation
The LT4356 limits the inrush current to any load capacitance
by controlling the GATE pin voltage slew rate. An external
capacitor can be connected from GATE to ground to slow
down the inrush current further at the expense of slower
turn-off time. The gate capacitor is set at:
C1 =
I
I
GATE(UP)
INRUSH
•CL
Figure4. Safe Operating Area Required to Survive
Prototypical Transient Waveform
V
PK
τ
VIN
4356 F04
VREG
tr
LT4356-1/LT4356-2
15
Rev. C
For more information www.analog.com
Figure5.
Figure6. Auxiliary LDO Output with Optional Current Limit
C1
R3
4356 F05
LT4356S
GATE
M1
R1
D1
IN4148W
RLIM
*4.7Ω
D1*
BAV99
Q2
2N2905A OR
BCP53
INPUT 2.5V OUTPUT
≈ 150mA MAX
* OPTIONAL FOR
CURRENT LIMIT
LT4356S
AOUT
IN+
11
12
R6
100k
4356 F06
R4
249k
C3
47nF
R5
249k
C5
10µF
VOUT =1.25 R 4 +R5
R5
ILIM ≈0.7
RLIM
APPLICATIONS INFORMATION
The LTC4356 does not need extra compensation compo-
nents at the GATE pin for stability during an overvoltage or
overcurrent event. With transient input voltage step faster
than 5V/µs, a gate capacitor, C1, to ground is needed to
prevent self enhancement of the N-channel MOSFET.
The extra gate capacitance slows down the turn off time
during fault conditions and may allow excessive current
during an output short event. An extra resistor, R1, in series
with the gate capacitor can improve the turn off time. A
diode, D1, should be placed across R1 with the cathode
connected to C1 as shown in Figure5.
Reverse Input Protection
A blocking diode is commonly employed when reverse input
potential is possible, such as in automotive applications.
This diode causes extra power loss, generates heat, and
reduces the available supply voltage range. During cold
crank, the extra voltage drop across the diode is partic-
ularly undesirable.
The L
T4356 is designed to withstand reverse voltage
without damage to itself or the load. The VCC, SNS, and
SHDN pins can withstand up to 60V of DC voltage below
the GND potential. Back-to-back MOSFETs must be used
to eliminate the current path through their body diodes
(Figure7). Figure8 shows the approach with a P-Channel
MOSFET in place of Q2.
Figure7. Overvoltage Regulator with N-channel MOSFET
Reverse Input Protection
CTMR
0.1µF
RSNS
10mΩ
M1
IRLR2908
M2
IRLR2908
VIN
12V
VOUT
12V, 3A
CLAMPED
AT 16V
4356 F07
LT4356S
GND TMR
10 1
OUTSNS
35
SHDN
7
AOUT
11
IN+
12
VCC
6
EN
FLT
FB
9
8
2
D2*
SMAJ58CA
R2
4.99k
R1
59k
GATE
4
R7
10k
R5
1M
Q1
2N3904
D1
1N4148
R3
10Ω
R4
10Ω
*DIODES INC.
Auxiliary Amplifier
An uncommitted amplifier is included in the LT4356 to
provide flexibility in the system design. With the negative
input connected internally to the 1.25V reference, the am-
plifier can be connected as a level detect comparator with
external hysteresis. The open collector output pin, AOUT,
is capable of driving an opto or LED. It can also interface
with the system via a pull-up resistor to a supply voltage
up to 80V. Another use is to implement undervoltage
lockout, as shown in the typical application “Overvoltage
Regulator with Undervoltage Lockout.” In shutdown, the
auxiliary amplifier turns off in the LT4356-1 but continues
operating in the LT4356-2.
The amplifier can also be configured as a low dropout
linear regulator controller. With an external PNP transistor,
such as 2N2905A, it can supply up to 100mA of current
with only a few hundred mV of dropout voltage. Current
limit can be easily included by adding two diodes and one
resistor (Figure6).
LT4356-1/LT4356-2
16
Rev. C
For more information www.analog.com
APPLICATIONS INFORMATION
Shutdown
The LT4356 can be shut down to a low current mode when
the voltage at the SHDN pin goes below the shutdown
threshold of 0.6V. The quiescent current drops to 7µA for
the LT4356-1 and 60µA for the LT4356-2 which leaves the
auxiliary amplifier on.
The SHDN pin can be pulled up to VCC or below GND by
up to 60V without damaging the pin. Leaving the pin open
allows an internal current source to pull it up and turn
on the part while clamping the pin to 2.5V. The leakage
current at the pin should be limited to no more than 1µA
if no pull up device is used to help turn it on.
Supply T
ransient Protection
The LT4356 is guaranteed to be safe from damage with
supply voltages up to 100V. Nevertheless, voltage tran-
sients above 100V may cause permanent damage. During
a short-circuit condition, the large change in current flowing
through power supply traces and associated wiring can
cause inductive voltage transients which could exceed
100V. To minimize the voltage transients, the power trace
parasitic inductance should be minimized by using wide
traces. A small surge suppressor, D2, in Figure9, at the
input will clamp the voltage spikes.
A total bulk capacitance of at least 22µF low ESR electro-
lytic is required close to the source pin of MOSFET Q1. In
addition, the bulk capacitance should be at least 10 times
larger than the total ceramic bypassing capacitor on the
input of the DC/DC converter
.
Figure8. Overvoltage Regulator with P-Channel MOSFET
Reverse Input Protection
Figure9. Overvoltage Regulator with Low-Battery
CTMR
0.1µF
RSNS
10mΩ
M1
IRLR2908
M2
Si4435
VIN
12V
VOUT
12V, 3A
CLAMPED
AT 16V
4356 F08
LT4356S
GND TMR
10 1
OUTSNS
35
SHDN
7
AOUT
11
IN+
12
VCC
6
EN
FLT
FB
9
8
2
R2
4.99k
R1
59k
GATE
4
R6
10k
D1
1N5245
15V
R3
10Ω
D2*
SMAJ58CA
*DIODES INC.
CTMR
47nF
*SANYO 25CE22GA
R3
10Ω
R
SNS
10mΩ M1
IRLR2908
D2
SMAJ58A
VIN
4356 F09
LT4356S
GND TMR
OUTGATESNS
IN+
SHDN
AOUT FAULT
EN
FLTUNDERVOLTAGE
FB
CL*
22µF
DC-DC
CONVERTER
GND
SHDN
VCC
R2
4.99k
R4
383k
R5
100k
R1
59k
10 1
345
7
12
VCC
6
11
2
9
8
LT4356-1/LT4356-2
17
Rev. C
For more information www.analog.com
Layout Considerations
To achieve accurate current sensing, Kelvin connection
to the current sense resistor (RSNS in Figure9) is recom-
mended. The minimum trace width for 1oz copper foil is
0.02" per amp to ensure the trace stays at a reasonable
temperature. 0.03" per amp or wider is recommended.
Note that 1oz copper exhibits a sheet resistance of about
530µΩ/square. Small resistances can cause large errors in
high current applications. Noise immunity will be improved
significantly by locating resistive dividers close to the pins
with short VCC and GND traces.
Design Example
As a design example, take an application with the following
specifications: VCC = 8V to 14V DC with transient up to 80V,
VOUT ≤ 16V, current limit (ILIM) at 5A, low battery detection
at 6V, and 1ms of overvoltage early warning (Figure9).
First, calculate the resistive divider value to limit VOUT to
16V during an overvoltage event:
VREG =1.25V • R1 + R2
( )
R2
=16V
Set the current through R1 and R2 during the overvoltage
condition to 250µA.
R2 = 1.25V
250µA = 5k
Choose 4.99k for R2.
R1 = 16V – 1.25V
( )
• R2
1.25V
= 58.88k
The closest standard value for R1 is 59k.
Next calculate the sense resistor, RSNS, value:
RSNS = 50mV
I
LIM
= 50mV
5A = 10mΩ
CTMR is then chosen for 1ms of early warning time:
CTMR = 1ms • 5µA
100mV
= 50nF
The closest standard value for CTMR is 47nF.
Finally, calculate R4 and R5 for the 6V low battery thresh-
old detection:
6V = 1.25V • R4 + R5
( )
R5
Choose 100k for R5.
R4 = 6V – 1.25V
( )
• R5
1.25V
= 380k
Select 383k for R4.
The pass transistor, Q1, should be chosen to withstand
the output short condition with VCC = 14V.
The total overcurrent fault time is:
tOC = 47nF • 0.85V
45.5µA = 0.878ms
The power dissipation on Q1 equals to:
P = 14V • 50mV
10mΩ
= 70W
These conditions are well within the Safe Operating Area
of IRLR2908.
APPLICATIONS INFORMATION
LT4356-1/LT4356-2
18
Rev. C
For more information www.analog.com
Wide Input Range 5V to 28V Hot Swap
with Undervoltage Lockout
CTMR
1µF
R3
10Ω
R
SNS
20mΩ
M1
SUD50N03-10
V
IN
4356 TA02
LT4356DE-1
GND TMR
OUTGATESNS
IN+
SHDN
AOUT
V
OUT
EN
FLT
FB
VCC
R7
49.9k
R6
118k
CL
100µF
C1
47nF
TYPICAL APPLICATIONS
24V Overvoltage Regulator Withstands 150V at VIN
CTMR
0.1µF
M1
IRF640
VIN
24V
VOUT
CLAMPED AT 32V
4356 TA03
LT4356DE
GND TMR
10 1
OUTSNS
35
SHDN
7
FLT
8
EN
9
VCC
6FB 2
D2*
SMAT70A
R2
4.99k
R1
118k
GATE
4
R3
10Ω
R9
1k
1W
*DIODES INC.
LT4356-1/LT4356-2
19
Rev. C
For more information www.analog.com
TYPICAL APPLICATIONS
Overvoltage Regulator with Undervoltage Lockout
CTMR
0.1µF
R3
10Ω
R
SNS
20mΩ
M1
IRLR2908
VIN
4356 TA04
LT4356DE-2
GND TMR
OUTGATESNS
IN+
SHDN
AOUT
VOUT
CLAMPED AT 16V
EN
FLT
FB
VCC
R2
4.99k
R7
100k
R6
280k
R4
1M
R5
1M
R1
59k
D2*
SMAJ58A
UV RISING = 5.04V
*DIODES INC.
Overvoltage Regulator with Low Battery Detection and Output Keep Alive During Shutdown
R3
10Ω
RSNS
10mΩ
VIN
12V
VOUT
12V, 4A
CLAMPED AT 16V
4356 TA05
LT4356DE
GND TMR
10 1
OUTGATESNS
345
IN+
12
SHDN
7
VCC
VDD
6
EN
FLT
FB
9
AOUT LBO
11
8
2
D1
1N4746A
18V
1W
R2
24.9k
R6
47k
R4
402k
R5
105k
R1
294k
1k
0.5W
M1
IRLR2908
M2
VN2222
CTMR
0.1µF
D2*
SMAJ58A
*DIODES INC.
LT4356-1/LT4356-2
20
Rev. C
For more information www.analog.com
TYPICAL APPLICATIONS
2.5A, 48V Hot Swap with Overvoltage Output Regulation at 72V and UV Shutdown at 35V
D1
1N4714
BV = 33V
C1
6.8nF
CTMR
0.1µF
R3
10Ω
RSNS
15mΩ VOUT
48V
2.5A
4356 TA06
LT4356DE
GND TMR
10 1
OUTGATESNSVCC
3456
SHDN
EN
FLT
7
9
8
AOUT PWRGD
FB
IN+
11
2
12
R7
1M
CL
300µF
R5
4.02k
R4
140k
R6
100k
R8
47k
R2
4.02k
R1
226k
M1
FDB3632
D2*
SMAT70A
VIN
48V
*DIODES INC.
2.5A, 28V Hot Swap with Overvoltage Output Regulation at 36V and UV Shutdown at 15V
D1
1N4700
BV = 13V
C1
6.8nF
CTMR
0.1µF
R3
10Ω
RSNS
15mΩ VOUT
28V
2.5A
4356 TA07
LT4356DE
GND TMR
10 1
OUTGATESNSVCC
3456
SHDN
EN
FLT
7
9
8
AOUT PWRGD
FB
IN+
11
2
12
R7
1M
CL
300µF
R5
4.02k
R4
113k
R6
27k
R8
47k
R2
4.02k
R1
110k
M1
FDB3632
D2*
SMAT70A
*DIODES INC.
VIN
28V
LT4356-1/LT4356-2
21
Rev. C
For more information www.analog.com
TYPICAL APPLICATIONS
Overvoltage Regulator with Reverse Input Protection Up to –80V
250mA High Voltage Low Dropout Linear Regulator
CTMR
0.1µF
R
SNS
10mΩ
M1
IRLR2908
M2
IRLR2908
VIN
12V
VOUT
12V, 3A
CLAMPED
AT 16V
4356 TA08
LT4356DE
GND TMR
10 1
OUTSNSVCC
35
SHDN
7
AOUT
11
IN+
12
6
EN
FLT
FB
9
8
2
D2*
SMAJ58CA
R2
4.99k
R1
59k
GATE
4
R7
10k
D3**
IN4148
* DIODES INC.
** OPTIONAL COMPONENT FOR
REDUCED STANDBY CURRENT
R5
1M
Q1
2N3904
D1
1N4148
R3
10Ω
R4
10Ω
M1
PSMN4R8 –100BSE
VIN
20V
VOUT
16V/250mA
RSNS
0.2Ω
4356 TA09
LT4356DE
GND TMR
10 1
OUTSNS
35
SHDN
7
FLT
8
EN
9
VCC
6FB 2
R2
4.99k
R3
7.5k
R1
59k
CL
100µF
GATE
4
R3
10Ω
*THE OUTPUT LOAD STEP
RESPONSE IS SLOW DUE TO
THE RESPONSE TIME OF THE
INTERNAL CHARGE PUMP
LT4356-1/LT4356-2
22
Rev. C
For more information www.analog.com
DE/UE Package
12-Lead Plastic DFN (4mm × 3mm)
(Reference LTC DWG # 05-08-1695 Rev D)
4.00 ±0.10
(2 SIDES)
3.00 ±0.10
(2 SIDES)
NOTE:
1. DRAWING PROPOSED TO BE A VARIATION OF VERSION
(WGED) IN JEDEC PACKAGE OUTLINE M0-229
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON THE TOP AND BOTTOM OF PACKAGE
0.40 ± 0.10
BOTTOM VIEW—EXPOSED PAD
1.70 ± 0.10
0.75 ±0.05
R = 0.115
TYP
R = 0.05
TYP
2.50 REF
16
127
PIN 1 NOTCH
R = 0.20 OR
0.35 × 45°
CHAMFER
PIN 1
TOP MARK
(NOTE 6)
0.200 REF
0.00 – 0.05
(UE12/DE12) DFN 0806 REV D
2.50 REF
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
2.20 ±0.05
0.70 ±0.05
3.60
±0.05
PACKAGE OUTLINE
3.30 ±0.10
0.25 ± 0.05
0.50 BSC
1.70 ± 0.05
3.30 ±0.05
0.50 BSC
0.25 ± 0.05
PACKAGE DESCRIPTION
LT4356-1/LT4356-2
23
Rev. C
For more information www.analog.com
PACKAGE DESCRIPTION
MSOP (MS) 0213 REV F
0.53 ±0.152
(.021 ±.006)
SEATING
PLANE
0.18
(.007)
1.10
(.043)
MAX
0.17 –0.27
(.007 – .011)
TYP
0.86
(.034)
REF
0.50
(.0197)
BSC
1234 5
4.90 ±0.152
(.193 ±.006)
0.497 ±0.076
(.0196 ±.003)
REF
8910 76
3.00 ±0.102
(.118 ±.004)
(NOTE 3)
3.00 ±0.102
(.118 ±.004)
(NOTE 4)
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
0.254
(.010) 0° – 6° TYP
DETAIL “A”
DETAIL “A”
GAUGE PLANE
5.10
(.201)
MIN
3.20 – 3.45
(.126 – .136)
0.889 ±0.127
(.035 ±.005)
RECOMMENDED SOLDER PAD LAYOUT
0.305 ±0.038
(.0120 ±.0015)
TYP
0.50
(.0197)
BSC
0.1016 ±0.0508
(.004 ±.002)
MS Package
10-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1661 Rev F)
LT4356-1/LT4356-2
24
Rev. C
For more information www.analog.com
PACKAGE DESCRIPTION
.016 – .050
(0.406 – 1.270)
.010 – .020
(0.254 – 0.508)× 45°
0° – 8° TYP
.008 – .010
(0.203 – 0.254)
1
N
2345678
N/2
.150 – .157
(3.810 – 3.988)
NOTE 3
16 15 14 13
.386 – .394
(9.804 – 10.008)
NOTE 3
.228 – .244
(5.791 – 6.197)
12 11 10 9
S16 REV G 0212
.053 – .069
(1.346 – 1.752)
.014 – .019
(0.355 – 0.483)
TYP
.004 – .010
(0.101 – 0.254)
.050
(1.270)
BSC
.245
MIN
N
1 2 3 N/2
.160 ±.005
RECOMMENDED SOLDER PAD LAYOUT
.045 ±.005
.050 BSC
.030 ±.005
TYP
INCHES
(MILLIMETERS)
NOTE:
1. DIMENSIONS IN
2. DRAWING NOT TO SCALE
3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)
4. PIN 1 CAN BE BEVEL EDGE OR A DIMPLE
S Package
16-Lead Plastic Small Outline (Narrow .150 Inch)
(Reference LTC DWG # 05-08-1610 Rev G)
LT4356-1/LT4356-2
25
Rev. C
For more information www.analog.com
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog
Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications
subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
REVISION HISTORY
REV DATE DESCRIPTION PAGE NUMBER
A 05/10 Revised Features and Description
Added parameters to VOL and updated Max value for VSHDN(FLT) in the Electrical Characteristics section
Revised Pin Functions section
Replaced Figure6 and made text edits in the Operation and Applications Information sections
Updated drawings in the Typical Applications section
1
4, 5
8
10-17
19, 21
B 09/17 Updated TMR pin function with minimum recommended capacitance 8
C 01/20 Revised SHDN Pin Function Description 8
(Revision history begins at Rev A)
LT4356-1/LT4356-2
26
Rev. C
For more information www.analog.com
01/20
www.analog.com
ANALOG DEVICES, INC. 2009–2020
TYPICAL APPLICATION
PART NUMBER DESCRIPTION COMMENTS
LT1641-1/LT1641-2 Positive High Voltage Hot Swap Controllers Active Current Limiting, Supplies From 9V to 80V
LTC1696 Overvoltage Protection Controller ThinSOT™ Package, 2.7V to 28V
LTC1735 High Efficiency Synchronous Step-Down
Switching Regulator
Output Fault Protection, 16-Pin SSOP
LTC1778 No RSENSE™ Wide Input Range Synchronous
Step-Down Controller
Up to 97% Efficiency, 4V ≤ VIN ≤ 36V, 0.8V ≤ VOUT ≤ (0.9)(VIN),
IOUT Up to 20A
LTC2909 Triple/Dual Inputs UV/OV Negative Monitor Pin Selectable Input Polarity Allows Negative and OV Monitoring
LTC2912/LTC2913 Single/Dual UV/OV Voltage Monitor Ads UV and OV Trip Values, ±1.5% Threshold Accuracy
LTC2914 Quad UV/OV Monitor For Positive and Negative Supplies
LTC3727/LTC3727-1 2-Phase, Dual, Synchronous Controller 4V ≤ VIN ≤ 36V, 0.8V ≤ VOUT ≤ 14V
LTC3827/LTC3827-1 Low IQ, Dual, Synchronous Controller 4V ≤ VIN ≤ 36V, 0.8V ≤ VOUT ≤ 10V, 80µA Quiescent Current
LTC3835/LTC3835-1 Low IQ, Synchronous Step-Down Controller Single Channel LTC3827/LTC3827-1
LT3845 Low IQ, Synchronous Step-Down Controller 4V ≤ VIN ≤ 60V, 1.23V ≤ VOUT ≤ 36V, 120µA Quiescent Current
LTC3850 Dual, 550kHz, 2-Phase Synchronous Step-Down
Controller
Dual 180° Phased Controllers, VIN 4V to 24V, 97% Duty Cycle, 4mm × 4mm
QFN-28, SSOP-28 Packages
LT4256-1/LT4256-2 Positive 48V Hot Swap Controller with
Open-Circuit Detect
Foldback Current Limiting, Open-Circuit and Overcurrent Fault Output, Up to
80V Supply
LTC4260 Positive High Voltage Hot Swap Controller with
ADC and I2C
Wide Operating Range 8.5V to 80V
LTC4352 Ideal MOSFET ORing Diode External N-channel MOSFETs Replace ORing Diodes, 0V to 18V Operation
LTC4354 Negative Voltage Diode-OR Controller Controls Two N-channel MOSFETs, 1µs Turn-Off, 80V Operation
LTC4355 Positive Voltage Diode-OR Controller Controls Two N-channel MOSFETs, 0.5µs Turn-Off, 80V Operation
Overvoltage Regulator with Linear Regulator Up to 100mA
CTMR
0.1µF
R3
10Ω
RSNS
10mΩ
Q2
2N2905A
VIN
12V
VOUT
12V, 3A
CLAMPED AT 16V
2.5V, 100mA
4356 TA10
LT4356DE
GND TMR
10 1
OUTGATESNS
345
AOUT
11
SHDN
7
VCC
6
EN
FLT
FB
9
IN+12
8
2
C5
10µF
R2
4.99k
R6
100k
R1
59k
R5
249k
R4
249k
C3
47nF
M1
IRLR2908
D2*
SMAJ58A
*DIODES INC.
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