REV. 0
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may result from its use. No license is granted by implication or otherwise
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One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700 www.analog.com
Fax: 781/326-8703 © 2003 Analog Devices, Inc. All rights reserved.
ADP3522
GSM Power Management System
FEATURES
Handles all GSM Baseband Power Management
6 LDOs Optimized for Specific GSM Subsystems
Li-Ion Battery Charge Function
Optimized for the AD20msp430 Baseband Chipset
Reduced Package Size: 5 mm 5 mm LFCSP-32
APPLICATIONS
GSM/GPRS Handsets
FUNCTIONAL BLOCK DIAGRAM
P
WRONKEY
PWRONIN
TCXOEN
CHRDET
EOC
BATSNS
VRTCIN
ROWX
CHGEN
ISENSE
CHRIN
RESCAP
VBAT VBAT2
POWER-UP
SEQUENCING
AND
PROTECTION
LOGIC
SIMEN
SIMVSEL
DGND
VCORE
AGND
MVBAT
VTCXO
VAN
VMEM
VRTC
REFOUT
VSIM
GATEDR
GATEIN
RESET
ADP3522
SIM
LDO
DIGITAL
CORE LDO
ANALOG
LDO
TCXO
LDO
MEMORY
LDO
RTC
LDO
REF
BUFFER
BATTERY
VOLTAGE
DIVIDER
BATTERY
CHARGE
CONTROLLER
GENERAL DESCRIPTION
The ADP3522 is a multifunction power system chip optimized
for GSM/GPRS handsets, especially those based on the Analog
Devices AD20msp430 system solution with 1.8 V digital
baseband processors, such as the AD6525, AD6526, and
AD6528. It contains six LDOs, one to power each of the critical
GSM subblocks. Sophisticated controls are available for power-
up during battery charging, keypad interface, and RTC alarm.
The charge circuit maintains low current charging during the
initial charge phase and provides an end of charge (EOC) signal
when a Li-Ion battery is being charged. This product also meets
the market trend of reduced size with a new LFCSP package.
Its footprint is only 5 mm 5 mm and yet offers excellent ther-
mal performance due to the exposed die attached paddle.
The ADP3522 is specified over the temperature range of
–20°C to +85°C.
REV. 0–2–
ADP3522–SPECIFICATIONS
ELECTRICAL CHARACTERISTICS
1
Parameter Symbol Conditions Min Typ Max Unit
SHUTDOWN SUPPLY CURRENT ICC
VBAT 2.5 V VBAT = VBAT2 = 2.3 V 15 40 µA
(Deep Discharged Lockout Active)
2.5 V < VBAT 3.2 V VBAT = VBAT2 = 3.0 V 30 55 µA
(UVLO Active)
VBAT > 3.2 V VBAT = VBAT2 = 4.0 V 45 80 µA
OPERATING GROUND CURRENT IGND VBAT = 3.6 V
VSIM, VCORE, VMEM, VRTC On Minimum Loads 225 300 µA
All LDOs On Minimum Loads 345 450 µA
All LDOs On Maximum Loads 1.0 3.0 % of Max
Load
UVLO ON THRESHOLD VUVLO Rising Edge 3.2 3.3 V
UVLO HYSTERESIS 200 mV
DEEP DISCHARGED LOCKOUT ON VDDLO Falling Edge 2.4 2.75 V
THRESHOLD
DEEP DISCHARGED LOCKOUT 100 mV
HYSTERESIS
INPUT HIGH VOLTAGE V
IH
PWRONIN 1.0 V
TCXOEN, SIMEN, 1.5 V
CHGEN, GATEIN, SIMVSEL
INPUT LOW VOLTAGE V
IL
0.3 V
(PWRONIN, TCXOEN, SIMEN,
CHGEN, SIMVSEL)
PWRONIN Pin Pull-Down Resistor R
PD
200 1000 5000 k
INPUT HIGH BIAS CURRENT I
IH
1.0 µA
(TCXOEN, SIMEN, CHGEN,
SIMVSEL )
INPUT LOW BIAS CURRENT I
IL
–1.0 µA
(PWRONIN, TCXOEN, SIMEN,
CHGEN, SIMVSEL)
PWRONKEY INPUT HIGH VOLTAGE V
IH
0.7 VBAT V
PWRONKEY INPUT LOW VOLTAGE V
IL
0.3 VBAT V
PWRONKEY INPUT PULL-UP 70 100 130 k
RESISTANCE TO VBAT
THERMAL SHUTDOWN 160 ºC
THRESHOLD
2
THERMAL SHUTDOWN 45 ºC
HYSTERESIS
(–20C < TA < +85C, VBAT = VBAT2 = 3 V–5.5 V, CVSIM = CVCORE = CVAN =
CVMEM = 2.2 F, VTCXO = 0.22 F, CVRTC = 0.1 F, CVBAT = 10 F, minimum
loads applied on all outputs, unless otherwise noted.)
REV. 0
ADP3522
–3–
Parameter Symbol Conditions Min Typ Max Unit
ROWX CHARACTERISTICS
ROWX Output Low Voltage V
OL
PWRONKEY = Low
I
OL
= 200 µA0.4 V
ROWX Output High Leakage Current I
IH
PWRONKEY = High
V(ROWX) = 5 V 1 µA
SIM CARD LDO
(VSIM)
Output Voltage VSIM Line, Load, Temperature 1.70 1.80 1.90 V
SIMVSEL = Low
Output Voltage VSIM Line, Load, Temperature 2.80 2.85 2.92 V
SIMVSEL = High
Line Regulation VSIM 2 mV
Load Regulation VSIM 50 µA I
LOAD
20 mA 2 mV
VBAT = 3.6 V
Output Capacitor Required for C
O
2.2 µF
Stability
Dropout Voltage V
DO
V
O
= V
INITIAL
– 100 mV,
I
LOAD
= 20 mA, 35 100 mV
VSIM = 2.85 V
DIGITAL CORE LDO (VCORE)
Output Voltage VCORE Line, Load, Temperature 1.75 1.80 1.85 V
Line Regulation VCORE 2 mV
Load Regulation VCORE 50 µA I
LOAD
100 mA 8 mV
VBAT = 3.6 V
Output Capacitor Required for C
O
2.2 µF
Stability
RTC LDO
REAL-TIME CLOCK LDO/
COIN CELL CHARGER (VRTC)
Maximum Output Voltage VRTC 1 µA I
LOAD
10 µA1.861.95 2.0 V
Maximum Output Current VRTC = 0.5 V 4.0 mA
Off Reverse Input Current I
L
VRTC = 1.90 V,
VBAT = 1.70 V, T
A
= 25
°
C0.5 µA
Output Capacitor Required for C
O
0.1 µF
Stability
ANALOG LDO (VAN)
Output Voltage VAN Line, Load, Temperature 2.50 2.55 2.60 V
Line Regulation VAN 2 mV
Load Regulation VAN 50 µA I
LOAD
180 mA, 11 mV
VBAT = 3.6 V
Output Capacitor Required for C
O
2.2 µF
Stability
Ripple Rejection VBAT/ f = 217 Hz (t = 4.6 ms) 65 dB
VAN
3
VBAT = 3.6 V
Output Noise Voltage V
NOISE
f = 10 Hz to 100 kHz 80 µV rms
I
LOAD
= 180 mA
VBAT = 3.6 V
Dropout Voltage V
O
= V
INITIAL
– 100 mV, 160 400 mV
I
LOAD
= 180 mA
REV. 0–4–
ADP3522
ELECTRICAL CHARACTERISTICS
1
(–20C < TA < +85C, VBAT = VBAT2 = 3 V–5.5 V, CVSIM = CVCORE = CVAN = CVMEM =
2.2 F, VTCXO = 0.22 F, CVRTC = 0.1 F, CVBAT = 10 F, minimum loads applied on
all outputs, unless otherwise noted.)
Parameter Symbol Conditions Min Typ Max Unit
TCXO LDO (VTCXO)
Output Voltage VTCXO Line, Load, Temperature 2.711 2.75 2.789 V
Line Regulation VTCXO 2 mV
Load Regulation VTCXO 50 µA I
LOAD
20 mA, 2 mV
VBAT = 3.6 V
Output Capacitor Required for C
O
0.22 µF
Stability
Dropout Voltage V
DO
V
O
= V
INITIAL
– 100 mV 160 300 mV
I
LOAD
= 20 mA
Ripple Rejection VBAT/ f = 217 Hz (t = 4.6 ms) 65 dB
VTCXO VBAT = 3.6 V
Output Noise Voltage V
NOISE
f = 10 Hz to 100 kHz 80 µV rms
I
LOAD
= 20 mA, VBAT = 3.6 V
MEMORY LDO (VMEM)
Output Voltage-3 VMEM Line, Load, Temperature 2.740 2.80 2.850 V
Output Voltage-1.8 VMEM Line, Load, Temperature 1.80 1.85 1.90 V
Line Regulation VMEM 2 mV
Load Regulation VMEM 50 µA < I
LOAD
< 150 mA 12 mV
VBAT = 3.6 V
Output Capacitor Required for C
O
2.2 µF
Stability
Dropout Voltage-3 V
O
= V
INITIAL
– 100 mV 160 360 mV
I
LOAD
= 150 mA
REFOUT
Output Voltage VREFOUT Line, Load, Temperature 1.19 1.21 1.23 V
Line Regulation VREFOUT Min Load 0.2 mV
Load Regulation VREFOUT 0 µA < I
LOAD
< 50 µA0.5 mV
VBAT = 3.6 V
Ripple Rejection VBAT/ f = 217 Hz (t = 4.6 ms) 65 75 dB
VREFOUT
Maximum Capacitive Load C
O
100 pF
Output Noise Voltage V
NOISE
f = 10 Hz to 100 kHz 40 µV rms
RESET GENERATOR (RESET)
Output High Voltage V
OH
I
OH
= +500 µAV
MEM
– 0.25 V
Output Low Voltage V
OL
I
OL
= –500 µA0.25V
Output Current I
OL
/I
OH
V
OL
= 0.25 V, 1 mA
V
OH
= V
MEM
– 0.25 V
Delay Time per Unit Capacitance t
D
0.6 1.2 2.4 ms/nF
Applied to RESCAP Pin
BATTERY VOLTAGE DIVIDER
Divider Ratio
BATSNS/
TCXOEN = High 2.32 2.35 2.37
MVBAT
Divider Impedance at MVBAT Z
O
59.5 85 110 k
Divider Leakage Current TCXOEN = Low 1 µA
Divider Resistance TCXOEN = High 215 300 385 k
REV. 0
ADP3522
–5–
Parameter Symbol Conditions Min Typ Max Unit
BATTERY CHARGER
Charger Output Voltage BATSNS
4.35 V CHRIN
10 V
3
4.150 4.200 4.250 V
CHGEN = Low, No Load
CHRIN = 10 V 4.155 4.250 V
CHGEN = Low, No Load
0°C < T
A
< 50°C
Load Regulation BATSNS CHRIN = 5 V 15 mV
0CHRIN ISENSE
< Current Limit Threshold
CHGEN = Low
CHRDET On Threshold CHRIN –
VBAT 30 90 150 mV
CHRDET Hysteresis 40 mV
CHRDET Off Delay
4
CHRIN < VBAT 6 ms/nF
CHRIN Supply Current CHRIN = 5 V 0.6 mA
Current Limit Threshold CHRIN –
ISENSE
High Current Limit CHRIN = 5 V DC 142 160 190 mV
(UVLO Not Active) VBAT = 3.6 V
CHGEN = Low
CHRIN = 5 V DC 149 160 180 mV
VBAT = 3.6 V
CHGEN = Low
0°C < T
A
< 50°C
Low Current Limit VBAT = 2 V 20 35 mV
(UVLO Active) CHGEN = Low
CHRIN = 5 V – 10 V
ISENSE Bias Current 200 µA
EOC Signal Threshold
CHRIN –
ISENSE
CHRIN = 5 V DC 14 35 mV
VBAT > 4.0 V
CHGEN = Low
EOC Reset Threshold VBAT CHGEN = Low 3.82 3.96 4.10 V
GATEDR Transition Time t
R
, t
F
CHRIN = 5 V 0.1 1 µs
VBAT > 3.6 V
CHGEN = High, C
L
= 2 nF
GATEDR High Voltage V
OH
CHRIN = 5 V 4.5 V
VBAT = 3.6 V
CHGEN = High
GATEIN = High
I
OH
= –1 mA
GATEDR Low Voltage V
OL
CHRIN = 5 V 0.5 V
VBAT = 3.6 V
CHGEN = High
GATEIN = Low
I
OL
= 1 mA
Output High Voltage V
OH
I
OH
= –250 µAV
MEM
– 0.25 V
(EOC, CHRDET)
Output Low Voltage V
OL
I
OL
= 250 µA0.25V
(EOC, CHRDET)
NOTES
1
All limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods.
2
This feature is intended to protect against catastrophic failure of the device. Maximum allowed operating junction temperature is 125ºC. Operation beyond 125ºC
could cause permanent damage to the device.
3
No isolation diode is present between the charger input and the battery.
4
Delay set by external capacitor on the RESCAP pin.
Specifications subject to change without notice.
REV. 0–6–
ADP3522
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although the
ADP3522 features proprietary ESD protection circuitry, permanent damage may occur on devices
subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended
to avoid performance degradation or loss of functionality.
ABSOLUTE MAXIMUM RATINGS*
Voltage on Any Pin with Respect to
Any GND Pin . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +10 V
Voltage on Any Pin May Not Exceed VBAT, with the Following
Exceptions: CHRIN, BASE, ISENSE
Storage Temperature Range . . . . . . . . . . . . . –65C to +150C
Operating Ambient Temperature Range . . . . . –20C to +85C
Maximum Junction Temperature . . . . . . . . . . . . . . . . . 125C
JA
, Thermal Impedance (LFCSP 5 mm 5 mm)
4-Layer JEDEC PCB . . . . . . . . . . . . . . . . . . . . . . . . . . 32C/W
2-Layer SEMI PCB . . . . . . . . . . . . . . . . . . . . . . . . . . 108C/W
Lead Temperature Range (Soldering, 60 sec.) . . . . . . . . 300C
*Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability. Absolute maximum
ratings apply individually only, not in combination. Unless otherwise specified all
other voltages are referenced to GND.
PIN CONFIGURATION
TOP VIEW
(Not to Scale)
1
2
3
4
5
6
7
TOP VIEW
ADP3522
8
24
23
22
21
20
19
18
17
9
10
11
12
13
14
15
16
32
31
30
29
28
27
26
25
PIN 1
INDICATOR
SIMEN
VRTCIN
VRTC
BATSNS
MVBAT
CHRDET
CHRIN
SIMVSEL
NC
VAN
VBAT
VCORE
VMEM
VBAT2
VSIM
NC
GATEDR
GATEIN
DGND
ISENSE
EOC
CHGEN
RESCAP
RESET
NC
ROWX
PWRONKE
Y
PWRONIN
TCXOEN
AGND
REFOUT
VTCXO
ORDERING GUIDE
Memory
LDO Temperature
Package
Model Output Range Option
ADP3522ACP-3 2.80 V –20C to +85CCP-32
ADP3522ACP-1.8 1.80 V –20C to +85CCP-32
PIN FUNCTION DESCRIPTIONS
Pin Mnemonic Description
1SIMEN SIM LDO Enable
2VRTCIN RTC LDO Input Voltage
3VRTC Real-Time Clock Supply/
Coin Cell Battery Charger
4BATSNS Battery Voltage Sense Input
5MVBAT Divided Battery Voltage Output
6CHRDET Charge Detect Output
7CHRIN Charger Input Voltage
8SIMVSEL Programs VSIM Output;
Low: 1.8 V
9GATEDR Charger Drive Output
10 GATEIN Microprocessor Charger Gate
Control Input
11 DGND Digital Ground
12 ISENSE Charge Current Sense Input
13 EOC End of Charge Output
14 CHGEN Charge Enable Control Input
15 RESCAP Reset Delay Time
16 RESET Main Reset, Open Drain
17, 24, 32 NC No Connection
18 VSIM SIM LDO Output
19 VBAT2 Battery Input Voltage 2
20 VMEM Memory LDO Output
21 VCORE Digital Core LDO Output
22 VBAT Battery Input Voltage
23 VAN Analog LDO Output
25 VTCXO TCXO LDO Output
26 REFOUT Output Reference
27 AGND Analog Ground
28 TCXOEN TCXO LDO Enable and
MVBAT Enable
29 PWRONIN Power On/Off Signal from
Microprocessor
30 PWRONKEY Power On/Off Key
31 ROWX Power Key Interface Output
REV. 0
Typical Performance Characteristics–ADP3522
–7–
VBAT – V
450
400
350
300
250
200
150
100
3.0 3.5 4.0 4.5 5.0 5.5
I
GND
A
50
0
ALL LDO, MVBAT, REFOUT,
ON_MIN_LOAD (SIMEN = H,
TCXOEN = H)
VCORE, VMEM, VRTC,
ON_MIN_LOAD (SIMEN = L,
TCXOEN = L)
VSIM, VCORE, VMEM, VRTC,
ON_MIN_LOAD (SIMEN = H,
TCXOEN = L)
TPC 1. Ground Current vs.
Battery Voltage
LOAD CURRENT – mA
180
160
140
120
0
DROPOUT VOLTAGE – mV
050100 150 200
VMEM VAN
VTCXO
VSIM
100
80
60
40
20
TPC 4. Dropout Voltage vs.
Load Current
VBAT
VAN
VCORE
10mV/DIV
10mV/DIV
3.2
3.0
TIME – 100s/DIV
VSIM 10mV/DIV
TPC 7. Line Transient
Response, Minimum Loads
VRTC – V
10000
1000
100
10
IRTC – A
0 0.5 1.0 1.5 2.0
+85C
+25C
–20C
TPC 2. RTC I/V Characteristic
VBAT
VTCXO
VMEM
10mV/DIV
10mV/DIV
3.2
3.0
TIME – 100s/DIV
TPC 5. Line Transient
Response, Minimum Loads
VBAT
VCORE
VSIM
10mV/DIV
10mV/DIV
3.2
3.0
VAN 10mV/DIV
TIME – 100s/DIV
TPC 8. Line Transient
Response, Maximum Loads
RTC REVERSE LEAKAGE
(VBAT = 2.3V)
RTC REVERSE LEAKAGE
(VBAT = FLOAT)
TEMPERATURE – C
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
REVERSE LEAKAGE CURRENT – A
25 30 35 40 45 50 55 60 65 70 75 80 85
TPC 3. VRTC Reverse Leakage
Current vs. Temperature
VBAT
VTCXO
VMEM
10mV/DIV
10mV/DIV
3.2
3.0
TIME – 100s/DIV
TPC 6. Line Transient
Response, Maximum Loads
LOAD
20mA
VTCXO 10mV/DIV
2mA
TIME – 200s/DIV
TPC 9. VTCXO Load Step
REV. 0–8–
ADP3522
LOAD
20mA
VSIM 10mV/DIV
2mA
TIME – 200s/DIV
TPC 10. VSIM Load Step
TIME – 200s/DIV
180mA
LOAD 18mA
20mV/DIV
TPC 13. VAN Load Step
TIME – 100s/DIV
PWRONIN (2V/DIV)
REFOUT (100mV/DIV)
VMEM = 2.8 (100mV/DIV)
VTCXO (100mV/DIV)
TPC 16. Turn On Transient
by PWRONIN, Minimum
Load (Part 3)
TIME – 200s/DIV
150mA
LOAD
15mA
VMEM
20mV/DIV
TPC 11. VMEM Load Step
TIME – 400s/DIV
PWRONIN (2V/DIV)
VAN (100mV/DIV)
VSIM = 2.8 (100mV/DIV)
VCORE (100mV/DIV)
TPC 14. Turn On Transient
by PWRONIN, Minimum
Load (Part 1)
TIME – 1ms/DIV
PWRONIN (2V/DIV)
VSIM = 1.8 (100V/DIV)
TPC 17. Turn On Transient
by PWRONIN, Minimum
Load (Part 4)
TIME – 200s/DIV
100mA
LOAD
10mA
VCORE
10mV/DIV
TPC 12. VCORE Load Setup
TIME – 200s/DIV
PWRONIN (2V/DIV)
VMEM = 1.8 (100mV/DIV)
TPC 15. Turn On Transient
by PWRONIN, Minimum
Load (Part 2)
TIME – 20s/DIV
PWRONIN (2V/DIV)
VAN (100mV/DIV)
VSIM = 2.8 (100mV/DIV)
VCORE (100mV/DIV)
TPC 18. Turn On Transient
by PWRONIN, Maximum
Load (Part 1)
REV. 0
ADP3522
–9–
TIME – 20s/DIV
PWRONIN (2V/DIV)
VSIM = 1.8 (100mV/DIV)
TPC 19. Turn On Transient
by PWRONIN, Maximum
Load (Part 2)
FREQUENCY – Hz
80
70
0
60
50
10
40
30
20
4 100
k
10 100 1k 10k
RIPPLE REJECTION – dB
VTCXO
VAN
VCORE
REFOUT
MLCC OUTPUT CAPS
VBAT = 3.2V, FULL LOADS
TPC 22. Ripple Rejection vs.
Frequency
TEMPERATURE – C
4.25
4.24
4.23
4.22
4.21
4.20
4.19
4.18
4.17
4.16
4.15
40–20 0 20 60 80 100 120–40
CHARGER VOUT – V
TPC 25. Charger V
OUT
vs.
Temperature, V
IN
= 5.0 V,
I
LOAD
= 10 mA
TIME – 100s/DIV
PWRONIN (2V/DIV)
REFOUT (100mV/DIV)
VMEM = 2.8(100mV/DIV)
VTCXO (100mV/DIV)
TPC 20. Turn On Transient
by PWRONIN, Maximum
Load (Part 3)
VBAT – V
80
70
60
50
40
30
20
10
0
RIPPLE REJECTION – dB
2.5 2.6 2.7 2.8 2.9 3.0 3.1 3.2 3.3
REFOUT
VAN
VMEM
VTCXO VSIM = 2.8V
FREQ = 217Hz,
MAX LOADS
VSIM
TPC 23. Ripple Rejection vs.
Battery Voltage
4.24
4.23
4.22
4.21
4.20
0 200 400 600 800
OUTPUT VOLTAGE – V
ILOAD – mA
VIN = 5.0V
RSENSE = 250m
TPC 26. Charger V
OUT
vs.
I
LOAD
(V
IN
= 5.0 V)
TIME – 20s/DIV
PWRONIN (2V/DIV)
VMEM = 1.8 (100mV/DIV)
TPC 21. Turn On Transient
by PWRONIN, Maximum
Load (Part 4)
FREQUENCY – Hz
600
500
200
100
0
400
300
10 100
k
100 1k 10k
VOLTAGE SPECTRAL NOISE DENSITY – nV/ Hz
FULL LOAD
MLCC CAPS
VAN
REF
TCXO
TPC 24. Output Noise Density
INPUT VOLTAGE – V
4.24
4.23
4.22
4.21
4.20
5678910
OUTPUT VOLTAGE – V
I
LOAD
= 10mA
R
SENSE
= 250m
I
LOAD
= 500mA
TPC 27. Charger V
OUT
vs. V
IN
REV. 0–10–
ADP3522
Table I. LDO Control Logic
DDLO
UVLO
CHRDET
PWRONKEY
PWRONIN
TCXOEN
SIMEN
VSIM
VCORE
VMEM
VRTC
VAN
VTCXO
REFOUT
MVBAT
PHONE STATUS
State No. 1
Battery Deep Discharged L X X X X X X OFF OFF OFF OFF OFF OFF OFF OFF
State No. 2
Phone Off H L XXXXXOFFOFFOFFONOFFOFFOFFOFF
State No. 3
Phone Off,
Turn-On Allowed H H L H L X X OFF OFF OFF ON OFF OFF OFF OFF
State No. 4
Charger Applied H H H X X X L OFF ON ON ON ON ON ON ON*
State No. 5
Phone Turned On by
User Key H H X L X X L OFF ON ON ON ON ON ON ON*
State No. 6
Deep Sleep H H L H H L H ON ON ON ON OFF OFF OFF OFF
State No. 7
Active H H L HHHHONONONONONONONON
State No. 8
Reset SIM Card H H L H H H L OFF ON ON ON ON ON ON ON
*The state of MVBAT is determined by TCXOEN. When TCXOEN is high, MVBAT is ON.
STATE NO.
REV. 0
ADP3522
–11–
P
WRONKEY
PWRONIN
ROWX
TCXOEN
RESCAP
SIMEN
CHRDET
EOC
BATSNS
CHGEN
ISENSE
CHRIN
GATEDR
GATEIN
MVBAT
Li-ION
BATTERY
CHARGE
CONTROLLER
AND
PROCESSOR
CHARGE
INTERFACE
RESET
GENERATOR
CHARGER
DETECT
OVERTEMP
SHUTDOWN
DEEP
DISCHARGED
UVLO
UVLO
VRTCIN
VBAT VBAT2
VCORE
VTCXO
VAN
VSIM
RESET
VMEM
VRTC
REFOUT
DGND
AGND
SIMVSEL
SIM LDO
VBAT
VREF
EN DGND
VSEL
OUT
VBAT
VREF
EN DGND
DIGITAL CORE LDO
OUT
PG
VBAT
VREF
EN
OUT
AGND
ANALOG LDO
TCXO LDO
VBAT
VREF
EN
OUT
AGND
MEMORY LDO
VBAT
VREF
EN
OUT
DGND
RTC LDO
VBAT
VREF
EN
OUT
DGND
EN
REF
BUFFER
1.21V
AGND
110k
QS
R
1M
Figure 1.
Functional Block Diagram
REV. 0–12–
ADP3522
SIMEN
VRTCIN
VRTC
BATSNS
MVBAT
CHRDET
CHRIN
SIMVSEL
NC
VAN
VBAT
VCORE
VMEM
VBAT2
VSIM
NC
NC
ROWX
PWRONKEY
PWRONIN
TCXOEN
AGND
REFOUT
VTCXO
GATEDR
GATEIN
DGND
ISENSE
EOC
CHGEN
RESCAP
RESET
PWRON
POWERKEY
SIMEN
VRTC
CHRIN
MVBAT
CHRDET
SIMSEL
CLKON
REFOUT
VTCXO
VAN
VCORE
RESET
VMEM
VSIM
CHGEN
EOC
C3
10F
C4
0.1F
C5
2.2F
C6
2.2F
C7
2.2F
C10
2.2F
C8
0.1F
C9
0.22F
R8
10
Li OR NiMH
BATTERY
D1
BAT1000
Q1
SI3441
R1
0.25
COIN CELL C1
0.1F
C2
1nF
ADP3522
ROWX
GATEIN
Figure 2.
Typical Application Circuit
THEORY OF OPERATION
The ADP3522 is a power management chip optimized for use
with GSM baseband chipsets in handset applications. Figure 1
shows a block diagram of the ADP3522. The ADP3522 con-
tains several blocks, such as:
Six low dropout regulators (SIM, core, analog, crystal
oscillator, memory, real-time clock)
Reset generator
Buffered precision reference
Lithium ion charge controller and processor interface
Power on/off logic
Undervoltage lockout
Deep discharge lockout
These functions have traditionally been done either as a discrete
implementation or as a custom ASIC design. The ADP3522
combines the benefits of both worlds by providing an integrated
standard product where every block is optimized to operate in a
GSM environment while maintaining a cost competitive solution.
Figure 2 shows the external circuitry associated with the
ADP3522. Only a minimal number of support components
are required.
Input Voltage
The input voltage range of the ADP3522 is 3 V to 5.5 V and is
optimized for a single Li-Ion cell or three NiMH cells. The type
of battery, the SIM LDO output voltage, and the memory LDO
output voltage will all affect the amount of power that the
ADP3522 needs to dissipate. The thermal impedance of the
CSP package is 32°C/W for a JEDEC standard 4-layer board.
The end of charge voltage for high capacity NiMH cells can be as
high as 5.5 V. This results in a worst-case power dissipation for
the ADP3522-1.8 to be as high as 1.6 W for NiMH cells. The
power dissipation for the ADP3522-3 is slightly lower at 1.45 W.
A fully charged Li-Ion battery is 4.25 V, where the ADP3522-3
can dissipate a maximum power of 0.85 W. However, the
ADP3522-1.8 can have a maximum dissipation of 1.0 W.
High battery voltages normally occur when the battery is being
charged and the handset is not in conversation mode. In this
mode, there is a relatively light load on the LDOs. The worst-
case power dissipation should be calculated based on the actual
load currents and voltages used.
Figure 3 shows the maximum power dissipation as a function of
the input voltage. Figure 4 shows the maximum allowable
power dissipation as a function of the ambient temperature.
Low Dropout Regulators (LDOs)
The ADP3522 high performance LDOs are optimized for their
given functions by balancing quiescent current, dropout voltage,
regulation, ripple rejection, and output noise. 2.2 µF tantalum
or MLCC ceramic capacitors are recommended for use with the
core, memory, SIM, and analog LDOs. A 0.22 µF capacitor is
recommended for the TCXO LDO.
REV. 0
ADP3522
–13–
Digital Core LDO (VCORE)
The digital core LDO supplies the baseband circuitry in the
handset (baseband processor and baseband converter). The
LDO has been optimized for very low quiescent current at light
loads as this LDO is on whenever the handset is switched on.
Memory LDO (VMEM)
The memory LDO supplies the system memory as well as the
subsystems of the baseband processor including memory IO,
display, and melody interfaces. It is capable of delivering up to
150 mA of current and is available for either 1.8 V or 3 V based
systems. The LDO has also been optimized for low quiescent
current and will power up at the same time as the core LDO.
Analog LDO (VAN)
This LDO has the same features as the core LDO. It has fur-
thermore been optimized for good low frequency ripple
rejection for use with the baseband converter sections in order
to reject the ripple coming from the RF power amplifier. VAN is
rated to 180 mA, which is sufficient to supply the analog section
of the baseband converter, such as the AD6521, as well as the
microphone and speaker.
TCXO LDO (VTCXO)
The TCXO LDO is intended as a supply for a temperature
compensated crystal oscillator, which needs its own ultralow
noise supply. VTCXO is rated for 20 mA of output current and
is turned on along with the analog LDO when TCXOEN is
asserted. Note that the ADP3522 has been optimized for use
with the AD6534 (Othello One™).
RTC LDO (VRTC)
The RTC LDO is capable of charging rechargeable Lithium or
capacitor-type backup coin cells to run the real-time clock mod-
ule. The RTC LDO supplies current both for charging the coin
cell and for the RTC module. In addition, it features a very low
quiescent current since this LDO is running all the time, even
when the handset is switched off. It also has reverse current
protection with low leakage, which is needed when the main
battery is removed and the coin cell supplies the RTC module.
SIM LDO (VSIM)
The SIM LDO generates the voltage needed for 1.8 V or 3 V
SIMs. It is rated for 20 mA of supply current and can be con-
trolled completely independently of the other LDOs.
Applying a low to SIMEN shuts down the SIM LDO. A dis-
charge circuit is active when SIMEN is low. This pulls the SIM
LDO’s output down when the LDO is disabled.
SIMVSEL allows the SIM LDO to be programmed for either
1.8 V or 2.8 V. Asserting a high on SIMVSEL sets the output
for 2.8 V.
SIMEN and SIMVSEL allow the baseband processor to prop-
erly sequence the SIM supply when determining which type of
SIM module is present.
Reference Output (REFOUT)
The reference output is a low noise, high precision reference
with
a guaranteed accuracy of 1.5% overtemperature. The
maximum
output current of the REFOUT supply is limited to 50 µA.
Power ON/OFF
The ADP3522 handles all issues regarding the powering ON
and OFF of the handset. It is possible to turn on the ADP3522
in three different ways:
Pulling the PWRONKEY low
Pulling the PWRONIN high
CHRIN exceeds CHRDET threshold
Pulling the PWRONKEY low is the normal way of turning on the
handset. This will turn on all the LDOs, except the SIM LDO, as
long as the PWRONKEY is held low. When the VCORE LDO
comes into regulation, the RESET timer is started. After timing
out, the RESET pin goes high, allowing the baseband processor to
start up. With the baseband processor running, it can poll the
ROWX pin of the ADP3522 to determine if the PWRONKEY has
been depressed and pull PWRONIN high. Once the PWRONIN is
taken high, the PWRONKEY can be released. Note that by moni-
toring the ROWX pin, the baseband processor can detect a second
PWRONKEY and press and turn the LDOs off in an orderly manner.
In this way, the PWRONKEY can be used for ON/OFF control.
Pulling the PWRONIN pin high is how the alarm in the real-
time clock module will turn the handset on. Asserting
PWRONIN will turn the core and memory LDOs on, starting
up the baseband processor.
1.6
3.5 4.0
1.2
1.8
4.5 5.03.0
POWER DISSIPATION – W
1.4
0.8
0.4
1.0
0.6
5.5 6.0
0.2
0
INPUT VOLTAGE – V
ADP3522-1.8
ADP3522-2.8
Figure 3.
Power Dissipation vs. Input Voltage
1.6
020
1.2
1.8
40 60–20
POWER DISSIPATION – W
1.4
0.8
0.4
1.0
0.6
80
0.2
0
AMBIENT TEMPERATURE – C
LFCSP
32C/W
Figure 4.
Allowable Package Power Dissipation
vs. Temperature
REV. 0–14–
ADP3522
NO
NO
NO
YES
VBAT > UVLO
NiMH
CHGEN = LOW
NO
VBAT > 4.2V
YES
BATTERY TYPE
CONSTANT VOLTAGE
MODE
YES
YES
EOC = HIGH
NO
CHGEN = HIGH
VBAT > 5.5V
NO
YES
VBAT > 5.5V
YES
NO
YES
YES
NONCHARGING
MODE
CHARGER DETECTED
CHRIN > BATSNS
LOW CURRENT
CHARGE MODE
V
SENSE
= 20mV
HIGH CURRENT
CHARGE MODE
V
SENSE
= 160mV
END OF CHARGE
V
SENSE
< 14mV
TERMINATE CHARGE
CHGEN = HIGH
GATEIN = HIGH
NiMH
CHARGING MODE
GATEIN = PULSED
NiMH
CHARGER OFF
GATEIN = HIGH
NO
Li+
YES
Figure 5.
Battery Charger Flow Chart
REV. 0
ADP3522
–15–
Applying an external charger can also turn the handset on. This
will turn on all the LDOs, except the SIM LDO, again starting
up the baseband processor. Note that if the battery voltage is
below the undervoltage lockout threshold, applying the adapter
will not start up the LDOs.
Deep Discharge Lockout (DDLO)
The DDLO block in the ADP3522 shuts down the handset in
the event that the software fails to turn off the phone when the
battery voltage drops below 2.9 V to 3.0 V. The DDLO will
shut down the handset when the battery falls below 2.4 V to
prevent further discharge and damage to the battery.
The DDLO will also shut down the RTC LDO when the main
battery is removed. This will prevent reverse current from dis-
charging the backup coin cell.
Undervoltage Lockout (UVLO)
The UVLO function in the ADP3522 prevents startup when the
initial voltage of the battery is below the 3.2 V threshold. If the
battery voltage is this low with no load, there is insufficient
capacity left to run the handset. When the battery is greater
than 3.2 V, such as inserting a fresh battery, the UVLO com-
parator trips, and the threshold is reduced to 3.0 V. This allows
the handset to start normally until the battery decays to below 3.0 V.
Once the system is started and the core and memory LDOs are
up and running, the UVLO function is entirely disabled. The
ADP3522 is then allowed to run until the battery voltage
reaches the DDLO threshold, typically 2.4 V. Normally, the
battery voltage is monitored by the baseband processor, which
usually shuts the phone off at a battery voltage of around 3.0 V.
If the handset is off and the battery voltage drops below 3.0 V,
the UVLO circuit disables startup and puts the ADP3522 into
UVLO shutdown mode. In this mode, the ADP3522 draws very
low quiescent current, typically 30 µA. In DDLO mode, the
ADP3522 draws 15 µA of quiescent current. NiMH batteries can
reverse polarity if the 3-cell battery voltage drops below 3.0 V,
which will degrade the batteries’ performance. Lithium ion bat-
teries will lose their capacity if overdischarged repeatedly, so
minimizing the quiescent currents helps prevent battery damage.
RESET
The ADP3522 contains a reset circuit that is active both at
power-up and power-down. The RESET pin is held low at
initial power-up. An internal power good signal is generated by
the core LDO when its output is up, starting the reset delay
timer. The delay is set by an external capacitor on RESCAP:
tms
nF C
RESET RESCAP
12.(1)
At power-off, RESET will be kept low to prevent any baseband
processor starts.
Overtemperature Protection
The maximum die temperature for the ADP3522 is 125°C. If
the die temperature exceeds 160°C, the ADP3522 will disable
all the LDOs except the RTC LDO. The LDOs will not be
re-enabled before the die temperature is below 125°C, regard-
less of the state of PWRONKEY, PWRONIN, and CHRDET.
This ensures that the handset will always power off before the
ADP3522 exceeds its absolute maximum thermal ratings.
Battery Charging
The ADP3522 battery charger can be used with lithium ion
(Li+) and nickel metal hydride (NiMH) batteries. The charger
initialization, trickle charging, and Li+ charging are imple-
mented in hardware. Battery type determination and NiMH
charging must be implemented in software.
The charger block works in three different modes:
1. Low current (trickle) charging
2. Lithium ion charging
3. Nickel metal hydride charging
See Figure 5 for the charger flow chart.
Charge Detection
The ADP3522 charger block has a detection circuit that deter-
mines if an adapter has been applied to the CHRIN pin. If the
adapter voltage exceeds the battery voltage by 100 mV, the
CHRDET output will go high. If the adapter is then removed
and the voltage at the CHRIN pin drops to only 50 mV above
the BATSNS pin, CHRDET goes low. The CHRDET signal is
not asserted if the battery voltage is below the UVLO threshold.
Trickle Charging
When the battery voltage is below the UVLO threshold, the
charge current is set to the low current limit, or about 10% of
the full charge current. The low current limit is determined by
the voltage developed across the current sense resistor. There-
fore, the trickle charge current can be calculated by
ImV
R
CHR TRICKLE
SENSE
()
=20
(2)
Trickle charging is performed for deeply discharged batteries to
prevent undue stress on either the battery or the charger.
Trickle charging will continue until the battery voltage exceeds
the UVLO threshold.
Once the UVLO threshold has been exceeded, the charger will
switch to the default charge mode, the LDOs will start up, and
the baseband processor will start to run. The processor must
then poll the battery to determine which chemistry is present
and set the charger to the proper mode. Control of the charge
mode, Li+ or NiMH, is determined by the CHGEN input.
REV. 0–16–
ADP3522
HIGH CURRENT
3.2V
LOW CURRENT
4.2V
EOC CURRENT
EOC
INDICATOR
I
CHARGE
0
V
BAT
Figure 6. Lithium Ion Charging Diagram
Lithium Ion Charging
For lithium ion charging, the CHGEN input must be low. This
allows the ADP3522 to continue charging the battery at the full
current. The full charge current can be calculated by using
ImV
R
CHR FULL
SENSE
()
=160
(3)
If the voltage at BATSNS is below the charger’s output voltage
of 4.2 V, the battery will continue to charge in the constant
current mode. If the battery has reached the final charge volt-
age, a constant voltage is applied to the battery until the charge
current has reduced to the charge termination threshold. The
charge termination threshold is determined by the voltage across
the sense resistor. If the battery voltage is above 4.0 V and the
voltage across the sense resistor has dropped to 14 mV, then an
end of charge signal is generated—the EOC output goes high
(see Figure 6).
The baseband processor can either let the charger continue to
charge the battery for an additional amount of time or terminate
the charging. To terminate the charging, the processor must
pull the GATEIN pin high and the CHGEN pin high.
NiMH Charging
For NiMH charging, the processor must pull the CHGEN pin
high. This disables the internal Li+ mode control of the gate
drive pin. The gate drive must now be controlled by the
baseband processor. By pulling GATEIN high, the GATEDR
pin is driven high, turning the PMOS off. By pulling the
GATEIN pin low, the GATEDR pin is driven low, and the
PMOS is turned on. So, by pulsing the GATEIN input, the
processor can charge a NiMH battery. Note that when charging
NiMH cells, a current limited adapter is required.
During the PMOS off periods, the battery voltage needs to be
monitored through the MVBAT pin. The battery voltage is con-
tinually polled until the final battery voltage is reached. Then the
charge can either be terminated or the frequency of the pulsing
reduced. An alternative method of determining the end of charge
is to monitor the temperature of the cells and terminate the
charging when a rapid rise in temperature is detected.
Battery Voltage Monitoring
The battery voltage can be monitored at MVBAT during charg-
ing and discharging to determine the condition of the battery. An
internal resistor divider can be connected to BATSNS when both
the digital and analog baseband sections are powered up. To
enable MVBAT, both PWRONIN and TCXOEN must be high.
The ratio of the voltage divider is selected so that the 2.4 V
maximum input of the AD6521’s auxiliary ADC will corre-
spond with the maximum battery voltage of 5.5 V. The divider
will be disconnected from the battery when the baseband sec-
tions are powered down.
APPLICATION INFORMATION
Input Capacitor Selection
For the input (VBAT, VBAT2, and VRTCIN) of the
ADP3522, a
local bypass capacitor is recommended; use a 10 µF, low ESR
capacitor. Multilayer ceramic chip (MLCC) capacitors provide
the best combination of low ESR and small size but may not be
cost effective. A lower cost alternative may be to use a 10 µF
tantalum capacitor with a small (1 µF to 2 µF) ceramic in parallel.
Separate inputs for the SIM LDO and the RTC LDO are sup-
plied for additional bypassing or filtering. The SIM LDO has
VBAT2 as its input and the RTC LDO has VRTCIN.
LDO Capacitor Selection
The performance of any LDO is a function of the output capacitor.
The core, memory, SIM, and analog LDOs require a 2.2 µF
capacitor and the TCXO LDO requires a 0.22 µF capacitor.
Larger values may be used, but the overshoot at startup will
increase slightly. If a larger output capacitor is desired, be
sure to check that the overshoot and settling time are accept-
able for the application.
All the LDOs are stable with a wide range of capacitor types and
ESR (anyCAP
®
technology). The ADP3522 is stable with
extremely low ESR capacitors (ESR ~ 0) such as multilayer
ceramic capacitors (MLCC), but care should be taken in their
selection. Note that the capacitance of some capacitor types
shows wide variations over temperature or with dc voltage. A
good quality dielectric, X7R or better, capacitor is recommended.
The RTC LDO can have a rechargeable coin cell or an electric
double-layer capacitor as a load, but an additional 0.1 µF ceramic
capacitor is recommended for stability and best performance.
REV. 0
ADP3522
–17–
1.75
20 40
1.25
2.00
60 800
1.50
0.75
0.25
1.00
0.50
0
100 120
VBAT – V
TIME – Minutes
CHARGE CHARACTERISTIC
Figure 7.
Kanebo PAS621 Charge Characteristic
1.75
20 40
1.25
2.00
60 800
1.50
0.75
0.25
1.00
0.50
0
100 120
VBAT – V
TIME – Minutes
CHARGER CHARACTERISTIC
Figure 8.
Panasonic EECEM0E204A Charge Characteristic
1.9
510
1.7
2.0
15 200
TIME – Hours
VBAT – V
1.8
1.5
1.3
1.6
1.4
0.9
25 30
1.2
1.0
1.1
CHARGE CHARACTERISTIC
Figure 9.
Maxell TC614 Charge Characteristic
1.9
510
1.7
2.0
15 200
TIME – Hours
VBAT – V
1.8
1.5
1.3
1.6
1.4
0.9
25 30
1.2
1.0
1.1
35 40
CHARGER CHARACTERISTIC
Figure 10.
Seiko TS621 Charge Characteristic
RTC Backup Coin Cell Selection
The choice of the backup cell is based upon size, cost, and
capacity. It must be able to support the RTC module’s current
requirement and voltage range, as well as handle the charge
current supplied by the ADP3522 (see TPC 2). Check with the
coin cell vendor if the ADP3522’s charge current profile is
acceptable.
Some suitable coin cells are the electric double layer capacitors
available from Kanebo (PAS621), Seiko (XC621), or Panasonic
(EECEM0E204A). They have a small physical size (6.8 mm
diameter) and a nominal capacity of 0.2 F to 0.3 F, giving hours
of backup time. Rechargeable lithium coin cells, such as the
TC614 from Maxell or the TS621 from Seiko, are also small in
size but have higher capacity than the double layer capacitors,
resulting in longer backup times. Typical charge curves for each
cell type are shown in Figures 7 through 10. Note that the
rechargeable lithium type coin cells generally come precharged
from the vendor.
RESET Capacitor Selection
RESET is held low at power up. An internal power-good signal
starts the reset delay when the core LDO is up. The delay is set
by an external capacitor on RESCAP:
tms
nF C
RESET RESCAP
12.
(4)
A 100 nF capacitor will produce a 120 ms reset delay. The
current capability of RESET is minimal (a few hundred nA)
when VCORE is off to minimize power consumption. When
VCORE is on, RESET is capable of driving 500 µA.
Setting the Charge Current
The ADP3522 is capable of charging both lithium ion and
NiMH batteries. For NiMH batteries, the charge current is
limited by the adapter. For lithium ion batteries, the charge
REV. 0–18–
ADP3522
current is programmed by selecting the sense resistor, R1 (see
Figure 2).
The lithium ion charge current is calculated using
IV
R
mV
R
CHR
SENSE
==
1
160
1
(5)
where V
SENSE
is the high current limit threshold voltage. Or if
the charge current is known, R1 can be found:
RV
I
mV
I
SENSE
CHR CHR
1160
==
(6)
Similarly the trickle charge current and the end of charge cur-
rent can be calculated:
IV
R
mV
R
TRICKLE
SENSE
==
1
20
1
(7)
IV
R
mV
R
EOC
SENSE
==
1
14
1
(8)
Example: Assume an 800 mA-H capacity lithium ion battery
and a 1 C charge rate. R1 = 200 m. Then I
TRICKLE
= 100 mA
and I
EOC
= 70 mA.
Appropriate sense resistors are available from the following
vendors:
Vishay Dale
IRC
Panasonic
Charger FET Selection
The type and size of the pass transistor is determined by the
threshold voltage, input-output voltage differential, and charge
current. The selected PMOS must satisfy the physical, electri-
cal, and thermal design requirements.
To ensure proper operation, the minimum VGS the ADP3522
can provide must be enough to turn on the FET. The available
gate drive voltage can be estimated using the following:
VV V V
GS ADAPTER MIN GATEDR SENSE
=--
()
(9)
where
V
ADAPTER(MIN)
is the minimum adapter voltage.
V
GATEDR
is the gate drive “low” voltage, 0.5 V.
V
SENSE
is the maximum high current limit threshold voltage.
The difference between the adapter voltage (V
ADAPTER
) and the
final battery voltage (V
BAT
) must exceed the voltage drop due to
the blocking diode, the sense resistor, and the on resistance of
the FET at maximum charge current.
VV V V V
DS ADAPTER DIODE SENSE BAT
=---
(10)
Then the R
DS(ON)
of the FET can be calculated:
RV
I
DS ON
DS
CHR MAX
()
()
=
(11)
The thermal characteristics of the FET must be considered
next. The worst-case dissipation can be determined using:
PV V V
UVLO I
DISS ADAPTER MAX DIODE SENSE
CHR
=−
−×
()
(12)
It should be noted that the adapter voltage can be either
preregulated or nonregulated. In the preregulated case, the
difference between the maximum and minimum adapter voltage
is probably not significant. In the unregulated case, the adapter
voltage can have a wide range specified. However, the maxi-
mum voltage specified is usually with no load applied. So, the
worst-case power dissipation calculation will often lead to an
overspecified pass device. In either case, it is best to determine
the load characteristics of the adapter to optimize the charger
design.
For example:
V
ADAPTER(MIN)
= 5.0 V
V
ADAPTER(MAX)
= 6.5 V
V
DIODE
= 0.5 V at 800 mA
V
GATEDR
= 0.5 V
V
SENSE
= 160 mV
V
GS
= 5 V – 0.5 V – 0.160 V = 4.3 V. So choose a low
threshold voltage FET.
VV V V V
VVV VV mV
DS ADAPTER MIN DIODE SENSE BAT
DS
=---
=- - - =
()
.. .505016042 140
(13)
RV
I
mV
mA m
DS ON
DS
CHR MAX
()
()
===
140
800 175
(14)
PV V V
UVLO I
PVVVV
AW
DISS ADAPTER MAX DIODE SENSE
CHR
DISS
=−
−×
=−
×=
(
)
(... .)
..
()
65 05 0160 32
08 21
(15)
Appropriate PMOS FETs are available from the following vendors:
Siliconix
IR
Fairchild
Charger Diode Selection
The diode, D1, shown in Figure 2 is used to prevent the battery
from discharging through the PMOS’ body diode into the
charger’s internal bias circuits. A Schottky diode is recom-
mended to minimize the voltage difference from the charger to
the battery and the power dissipation. Choose a diode with a
current rating high enough to handle the battery charging cur-
rent and a voltage rating greater than VBAT. The blocking
diode is required for both lithium and nickel battery types.
REV. 0
ADP3522
–19–
Printed Circuit Board Layout Considerations
Use the following general guidelines when designing printed
circuit boards:
1. Connect the battery to the VBAT, VBAT2, and VRTCIN
pins of the ADP3522. Locate the input capacitor as close to
the pins as possible.
2. VAN and VTCXO output capacitors should be returned to
AGND.
3. VCORE, VMEM, and VSIM output capacitors should be
returned to DGND.
4. Split the ground connections. Use separate traces or planes
for the analog, digital, and power grounds and tie them to-
gether at a single point, preferably close to the battery return.
5. Run a separate trace from the BATSNS pin to the battery to
prevent voltage drop error in the MVBAT measurement.
6.
Kelvin connect the charger’s sense resistor by running
separate traces to the CHRIN pin and ISENSE pin. Make
sure the traces are terminated as close to the resistor’s
body as possible.
7. Use the best industry practice for thermal considerations
during the layout of the ADP3522 and charger components.
Careful use of copper area, weight, and multilayer construc-
tion all contribute to improved thermal performance.
LFCSP Layout Considerations
The CSP package has an exposed die paddle on the bottom that
efficiently conducts heat to the PCB. In order to achieve the
optimum performance from the CSP package, special consider-
ation must be given to the layout of the PCB. Use the following
layout guidelines for the CSP package:
1. The pad pattern is given in Figure 11. The pad dimension
should be followed closely for reliable solder joints while
maintaining reasonable clearances to prevent solder bridging.
2. The thermal pad of the CSP package provides a low thermal
impedance path (approximately 15°C/W) to the PCB.
Therefore, the PCB must be properly designed to effectively
conduct the heat away from the package. This is achieved by
adding thermal vias to the PCB, which provide a thermal
path to the inner or bottom layers. See Figure 12 for the
recommended via pattern. Note that the via diameter is
small. This is to prevent the solder from flowing through the
via and leaving voids in the thermal pad solder joint.
Note that the thermal pad is attached to the die substrate;
the thermal planes that the vias attach the package to must
be electrically isolated or connected to VBAT. Do NOT
connect the thermal pad to ground.
3. The solder mask opening should be about 120 microns (4.7 mils)
larger than the pad size resulting in a minimum 60 microns
(2.4 mils) clearance between the pad and the solder mask.
4. The paste mask opening is typically designed to match the
pad size used on the peripheral pads of the LFCSP package.
This should provide a reliable solder joint as long as the
stencil thickness is about 0.125 mm.
The paste mask for the thermal pad needs to be designed for
the maximum coverage to effectively remove the heat from
the package. However, due to the presence of thermal vias
and the large size of the thermal pad, eliminating voids may
not be possible. Also, if the solder paste coverage is too large,
solder joint defects may occur. Therefore, it is recommended
to use multiple small openings over a single big opening in
designing the paste mask. The recommended paste mask
pattern is given in Figure 13. This pattern will result in about
80% coverage, which should not degrade the thermal perfor-
mance of the package significantly.
5. The recommended paste mask stencil thickness is 0.125 mm.
A laser cut stainless steel stencil with trapezoidal walls should
be used.
A “No Clean,” Type 3 solder paste should be used for
mounting the LFCSP package. Also, a nitrogen purge during
the reflow process is recommended.
6. The package manufacturer recommends that the reflow
temperature should not exceed 220°C and the time above
liquids is less than 75 seconds. The preheat ramp should be
3°C/second or lower. The actual temperature profile depends
on the board’s density and must be determined by the assembly
house as to what works best.
REV. 0
C03535–0–2/03(0)
PRINTED IN U.S.A.
–20–
ADP3522
OUTLINE DIMENSIONS
32-Lead Frame Chip Scale Package [LFCSP]
5 mm 5 mm Body
Dimensions shown in millimeters
COMPLIANT TO JEDEC STANDARDS MO-220-VHHD-2
0.30
0.23
0.18
12MAX
0.20 REF
0.05 MAX
0.02 NOM
COPLANARITY
0.08
1.00 MAX
0.65 NOM
1.00
0.90
0.80
1
32
8
9
25
24
16
17
BOTTOM
VIEW
0.50
0.40
0.30
3.50
REF
0.50
BSC
PIN 1
INDICATOR
TOP
VIEW
5.00
BSC SQ
4.75
BSC SQ SQ
3.25
3.10
2.95
PIN 1
INDICATOR
0.60 MAX
0.60 MAX
SEATING
PLANE
5.36
3.96 3.56
3.80
0.08
0.50 0.20
0.70
0.30
Dimensions shown in millimeters
Figure 11.
5 mm
5 mm LFCSP Pad Pattern
0.60
1.18
1.18
0.60
ARRAY OF 9 VIAS
0.25mm DIAMETER
0.35m PLATING
THERMAL PAD AREA
Dimensions shown in millimeters
Figure 12. 5 mm
5 mm LFSCP Via Pattern
CREATE SOLDER PASTE
WEB FOR APPROX 80%
COVERAGE 125 MICRONS
WIDE TO SEPARATE
SOLDER PASTE AREA
THERMAL PAD AREA
Figure 13. 5 mm
5 mm LFSCP Solder Paste Mask Pattern