ISL8843AMBEPZ - Intersil Corporation

FN6792.1

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ,

ISL8843AMZ, ISL8844AMZ, ISL8845AMZ

High Performance Industry S tandard

Single-Ended Current Mode PWM

Controller

The ISL884xAMBEPZ is a high performance drop-in

replacement for the popular 28C4x and 18C4x PWM

controllers suitable for a wide range of power conversion

applications including boost, flyback, and isolated output

configurations. Its fast signal propagation and output

switching characteristics make this an ideal product for

existing and new designs.

Features include 30V operation, low operating current, 90µA

start-up current, adjustable operating frequency to 2MHz,

and high peak current drive capability with 20ns rise and fall

times.

Pinout ISL884XAMBEPZ

(8 LD SOIC)

TOP VIEW

Features

• Full Mil-Temp Electrical Performance from -55°C to +125°C

• Controlled Baseline with One W afer Fabrication Site and

One Assembly/Test Site

• Full Homogenous Lot Processing in Wafer Fab

• No Combination of Wafer Fabrication Lots in Assembly

• Full Traceability Through Assembly and Test by

Date/Trace Code Assignment

• Enhanced Process Change Notification

• Enhanced Obsolescence Management

• Eliminates Need for Up-Screening a COTS Component

• 1A MOSFET Gate Driver

• 90µA Start-up Current, 125µA Maximum

• 35ns Propagation Delay Current Sense to Output

• Fast Transient Response with Peak Current Mode Control

• 30V Operation

• Adjustable Switching Frequency to 2MHz

• 20ns Rise and Fall Times with 1nF Output Load

• T rimmed T iming Capacitor Discharge Current for Accurate

Deadtime/Maximum Duty Cycle Control

• 1.5MHz Bandwidth Error Amplifier

• Tight Tolerance Voltage Reference Over Line, Load and

Temperature

• ±3% Current Limit Threshold

• Pb-Free (RoHS compliant)

Applications

• Isolated Flyback and Forward Regulators

• Boost Regulators

PART NUMBER RISING UVLO

(V) MAX. DUTY CYCLE

(%)

ISL8840AMBEPZ 7.0 100

ISL8841AMBEPZ 7.0 50

ISL8842AMBEPZ 14.4 100

ISL8843AMBEPZ 8.4 100

ISL8844AMBEPZ 14.4 50

ISL8845AMBEPZ 8.4 50

COMP

RTCT

VREF

VDD

OUT

GND

Data Sheet December 1, 2011

CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.

1-888-INTERSIL or 1-888-468-3774 |Intersil (and design) is a registered trademark of Intersil Americas Inc.

All other trademarks mentioned are the property of their respective owners.

2FN6792.1

December 1, 2011

Ordering Information

PART NUMBER

(Notes 1, 2) PART

MARKING TEMP RANGE

(°C) PACKAGE

(Pb-Free) PKG.

DWG. #

ISL8840AMBEPZ 8840A MBEPZ -55 to +125 8 Ld SOIC M8.15

ISL8841AMBEPZ 8841A MBEPZ -55 to +125 8 Ld SOIC M8.15

ISL8842AMBEPZ 8842A MBEPZ -55 to +125 8 Ld SOIC M8.15

ISL8843AMBEPZ 8843A MBEPZ -55 to +125 8 Ld SOIC M8.15

ISL8844AMBEPZ 8844A MBEPZ -55 to +125 8 Ld SOIC M8.15

ISL8845AMBEPZ 8845A MBEPZ -55 to +125 8 Ld SOIC M8.15

NOTES:

1. Add “-TK” suffix for tape and reel. Please refer to TB347 for details on reel specifications.

2. These Intersil Pb-free plastic packaged products employ special Pb-free material sets, molding compounds/die attach materials, and 100% matte

tin plate plus anneal (e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations). Intersil

Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-

020.

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

3FN6792.1

December 1, 2011

Functional Block Diagram

150k

100k

VDD

OUT

RTCT

GND

VREF

PWM

COMPARATOR

RESET

DOMINANT

2.5V

ENABLE

8.4mA

2.9V

1.0V

OSCILLATOR

COMPARATOR

<10ns

START/STOP

UV COMPARATOR

VREF

5.00V

100mV

ERROR

AMPLIFIER

VREF

COMP

VREF

UV COMPARATOR

4.65V 4.80V

A = 0.5

CLOCK

1.1V

CLAMP

VF TOTAL = 1.15V

VREF FAULT

OKVDD

36k

ISL8841AMBEPZ/

ONLY

ISL8844AMBEPZ/

ISL8845AMBEPZ

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845AMZ

4FN6792.1

December 1, 2011

Absolute Maximum Ratings Thermal Information

Supply Voltage, VDD . . . . . . . . . . . . . . . . . . . . . GND -0.3V to +30V

OUT . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND -0.3V to VDD + 0.3V

Signal Pins . . . . . . . . . . . . . . . . . . . . . . . . . . . . .GND -0.3V to 6.0V

Peak GATE Current. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .1A

Thermal Resistance (Note 4) θJA (°C/W)

SOIC Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 100

Maximum Junction Temperature . . . . . . . . . . . . . . . . . . . . . .+150°C

Maximum Storage Temperature Range. . . . . . . . . .-65°C to +150°C

Pb-Free Reflow Profile. . . . . . . . . . . . . . . . . . . . . . . . .see link below

http://www.intersil.com/pbfree/Pb-FreeReflow.asp

Operating Conditions

Supply Voltage Range (Note 3). . . . . . . . . . . . . . . . . . . . . 9V to 30V

Temperature Range. . . . . . . . . . . . . . . . . . . . . . . . .-55°C to +125°C

CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and

result in failures not covered by warranty.

NOTES:

3. All voltages are with respect to GND.

4. θJA is measured with the component mounted on a high effective thermal conductivity test board in free air . See Technical Brief TB379 for details.

Electrical Specifications Recommended operating conditions unless otherwise noted. Refer to “Functional Block Diagram” on page 3.

VDD = 15V, Rt = 10kΩ, Ct = 3.3nF, TA = -55 to +125°C, Typical values are at TA= +25°C. Parameters with MIN

and/or MAX limits are 100% tested at +25°C, unless otherwise specified. Temperature limits established by

characterization and are not production tested

PARAMETER TEST CONDITIONS MIN TYP MAX UNITS

UNDERVOLTAGE LOCKOUT

START Threshold (ISL8840AMBEPZ,

ISL8841AMBEPZ) 6.5 7.0 7.5 V

START Threshold (ISL8843AMBEPZ,

ISL8845AMBEPZ) 8.0 8.4 9.0 V

START Threshold (ISL8842AMBEPZ,

ISL8844AMBEPZ) (Note 7) 13.3 14.3 15.3 V

STOP Threshold (ISL8840AMBEPZ,

ISL8841AMBEPZ) 6.1 6.6 6.9 V

STOP Threshold (ISL8843AMBEPZ,

ISL8845AMBEPZ) 7.3 7.6 8.0 V

STOP Threshold (ISL8842AMBEPZ,

ISL8844AMBEPZ) 8.0 8.8 9.6 V

Hysteresis (ISL8840AMBEPZ, ISL8841AMBEPZ) - 0.4 - V

Hysteresis (ISL8843AMBEPZ, ISL8845AMBEPZ) - 0.8 - V

Hysteresis (ISL8842AMBEPZ, ISL8844AMBEPZ) - 5.4 - V

Start-up Current, IDD VDD < START Threshold - 90 125 µA

Operating Current, IDD (Note 5) - 2.9 4.0 mA

Operating Supply Current, IDIncludes 1nF GATE loading - 4.75 5.5 mA

REFERENCE VOLTAGE

Overall Accuracy Over line (VDD = 12V to 30V), load,

temperature 4.900 5.000 5.050 V

Long Term Stability TA = +125°C, 1000 hours (Note 6) - 5 - mV

Current Limit, Sourcing -20 - - mA

Current Limit, Sinking 5--mA

CURRENT SENSE

Input Bias Current VCS = 1V -1.0 - 1.0 µA

CS Offset Voltage VCS = 0V (Note 6) 95 100 105 mV

COMP to PWM Comparator Offset Voltage VCS = 0V (Note 6) 0.80 1.15 1.30 V

Input Signal, Maximum 0.97 1.00 1.03 V

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

5FN6792.1

December 1, 2011

Gain, ACS = ΔVCOMP/ΔVCS 0 < VCS < 910mV, VFB = 0V 2.5 3.0 3.5 V/V

CS to OUT Delay -3560ns

ERROR AMPLIFIER

Open Loop Voltage Gain (Note 6) 60 90 - dB

Unity Gain Bandwidth (Note 6) 1.0 1.5 - MHz

Reference Voltage VFB = VCOMP 2.460 2.500 2.535 V

FB Input Bias Current VFB = 0V -1.0 -0.2 1.0 µA

COMP Sink Current VCOMP = 1.5V, VFB = 2.7V 1.0 - - mA

COMP Source Current VCOMP = 1.5V, VFB = 2.3V -0.4 - - mA

COMP VOH VFB = 2.3V 4.80 - VREF V

COMP VOL VFB = 2.7V 0.4 - 1.0 V

PSRR Frequency = 120Hz, VDD = 12V to

30V (Note 6) 60 80 - dB

OSCILLATOR

Frequency Accuracy Initial, TA = +25°C 48 51 53 kHz

Frequency Variation with VDD TA = +25°C, (f30V - f10V)/f30V -0.21.0%

Temperature Stability (Note 6) - - 5 %

Amplitude, Peak-to-Peak Static Test - 1.75 - V

RTCT Discharge Voltage (Valley Voltage) Static Test - 1.0 - V

Discharge Current RTCT = 2.0V 6.2 8.0 8.5 mA

OUTPUT

Gate VOH VDD - OUT, IOUT = -200mA - 1.0 2.0 V

Gate VOL OUT - GND, IOUT = 200mA - 1.0 2.0 V

Peak Output Current COUT = 1nF (Note 6) - 1.0 - A

Rise Time COUT = 1nF (Note 6) - 20 40 ns

Fall Time COUT = 1nF (Note 6) - 20 40 ns

GATE VOL UVLO Clamp Voltage VDD = 5V, ILOAD = 1mA - - 1.2 V

PWM

Maximum Duty Cycle

(ISL8840AMBEPZ, ISL8842AMBEPZ,

ISL8843AMBEPZ)

COMP = VREF 94.0 96.0 - %

Maximum Duty Cycle

(ISL8841AMBEPZ, ISL8844AMBEPZ,

ISL8845AMBEPZ)

COMP = VREF 47.0 48.0 - %

Minimum Duty Cycle COMP = GND - - 0 %

NOTES:

5. This is the VDD current consumed when the device is active but not switching. Do es not include gate drive current.

6. Limits established by characterization and are not production tested.

7. Adjust VDD above the start threshold and then lower to 15V.

Electrical Specifications Recommended operating conditions unless otherwise noted. Refer to “Functional Block Diagram” on page 3.

VDD = 15V, Rt = 10kΩ, Ct = 3.3nF, TA = -55 to +125°C, T ypical values are at T A= +25°C. Parameters with MIN

and/or MAX limits are 100% tested at +25°C, unless otherwise specified. Temperature limits established by

characterization and are not production tested (Continued)

PARAMETER TEST CONDITIONS MIN TYP MAX UNITS

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

6FN6792.1

December 1, 2011

Pin Descriptions

RTCT - This is the oscillator timing control pin. The

operational frequency and maximum duty cycle are set by

connecting a resistor, Rt, between VREF and this pin and a

timing capacitor, Ct, from this pin to GND. The oscillator

produces a sawtooth waveform with a programmable

frequency range up to 2.0MHz. The charge time, tC, the

discharge time, tD, the switching frequency, f, and the

maximum duty cycle, DMAX, can be approximated from the

following equations:

The formulae have increased error at higher frequencies due

to propagation delays. Figure 4 may be used as a guideline

in selecting the capacitor and resistor values required for a

given frequency.

COMP - COMP is the output of the error amplifier and the

input of the PWM comparator. The control loop frequency

compensation network is connected between the COMP and

FB pins.

FB - The output voltage feedback is connected to the

inverting input of th e error amplifier through this pin. The

non-inverting input of the error amplifier is internally tied to a

reference vol tage.

CS - This is the current se nse input t o the PWM comp arat or.

The range of the input signal is nominally 0V to 1.0V and has

an internal offset of 100mV.

GND - GND is the power and small signal reference ground

for all functions.

OUT - This is the drive output to the power switching device.

It is a high current output capable of driving the gate of a

power MOSFET with peak currents of 1.0A. This GATE

output is actively held low when VDD is below the UVLO

threshold.

VDD - VDD is the power connection for the device. The total

supply current will depend on the load applied to OUT. Total

IDD current is the sum of the operating current and the

average output current. Knowing the operating frequency, f,

Typical Performance Curves

FIGURE 1. FREQUENCY vs TEMPERATURE FIGURE 2. REFERENCE VOLTAGE vs TEMPERATURE

FIGURE 3. EA REFERENCE vs TEMPERATURE FIGURE 4. RESISTANCE FOR CT CAPACITOR VALUES GIVEN

-60 -40 -20 0 20 40 60 80 100 120 140

0.98

0.99

1.00

1.01

TEMPERATURE (°C)

NORMALIZED FREQUENCY

-60 -40 -20 0 20 40 60 80 100

0.995

0.996

0.997

0.998

0.999

1.000

1.001

TEMPERATURE (°C)

NORMALIZED VREF

140120

-60 -40 -20 0 20 40 60 80 100 120 140

0.996

0.997

0.998

1.000

1.001

TEMPERATURE (°C)

NORMALIZED EA REFERENCE

110100

100

103

Rt (kΩ)

FREQUENCY (Hz)

100pF

220pF

330pF

470pF

1.0nF

2.2nF

3.3nF

4.7nF

6.8nF

tC0.533 RtCt

⋅⋅≈(EQ. 1)

tDRt

–CtIn 0.008 Rt3.83–⋅

0.008 Rt1.71–⋅

-------------------------------------------⎠

⎟

⎞

⎝

⎜

⎛

⋅⋅≈(EQ. 2)

f1t

CtD

+()⁄=(EQ. 3)

Cf⋅=(EQ. 4)

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

7FN6792.1

December 1, 2011

and the MOSFET gate charge, Qg, the average output

current can be calculated from Equation 5:

To optimize noise immunity, bypass VDD to GND with a

ceramic capacitor as close to the VDD and GND pins as

possible.

VREF - The 5.00V reference voltage output. +1.0/-1.5%

tolerance over line, load and operating temperature. Bypass

to GND with a 0.1µF to 3.3µF capacitor to filter this output as

needed.

Functional Description

Features

The ISL884xAMBEPZ current mode PWM makes an ideal

choice for low-cost flyback and forward topology

applications. With its greatly improved performance over

industry standard parts, it is the obvious choice for new

designs or existing designs which require up dating.

Oscillator

The ISL884xAMBEPZ has a sawtooth oscillator with a

programmable frequency range to 2MHz, wh ich can be

program med wi th a resistor from V REF and a capacitor to

GND on the RTCT pin. (Please refer to Figure 4 for the

resistor and capacitance required for a given frequency.)

Soft-Start Operation

Soft-start must be implemented externally. One method,

illustrated in Figure 5, clamps the voltage on COMP.

The COMP pin is clamped to the voltage on capacitor C1

plus a base-emitter junction by transistor Q1. C1 is charged

from VREF through resistor R1 and the base current of Q1.

At power-up C1 is fully discharged, COMP is at ~0.7V, and

the duty cycle is zero. As C1 charges, the voltage on COMP

increases, and the duty cycle increases in proportion to the

voltage on C1. When COMP reaches the steady state

operating point, the control loop takes over and soft-start is

complete. C1 continues to charge up to VREF and no longer

affects COMP. During power-down, diode D1 quickly

discharges C1 so that the soft-start circuit is properly

initialized prior to the next power-on sequ ence.

Gate Drive

The ISL884xAMBEPZ is capable of sourcing and sinking 1A

peak current. To limit the peak current through the IC, an

optional external resistor may be placed between the

totem-pole output of the IC (OUT pin) and the gate of the

MOSFET. This small series resistor also damps any

oscillations caused by the resonant tank of the parasitic

inductances in the traces of the board and the FET’s input

capacitance.

Slope Compensation

For applications where the maximum duty cycle is less than

50%, slope compensation may be used to improve noise

immunity, particularly at lighter loads. The amount of slope

compensation required for noise immunity is determined

empirically, but is generally about 10% of the full scale

current feedback signal. For applications where the duty

cycle is greater than 50%, slope compensation is required to

prevent instability.

Slope compensation may be accomplished by summing an

external ramp with the current feedback signal or by

subtracting the external ramp from the voltage feedback

error signal. Adding the external ramp to the current

feedback signal is the more popular method.

From the small signal current-mode model [1] it can be

shown that the naturally-sampled modula to r gain, Fm,

without slope compensation, is in Equation 6.

where Sn is the slope of the sawtooth signal and tsw is the

duration of the half-cycle. W hen an external ramp is added,

the modulator gain becomes Equation 7:

where Se is slope of the external ramp and

The criteria for determining the correct amount of external

ramp can be determined by appropria tely setting the

damping factor of the double-pole located at the switching

frequency. The double-pole will be critically damped if the

Q-factor is set to 1, over-damped for Q < 1, and

under-damped for Q > 1. An under-damped condition may

result in current loop instability.

IOUT Qg f×=(EQ. 5)

FIGURE 5. SOFT-START

VREF

COMP

GND

ISL884xAMBEPZ

D1 R1

Fm 1

SntSW

------------------

=(EQ. 6)

Fm 1

SnSe

+()tSW

------------------------------------ 1

mcSntSW

---------------------------

== (EQ. 7)

mc1Se

-------

+= (EQ. 8)

πmc1D–()0.5–()

-------------------------------------------------

=(EQ. 9)

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

8FN6792.1

December 1, 2011

where D is the percent of on-time during a switching cycle.

Setting Q = 1 and solving for Se yields Equation 10:

Since Sn and Se are the on time slopes of the current ramp

and the external ramp, respectively, they can be multiplied

by tON to obtain the voltage change that occurs during tON.

where Vn is the change in the current feedback signal (ΔI)

during the on-time and Ve is the voltage that must be added

by the external ramp.

For a flyback converter, Vn can be solved for in terms of

input voltage, current transducer components, and primary

inductance, yielding

where R CS is the current sense resistor , fSW is the switching

frequency, Lp is the primary inductance, VIN is the minimum

input voltage, and D is the maximum duty cycle.

The current sense signal at the end of the on-time for CCM

operation is:

where VCS is the voltage across the current sense resistor,

Ls is the secondary winding inductance, and IO is the output

current at current limit. Equation 13 assumes the voltage

drop across the output rectifier is negligible.

Since the peak current limit thresho ld is 1.00V, the total

current feedback signal plus the external ramp voltage must

sum to this value when the output load is at the current limit

threshold.

Substituting Equations 12 and 13 into Equation 14 an d

solving for RCS yields Equation 15:

Adding slope compensation is accomplished in the

ISL884xAMBEPZ using an external buffer transistor and the

RtCt signal. A typical application sums the buffered RtCt

signal with the current sense feedback and applies the result

to the CS pin, as shown in Figure 6.

Assuming the designer has selected values for the RC filter

(R6 and C4) placed on the CS pin, the value of R9 required

to add the appropriate external ramp can be found by

superposition.

The factor of 2.05 in Equation 16 arises from the peak

amplitude of the sawtooth waveform on RtCt minus a

base-emitter junction drop. That voltage multiplied by the

maximum duty cycle is the voltage source for the slope

compensation. Rearranging to solve for R9 yields:

The value of RCS determined in Equation 15 must be

rescaled so that the current sense signal presented at the

CS pin is that predicted by Equation 13. The divider created

by R6 and R9 makes this necessary.

Example:

VIN = 12V

VO = 48V

Ls = 800µH

Ns/Np = 10

Lp = 8.0µH

IO = 200mA

Switching Frequency, f SW = 20 0kHz

Duty Cycle, D = 28.6%

SeSn1

---0.5+

⎝⎠

⎛⎞

1D–

------------- 1–

⎝⎠

⎛⎞

=(EQ. 10)

VeVn1

---0.5+

⎝⎠

⎛⎞

1D–

------------- 1–

⎝⎠

⎛⎞

=(EQ. 11)

VeDt⋅SW VIN RCS

⋅⋅

-------------------------------------------------- 1

---0.5+

⎝⎠

⎛⎞

1D–

------------- 1–

⎝⎠

⎛⎞

(EQ. 12)

VCS NSRCS

⋅

------------------------ IO1D–()VOf⋅⋅

2Ls

----------------------------------------------

⎝⎠

⎜⎟

⎛⎞

=V(EQ. 13)

VeVCS

+1=(EQ. 14)

RCS 1

sw VIN

⋅⋅

-------------------------------

---0.5+

1D–

------------------1–

⎝⎠

⎜⎟

⎛⎞

⋅Ns

-------IO1D–()VOfsw

⋅⋅

2Ls

--------------------------------------------

⎝⎠

⎜⎟

⎛⎞

⋅+

-----------------------------------------------------------------------------------------------------------------------------------------------------

(EQ. 15)

RTCT

ISL8843

VREF

FIGURE 6. SLOPE COMPENSATION

Ve2.05D R6

⋅

R6R9

----------------------------

=V(EQ. 16)

R92.05D Ve

–()R6

⋅

----------------------------------------------

=Ω(EQ. 17)

R′CS R6R9

---------------------RCS

⋅=(EQ. 18)

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

9FN6792.1

December 1, 2011

R6 = 499Ω

Solve for the current sense resistor, RCS, using Equation 15.

RCS = 295mΩ

Determine the amount of voltage, Ve, that must be added to

the current feedback signal using Eq uation 12.

Ve = 92.4mV

Using Equation 17, solve for the summing resistor, R9, from

CT to CS.

R9 = 2.67kΩ

Determine the new value of RCS (R’CS) using Equation 18.

R’CS = 350mΩ

Additional slope compensation may be considered for

design margin. The previous discussion determines the

minimum external ramp that is required. The buffer transistor

used to create the external ramp from RtCt should have a

sufficiently high gain (>200) so as to minimize the required

base current. Whatever base current is required reduces the

charging current into RtCt and will reduce the oscillator

frequency.

Fault Conditions

A Fault condition occurs if VREF falls below 4.65V. When a

Fault is detected, OUT is disabled. When VREF exceeds

4.80V, the Fault condition clears, and OUT is enabled.

Ground Plane Requirements

Careful layout is essential for satisfactory operation of the

device. A good ground plane mu st be employed. A unique

section of the ground plane must be designated for high di/dt

currents associated with the output stage. VDD should be

bypassed directly to GND with good high frequency

capacitors.

References

[1] Ridley, R., “A New Continuous-T ime Model for Current

Mode Control”, IEEE Transactions on Power

Electronics, Vol. 6, No. 2, April 1991.

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.

Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality

Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without

notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and

reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result

from its use. No lice nse is gran t ed by i mpli catio n or other wise u nder an y p a tent or patent rights of Intersil or its subsidiari es.

For information regarding Intersil Corporation and its products, see www.intersil.com

FN6792.1

December 1, 2011

ISL8840AMZ, ISL8841AMZ, ISL8842AMZ, ISL8843AMZ, ISL8844AMZ, ISL8845 AMZ

Small Outline Plastic Packages (SOIC)

INDEX

AREA E

123

-B-

0.25(0.010) C AMBS

-A-

-C-

SEATING PLANE

0.10(0.004)

h x 45°

H0.25(0.010) BM M

NOTES:

1. Symbols are defined in the “MO Series Symbol List” in Section 2.2 of

Publication Number 95.

2. Dimensioning and toleran cing per ANSI Y14.5M-1982.

3. Dimension “D” does not include mold flash, protrusions or gate burrs.

Mold flash, protrusion and gate burrs shall not exceed 0.15mm (0.006

inch) per side.

4. Dimension “E” does not include interlead flash or protrusions. Inter-

lead flash and protrusions shall not exceed 0.25mm (0.010 inch ) per

side.

5. The chamfer on the body is optional. If it is not present, a visual index

feature must be located within the crosshatched area.

6. “L” is the length of terminal for soldering to a substrate.

7. “N” is the number of terminal positions.

8. Terminal numbers are shown for reference only.

9. The lead width “B”, as measured 0.36mm (0.014 inch) or greater

above the seating plane, shall not exceed a maximum value of

0.61mm (0.024 inch).

10. Controlling dimension: MILLIMETER. Converted inch dimensions

are not necessarily exact.

M8.15 (JEDEC MS-012-AA ISSUE C)

8 LEAD NARROW BODY SMALL OUTLINE PLASTIC PACKAGE

SYMBOL

INCHES MILLIMETERS

NOTESMIN MAX MIN MAX

A 0.0532 0.0688 1.35 1.75 -

A1 0.0040 0.0098 0.10 0.25 -

B 0.013 0.020 0.33 0.51 9

C 0.0075 0.0098 0.19 0.25 -

D 0.1890 0.1968 4.80 5.00 3

E 0.1497 0.1574 3.80 4.00 4

e 0.050 BSC 1.27 BSC -

H 0.2284 0.2440 5.80 6.20 -

h 0.0099 0.0196 0.25 0.50 5

L 0.016 0.050 0.40 1.27 6

N8 87

α0° 8° 0° 8° -

Rev. 1 6/05