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DATA SHEET
AAT1110: Fast Transient 800 mA Step-Down Converter
Applications
Cellular phones
Digital cameras
Handheld instruments
Microprocessor/DSP core/IO power
PDAs and handheld computers
USB devices
Features
VIN range: 2.7 V to 5.5 V
VOUT fixed or adjustable from 0.6 V to VIN
27 A no-load quiescent current
Output current up to 800 mA
1.4 MHz switching frequency
120 s soft start
Fast load transient
Over-temperature protection
Current limit protection
100% duty cycle low-dropout operation
Shutdown current: <1 A
Temperature range: 40 °C to +85 °C
SC70JW (8-pin, 2.2 mm 2 mm) package (MSL1, 260 °C per
JEDEC-J-STD-020)
Description
The AAT1110 SwitchReg™ is a member of Skyworks' Total
Power Management IC (TPMIC™) product family. It is a 1.4 MHz
step-down converter with an input voltage range of 2.7 V to 5.5 V
and output as low as 0.6 V. Its low supply current, small size, and
high switching frequency make the AAT1110 the ideal choice for
portable applications.
The AAT1110 is available in either a fixed version with internal
feedback or a adjustable version with external feedback resistors.
It can deliver up to 800 mA of load current while maintaining a
low 27 A no-load quiescent current. The 1.4 MHz switching
frequency minimizes the size of external components while
keeping switching losses low. The AAT1110 has excellent load
regulation and transient response with a small output inductor
and capacitor.
The AAT1110 is designed to maintain high efficiency throughout
the operating range and provides fast turn-on time.
The AAT1110 is available in a space-saving 2.0 mm 2.2 mm
SC70JW-8 package and is rated over the 40 °C to +85 °C
temperature range.
A typical application circuit is shown in Figure 1. The pin
configuration is shown in Figure 2. Signal pin assignments and
functional pin descriptions are provided in Table 1.
Skyworks Green™ products are compliant with
all applicable legislation and are halogen-free.
For additional information, refer to Skyworks
Definition of Green™, document number
SQ04-0074.
4.7 μH
L1
10 μF
C1
4.7 μF
C2
EN
1OUT 2
VIN
3LX 4
AGND
5
PGND 6
PGND 7
PGND
8
AAT1110
U1
V
IN
V
OUT
tc87
Figure 1. AAT1110 Typical Application Circuit
PRELIMINARY DATA SHEET • AAT1110 FAST TRANSIENT 800 MA STEP-DOWN CONVERTER
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OUT
VIN
LX
PGND
PGND
PGND
AGND
EN 1
2
3
45
6
7
8
tc88
Figure 2. AAT1110 8-Pin SC70JW-8
(Top View)
Table 1. AAT1110 Pin Descriptions
Pin # Name Description
1 EN Enable pin.
2 OUT
Feedback input pin. This pin is connected either directly to the converter output or to an external resistive divider for an
adjustable output.
3 VIN Input supply voltage for the converter.
4 LX Switching node. Connect the inductor to this pin. It is internally connected to the drain of both high- and low-side MOSFETs.
5 AGND Non-power signal ground pin.
6, 7, 8 PGND Main power ground return pin. Connect to the output and input capacitor return.
Electrical and Mechanical Specifications
The absolute maximum ratings of the AAT1110 are provided in
Table 2, and the electrical specifications are provided in Table 3.
Typical performance characteristics of the AAT1110 are illustrated
in Figures 3 through 24.
Table 2. AAT1110 Absolute Maximum Ratings (Note 1)
Parameter Symbol Minimum Typical Maximum Units
Input voltage to GND VIN 6.0 V
LX to GND VLX 0.3 Vin + 0.3 V
OUT to GND VOUT 0.3 Vin + 0.3 V
EN to GND VEN 0.3 +6.0 V
Operating junction temperature TJ 40 +140 °C
Maximum soldering temperature (at leads, 10 seconds) TLEAD 300 °C
Maximum power dissipation (SC70JW-8) PD 719 mW
Thermal resistance (SC70JW-8) (Note 2) JA 160 °C/W
Note 1: Exposure to maximum rating conditions for extended periods may reduce device reliability. There is no damage to device with only one parameter set at the limit and all other
parameters set at or below their nominal value. Exceeding any of the limits listed may result in permanent damage to the device.
Note 2: Mounted on an FR4 board.
CAUTION: Although this device is designed to be as robust as possible, Electrostatic Discharge (ESD) can damage this device. This device
must be protected at all times from ESD. Static charges may easily produce potentials of several kilovolts on the human body
or equipment, which can discharge without detection. Industry-standard ESD precautions should be used at all times.
PRELIMINARY DATA SHEET • AAT1110 FAST TRANSIENT 800 MA STEP-DOWN CONVERTER
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Table 3. AAT1110 Electrical Specifications (Note 1)
(VIN = 3.6 V, TA = 40 °C to 85 °C, Unless Otherwise Noted. Typical Values are at TA = 25 °C)
Parameter Symbol Test Condition Min Typical Max Units
Step-Down Converter
Input voltage VIN 2.7 5.5 V
UVLO threshold VUVLO
Vin rising 2.7 V
Hysteresis 100 mV
VIN falling 1.8 V
Output voltage tolerance VOUT IOUT = 0 to 800 mA, VIN = 2.7 V to 5.5 V 3.5 +3.5 %
Output voltage VOUT 0.6 VIN V
Quiescent current IQ No load, 0.6 V adjustable version 27 70 A
Shutdown current ISHDN EN = AGND = PGND 1.0 A
P-channel current limit ILIM 800 1200 mA
High-side switch on resistance RDS(ON)H 0.45
Low-side switch on resistance RDS(ON)L 0.40
Line regulation VLINEREG VIN = 2.7 V to 5.5 V 0.1 %/V
OUT pin leakage current IOUT_LEAK 0.6 V output 0.2 A
Output impedance ROUT >0.6 V output 250 k
Soft-start time tSS From enable to output regulation 120 s
Oscillator frequency fOSC TA = 25 °C 1.0 1.4 2.0 MHz
Over-temperature shutdown threshold TSD 140 °C
Over-temperature shutdown hysteresis THYS 15 °C
EN
Enable threshold low VEN(L) 0.6 V
Enable threshold high VEN(H) 1.4 V
Input low current IEN VIN = VOUT = 5.5 V 1.0 1.0 A
Note 1: Performance is guaranteed only under the conditions listed in this Table.
PRELIMINARY DATA SHEET • AAT1110 FAST TRANSIENT 800 MA STEP-DOWN CONVERTER
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6Typical Performance Characteristics
Output Current (mA)
Efficiency (%)
50
60
70
80
90
100
0.1 1 10 100 1000
V
IN
= 2.7 V
V
IN
= 3.6 V V
IN
= 4.2 V
Figure 3. Efficiency vs Load
(VOUT = 1.8 V, L = 4.7 H)
Output Current (mA)
Efficiency (%)
50
60
70
80
90
100
0.1 1 10 100 1000
VIN = 5.0 V
VIN = 3.6 V
VIN = 3.0 V
VIN = 4.2 V
Figure 5. Efficiency vs Load
(VOUT = 2.5 V, L = 6.8 H)
Output Current (mA)
Efficiency (%)
50
60
70
80
90
100
0.1 1 10 100 1000
VIN = 5.0 V
VIN = 3.6 V
VIN = 4.2 V
Figure 7. Efficiency vs Load
(VOUT = 3.3 V, L = 6.8 H)
Output Current (mA)
Output Error (%)
-1.0
-0.5
0.0
0.5
1.0
0.1 1 10 100 1000
V
IN
= 2.7 V
V
IN
= 3.6 V
V
IN
= 4.2 V
Figure 4. DC Regulation
(VOUT = 1.8 V)
Output Current (mA)
Output Error (%)
-2.0
-1.5
-1.0
-0.5
0.0
0.5
1.0
1.5
2.0
0.1 1 10 100 1000
V
IN
= 5.0 V
V
IN
= 3.6 V
V
IN
= 3.0 V
V
IN
= 4.2 V
Figure 6. DC Regulation
(VOUT = 2.5 V)
Output Current (mA)
Output Error (%)
-1.0
-0.5
0.0
0.5
1.0
0.1 1 10 100 1000
V
IN
= 5.0 V
V
IN
= 4.2 V
Figure 8. DC Regulation
(VOUT = 3.3 V)
PRELIMINARY DATA SHEET • AAT1110 FAST TRANSIENT 800 MA STEP-DOWN CONVERTER
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Typical Performance Characteristics
Time (100 μ
μ
s/div)
Enable and Output Voltage
(top) (V)
Inductor Current
(bottom) (A)
-5.0
-4.0
-3.0
-2.0
-1.0
0.0
1.0
2.0
3.0
4.0
5.0
-0.2
0.0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
V
EN
V
OUT
I
L
^
^
^
Figure 9. Soft Start
(VIN = 3.6 V, VOUT = 1.8 V, IOUT = 800 mA)
Temperature (°
°
C)
Output Error (%)
-2.0
-1.0
0.0
1.0
2.0
-40 -20 0 20 40 60 80 100
Figure 11. Output Voltage Error vs Temperature
(VIN = 3.6 V, VOUT = 1.8 V, IOUT = 400 mA)
Input Voltage (V)
Frequency Variation (%)
-4.0
-3.0
-2.0
-1.0
0.0
1.0
2.0
2.7 3.1 3.5 3.94.3 4.7 5.1 5.5
V
OUT
= 1.8 V V
OUT
= 2.5 V
V
OUT
= 3.3 V
Figure 13. Frequency vs Input Voltage
(IOUT = 800 mA)
Input Voltage (V)
Accuracy (%)
-0.40
-0.30
-0.20
-0.10
0.00
0.10
0.20
0.30
0.40
2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
I
OUT
= 1 mA
I
OUT
= 400 mA
I
OUT
= 800 mA
I
OUT
= 10 mA
Figure 10. Line Regulation
(VOUT = 1.8 V)
Temperature (°
°
C)
Variation (%)
-15.0
-12.0
-9.0
-6.0
-3.0
0.0
3.0
6.0
9.0
12.0
15.0
-40 -20 0 20 40 60 80 100
Figure 12. Switching Frequency vs Temperature
(VIN = 3.6 V, VOUT = 1.8 V)
Input Voltage (V)
Supply Current (m
m
A)
10
15
20
25
30
35
40
45
50
2.7 3.1 3.5 3.94.3 4.7 5.1 5.5
85 °C25 °C
–40 °C
Figure 14. No Load Quiescent Current vs Input Voltage
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Typical Performance Characteristics
Output Voltage
(top) (V)
Load and Inductor Current
(500 mA/div) (bottom)
Time (50 μs/div)
1.5
2.0
2.5
-0.5
0.0
0.5
V
OUT
(
AC
)
^
L
LOAD
^
I
L
^
Figure 15. Load Transient Response
(1 mA to 600 mA, VIN = 3.6 V, VOUT = 1.8 V, C1 = 10 F)
1.6
1.8
2.0
2.2
-0.5
0.0
0.5
Output Voltage
(top) (V)
Load and Inductor Current
(500 mA/div) (bottom)
Time (50 μs/div)
V
OUT
(
AC
)
^
L
LOAD
^
I
L
^
Figure 17. Load Transient Response
(1 mA to 600 mA, VIN = 3.6 V, VOUT = 1.8 V,
C1 = 10 F, CFF = 100 pF)
1.8
2.0
2.2
-0.5
0.0
0.5
Output Voltage
(top) (V)
Load and Inductor Current
(500 mA/div) (bottom)
Time (50 μs/div)
V
OUT
(
AC
)
^
I
LOAD
^
^
I
L
Figure 19. Load Transient Response
(1 mA to 600 mA, VIN = 3.6 V, VOUT = 1.8 V,
C1 = 22 F, CFF = 100 pF)
Time (50 μs/div)
1.7
1.8
1.9
2.0
0.4
0.5
0.6
0.7
0.8
Output Voltage
(top) (V)
Load and Inductor Current
(100 mA/div) (bottom)
V
OUT
(
AC
)
^
I
LOAD
^
^
I
L
Figure 16. Load Transient Response
(600 mA to 800 mA, VIN = 3.6 V, VOUT = 1.8 V, C1 = 10 F)
1.7
1.8
1.9
2.0
0.4
0.5
0.6
0.7
0.8
Output Voltage
(top) (V)
Load and Inductor Current
(100 mA/div) (bottom)
Time (50 μs/div)
V
OUT
(
AC
)
^
I
LOAD
^
^
I
L
Figure 18. Load Transient Response
(600 mA to 800 mA, VIN = 3.6 V, VOUT = 1.8 V, C1 = 22 F)
1.7
1.8
1.9
2.0
0.4
0.5
0.6
0.7
0.8
Output Voltage
(top) (V)
Load and Inductor Current
(100 mA/div) (bottom)
Time (50 μs/div)
V
OUT
(
AC
)
^
I
LOAD
^
^
I
L
Figure 20. Load Transient Response
(600 mA to 800 mA, VIN = 3.6 V, VOUT = 1.8 V,
C1 = 10 F, CFF = 100 pF)
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Typical Performance Characteristics
1.66
1.68
1.70
1.72
1.74
1.76
1.78
1.80
1.82
1.84
1.86
2.6
3.1
3.6
4.1
4.6
5.1
5.6
6.1
6.6
7.1
7.6
Output Voltage
(top) (V)
Input Voltage
(bottom) (V)
Time (50 μs/div)
Figure 21. Line Response
(VOUT = 1.8 V @ 800 mA)
-120
-100
-80
-60
-40
-20
0
20
40
-0.10
-0.05
0.00
0.05
0.10
0.15
0.20
0.25
0.30
Time (10 μs/div)
Output Voltage (AC Coupled)
(top) (mV)
Inductor Current
(bottom) (A)
Figure 23. Output Ripple
(VIN = 3.6 V, VOUT = 1.8 V, IOUT = 1 mA)
-60
-50
-40
-30
-20
-10
0
10
20
0.5
0.6
0.7
0.8
0.9
1.0
1.1
1.2
1.3
Output Voltage (AC Coupled)
(top) (mV)
Inductor Current
(bottom) (A)
Time (500 ns/div)
Figure 22. Output Ripple
(VIN = 3.6 V, VOUT = 1.8 V, IOUT = 800 mA)
Input Voltage (V)
R
DS
(
ON
) (m
Ω
)
300
350
400
450
500
550
600
650
700
750
2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
25 °C
120 °C
100 °C
85 °C
Figure 24. P-Channel RDS(ON) vs Input Voltage
(VOUT = 1.8 V; CFF = 100 pF)
PRELIMINARY DATA SHEET • AAT1110 FAST TRANSIENT 800 MA STEP-DOWN CONVERTER
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EN
LX
Error
.
Amp.
Logic
DH
DL
PGND
VIN
OUT
AGND
Voltage
Reference
INPUT
See note
Note: For adjustable version, the internal feedback divider is omitted and the OUT pin is tied directly
to the internal error amplifier.
tc89
Figure 25. AAT1110 Functional Block Diagram
Functional Description
The AAT1110 is a high performance 800 mA, 1.4 MHz
monolithic step-down converter. It has been designed with the
goal of minimizing external component size and optimizing
efficiency over the complete load range. Apart from the small
bypass input capacitor, only a small L-C filter is required at the
output. Typically, a 4.7 H inductor and a 10 F ceramic
capacitor are recommended..
A functional block diagram is shown in Figure 25.
The fixed output version requires only three external power
components (CIN, COUT, and L). The adjustable version can be
programmed with external feedback to any voltage, ranging
from 0.6 V to the input voltage. An additional feed-forward
capacitor (C4) can also be added to the external feedback to
provide improved transient response (see Figure 26).
At dropout, the converter duty cycle increases to 100% and the
output voltage tracks the input voltage minus the RDSON drop of
the P-channel high-side MOSFET.
The input voltage range is 2.7 V to 5.5 V. The converter
efficiency has been optimized for all load conditions, ranging
from no load to 800 mA.
The internal error amplifier and compensation provides
excellent transient response, load, and line regulation. Soft start
eliminates any output voltage overshoot when the enable is
applied.
Control Loop
The AAT1110 is a peak current mode step-down converter. The
current through the P-channel MOSFET (high side) is sensed for
current loop control, as well as short circuit and overload
protection. A fixed slope compensation signal is added to the
sensed current to maintain stability for duty cycles greater than
50%. The peak current mode loop appears as a voltage-
programmed current source in parallel with the output capacitor.
The output of the voltage error amplifier programs the current
mode loop for the necessary peak switch current to force a
constant output voltage for all load and line conditions. Internal
loop compensation terminates the transconductance voltage
error amplifier output. For fixed voltage versions, the error
amplifier reference voltage is internally set to program the
converter output voltage. For the adjustable output, the error
amplifier reference is fixed at 0.6 V.
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L1: CDRH3D16-4R7
L1
C1 C2
U1: AAT1110 SC70JW-8
C2: 4.7 F, 10 V, 0805 X5R
V
OUT
1.8 V
GND
1
2
3
Enable
LX
EN
1
OUT
2
VIN
3
LX
4AGND 5
PGND 6
PGND 7
PGND 8
AAT1110
U1
GND2
118 k
R1
59 k
R2
C1: 10 F, 6.3 V, 0805 X5R
100 pF
C4
n/a
C3
V
IN
4.7 H
10 F
tc90
Figure 26. Enhanced Transient Response Schematic
Soft Start/Enable
Soft start limits the current surge seen at the input and
eliminates output voltage overshoot. When pulled low, the
enable input forces the AAT1110 into a low power, non-
switching state. The total input current during shutdown is less
than 1 A.
Current Limit and Over-Temperature Protection
For overload conditions, the peak input current is limited. To
minimize power dissipation under current limit and short-circuit
conditions, switching is terminated after entering current limit
for a series of pulses. Switching is terminated for seven
consecutive clock cycles after a current limit has been sensed
for a series of four consecutive clock cycles.
Thermal protection completely disables switching when internal
dissipation becomes excessive. The junction over-temperature
threshold is 140 °C with 15 °C of hysteresis. Once an over-
temperature or over-current fault conditions is removed, the
output voltage automatically recovers.
Under-Voltage Lockout
Internal bias of all circuits is controlled via the VIN input. Under-
voltage lockout (UVLO) guarantees sufficient VIN bias and proper
operation of all internal circuitry prior to activation.
Applications Information
Inductor Selection
The step-down converter uses peak current mode control with
slope compensation to maintain stability for duty cycles greater
than 50%. The output inductor value must be selected so the
inductor current down slope meets the internal slope
compensation requirements. The internal slope compensation
for the adjustable and low-voltage fixed versions of the
AAT1110 is 0.24 A/s. This equates to a slope compensation
that is 75% of the inductor current down slope for a 1.5 V
output and 4.7 H inductor.
s
A
24.0
H7.4 V5.175.0
LV75.0
mOUT
This is the internal slope compensation for the adjustable (0.6 V)
version or low-voltage fixed versions. When externally
programming the 0.6 V version to 2.5 V, the calculated
inductance is 7.5 H.
H5.7V5.2
A
s
3
V
A
s
3
s
A
24.0
V75.0
mV75.0
LOUT
OUTOUT
In this case, a standard 6.8 H value is selected.
For high-voltage fixed versions ( 2.5 V), m = 0.48 A/s.
Manufacturer’s specifications list both the inductor DC current
rating, which is a thermal limitation, and the peak current rating,
which is determined by the saturation characteristics. The
inductor should not show any appreciable saturation under
normal load conditions. Some inductors may meet the peak and
average current ratings yet result in excessive losses due to a
high DCR. Always consider the losses associated with the DCR
and its effect on the total converter efficiency when selecting an
inductor.
Input Capacitor
Select a 4.7 F to 22 F X7R or X5R ceramic capacitor for the
input. To estimate the required input capacitor size, determine
the acceptable input ripple level (VPP) and solve for C. The
calculated value varies with input voltage and is a maximum
when VIN is double the output voltage.
S
OUT
PP
IN
OUT
IN
OUT
IN fESR
I
V
V
V
1
V
V
C
4
1
V
V
1
V
V
IN
OUT
IN
OUT
for OUTIN V2V
PRELIMINARY DATA SHEET • AAT1110 FAST TRANSIENT 800 MA STEP-DOWN CONVERTER
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S
OUT
PP
)MIN(IN f4ESR
I
V
1
C
Where, fS is the switching frequency.
Always examine the ceramic capacitor DC voltage coefficient
characteristics when selecting the proper value. For example,
the capacitance of a 10 F, 6.3 V, X5R ceramic capacitor with
5.0 V DC applied is actually about 6 F.
The maximum input capacitor RMS current is:
IN
OUT
IN
OUT
OUTRMS V
V
1
V
V
II
The input capacitor RMS ripple current varies with the input and
output voltage and always is less than or equal to half of the
total DC load current.

2
1
5.0D1D
V
V
1
V
V2
IN
OUT
IN
OUT
for VIN = 2 VOUT
2
I
IOUT
MAXRMS
）（
The term
IN
OUT
IN
OUT V
V
1
V
V appears in both the input voltage
ripple and input capacitor RMS current equations and is a
maximum when VOUT is twice VIN. This is why the input voltage
ripple and the input capacitor RMS current ripple are a
maximum at 50% duty cycle.
The input capacitor provides a low impedance loop for the
edges of pulsed current drawn by the AAT1110. Low ESR/ESL
X7R and X5R ceramic capacitors are ideal for this function. To
minimize stray inductance, the capacitor should be placed as
closely as possible to the IC. This keeps the high frequency
content of the input current localized, minimizing EMI and input
voltage ripple.
The proper placement of the input capacitor (C2) can be seen in
the evaluation board layout in Figure 28.
A laboratory test setup typically consists of two long wires
running from the bench power supply to the evaluation board
input voltage pins. The inductance of these wires, along with
the low-ESR ceramic input capacitor, can create a high-Q
network that may affect converter performance. This problem
often becomes apparent in the form of excessive ringing in the
output voltage during load transients. Errors in the loop phase
and gain measurements can also result.
Because the inductance of a short PCB trace feeding the input
voltage is significantly lower than the power leads from the
bench power supply, most applications do not exhibit this
problem.
In applications where the input power source lead inductance
cannot be reduced to a level that does not affect the converter
performance, a high ESR tantalum or aluminum electrolytic
should be placed in parallel with the low ESR, ESL bypass
ceramic. This dampens the high-Q network and stabilizes the
system.
Output Capacitor
The output capacitor limits the output ripple and provides
holdup during large load transitions. A 4.7 F to 10 F X5R or
X7R ceramic capacitor typically provides sufficient bulk
capacitance to stabilize the output during large load transitions
and has the ESR and ESL characteristics necessary for low
output ripple.
The output voltage droop due to a load transient (ILOAD) is
dominated by the capacitance of the ceramic output capacitor.
During a step increase in load current, the ceramic output
capacitor alone supplies the load current until the loop
responds. Within two or three switching cycles, the loop
responds and the inductor current increases to match the load
current demand. The relationship of the output voltage droop
during the three switching cycles to the output capacitance can
be estimated by:
SDROOP
LOAD
OUT fV I3
C
Once the average inductor current increases to the DC load
level, the output voltage recovers. The above equation
establishes a limit on the minimum value for the output
capacitor with respect to load transients.
The internal voltage loop compensation also limits the minimum
output capacitor value to 4.7 F. This is due to its effect on the
loop crossover frequency (bandwidth), phase margin, and gain
margin. Increased output capacitance reduces the crossover
frequency with greater phase margin.
The maximum output capacitor RMS ripple current is given by:
)MAX(INS
OUT)MAX(INOUT
MAXRMS VfL
VVV
32
1
I
）（
Dissipation due to the RMS current in the ceramic output
capacitor ESR is typically minimal, resulting in less than a few
degrees rise in hot-spot temperature.
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Adjustable Output Resistor Selection
For applications requiring an adjustable output voltage, the
0.6 V version can be externally programmed. Resistors R1 and
R2 of Figure 28 program the output to regulate at a voltage
higher than 0.6 V. To limit the bias current required for the
external feedback resistor string while maintaining good noise
immunity, the minimum suggested value for R2 is 59 k.
Although a larger value can further reduce quiescent current, it
also increases the impedance of the feedback node, making it
more sensitive to external noise and interference. Table 4
summarizes the resistor values for various output voltages with
R2 set to either 59 k for good noise immunity or 221 k for
reduced no-load input current.
k5.88k591
V6.0 V5.1
2R1
V
V
R1
REF
OUT
The adjustable version of the AAT1110, combined with an
external feed-forward capacitor (C4 in Figure 26), delivers
enhanced transient response for extreme pulsed load
applications. Addition of the feed-forward capacitor typically
requires a larger output capacitor C1 for stability.
Table 4. Adjustable Resistor Values for Use with 0.6 V Step-
Down Converter
VOUT (V) R1 (k)
(R2 = 59 k)
R1 (k)
(R2 = 221 k)
0.8 19.6 75
0.9 29.4 113
1.0 39.2 150
1.1 49.9 187
1.2 59.0 221
1.3 68.1 261
1.4 78.7 301
1.5 88.7 332
1.8 118 442
1.85 124 464
2.0 137 523
2.5 187 715
3.3 267 1000
Thermal Calculations
There are three types of losses associated with the AAT1110
step-down converter: switching losses, conduction losses, and
quiescent current losses. Conduction losses are associated with
the RDS(ON) characteristics of the power output switching
devices. Switching losses are dominated by the gate charge of
the power output switching devices. At full load, assuming
continuous conduction mode (CCM), a simplified form of the
losses is given by:

INQOUTSSW
IN
OUTINL)ON(DSOUTH)ON(DS
2
OUT
TOTAL
VIIft
V
VVRVRI
P
IQ is the step-down converter quiescent current. The term tSW is
used to estimate the full load step-down converter switching
losses.
For the condition where the step-down converter is in dropout
at 100% duty cycle, the total device dissipation reduces to:
INQH)ON(DS
2
OUTTOTAL VIRIP
Since RDS(ON), quiescent current, and switching losses all vary
with input voltage, the total losses should be investigated over
the complete input voltage range.
Given the total losses, the maximum junction temperature can
be derived from the JA for the SC70JW-8 package which is
160 °C/W.
AJATOTALJ(MAX) TPT
Layout
The following guidelines should be used to help ensure a proper
layout.
The input capacitor (C2) should connect as closely as possible
to VIN (Pin 3) and PGND (Pins 6-8).
C1 and L1 should be connected as closely as possible. The
connection of L1 to the LX pin should be as short as
possible.
The feedback trace or OUT pin (Pin 2) should be separate
from any power trace and connect as closely as possible to
the load point. Sensing along a high-current load trace
degrades DC load regulation. If external feedback resistors
are used, they should be placed as closely as possible to
the OUT pin (Pin 2) to minimize the length of the high
impedance feedback trace.
The resistance of the trace from the load return to the PGND
(Pins 6-8) should be kept to a minimum. This helps
minimize any error in DC regulation due to differences in
the potential of the internal signal ground and the power
ground.
Evaluation Board Description
The AAT1110 Evaluation Board schematic diagram is provided
in Figure 27. The PCB layer details are shown in Figure 28.
Table 5 lists the evaluation board component values. Tables 6
and 7 give the typical surface mount inductors and surface
mount capacitors.
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OUT
2
EN
1
VIN
3
LX
4AGND 5
PGND 7
PGND 8
PGND 6
U1 AAT1110
1
2
3
JP1
GND
GND
C4(option)
option
C3
4.7 μH
L1
10 μF
C1C2
118 kΩ
R1
59 kΩ
R2
VIN
4.7 μF
VOUT
L1: CDRH3D16-4R7
U1: AAT1110 SC70JW-8
C2: 4.7 μF, 10 V, 0805 X5R
C1: 10 μF, 6.3 V, 0805 X5R
tc91
Figure 27. AAT1110 Adjustable Evaluation Board Schematic
Top Side Bottom Side
tc92
Figure 28. AAT1110 Evaluation Board Layer Details
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Table 5. Evaluation Board Component Values
Adjustable Version (0.6 V device)
VOUT (V) R1 (k)
(R2 = 59 k)
R1 (k)
(R2 = 221 k) (Note 1) L1 (H)
0.8 19.6 75.0 2.2
0.9 29.4 113 2.2
1.0 39.2 150 2.2
1.1 49.9 187 2.2
1.2 59.0 221 2.2
1.3 68.1 261 2.2
1.4 78.7 301 4.7
1.5 88.7 332 4.7
1.8 118 442 4.7
1.85 124 464 4.7
2.0 137 523 6.8
2.5 187 715 6.8
3.3 267 1000 6.8
Fixed Version
VOUT (V) （R1, R2 Not Used） L1 (H)
0.6-3.3V 4.7
Note 1: For reduced quiescent current, R2 = 221 k.
Table 6. Typical Surface Mount Inductors
Manufacturer Part Number/Type Inductance
(H)
Max. DC Current
(A)
DCR
(m)
Size (mm)
LWH
TOKO 1276AS-H-2R2N 2.2 1.60 98 3.22.51.0
TOKO 1239AS-H-4R7M 4.7 1.30 200 2.52.01.2
TOKO 1277AS-H-6R8N 6.8 1.20 230 3.22.51.2
Murata LQM2HPN2R2MMR 2.2 1.38 68 2.52.01.1
Murata LQH32PN4R7NNC 4.7 1.20 155 3.13.11.5
Coilcraft LPS3015-222MLB 2.2 2.0 110 3.13.11.5
Table 7. Surface Mount Capacitors
Manufacturer Part Number Value (F) Voltage (V) Temperature Coefficient Case
Murata GRM219R61A475KE19 4.7 10 X5R 0805
Murata GRM21BR60J106KE19 10 6.3 X5R 0805
Murata GRM21BR60J226ME39 22 6.3 X5R 0603
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Package Information
Package dimensions and tape & reel dimensions are shown in
Figures 29 and 30, respectively.
0.225 ±
±
0.075
0.45 ±
±
0.10
0.05 ±
±
0.05
2.10 ±
±
0.30
2.00 ±
±
0.20
7
°
±
3
°
4°
°
±
±
4°
°
1.75 ±
±
0.10
0.85 ±
±
0.15
0.15 ±
±
0.05
1.10 Max.
0.100
2.20 ±
±
0.20
0.048 Ref.
0.50 BSC 0.50 BSC 0.50 BSC
tc13
Top View
Side View Front View
All dimensions are in millimeters.
Figure 29. AAT1110 8-pin SC70JW Package Dimensions
1.55 ± 0.05
8.00 ± 0.30
4.00 ± 0.10
2.00 ± 0.05
1.75 ± 0.05 3.50 ± 0.05
Pin 1 Location
4.00 ± 0.10 1.30 ± 0.10
0.20 ± 0.03
2.40 ± 0.10
2.50 ± 0.10
tc38
All dimensions are in millimeters.
Figure 30. AAT1110 Carrier Tape Dimensions
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Ordering Information
Model Name Output Voltage (Note 1) Package
Marking (Note 2) Manufacturing Part Number (Note 3)
AAT1110 Fast Transient 800 mA
Step-Down Converter
3.3 V SC70JW-8 TSXYY AAT1110IJS-3.3-T1
Adj. 0.6 V SC70JW-8 SRXYY AAT1110IJS-0.6-T1
Note 1: Contact Sales for other voltage options.
Note 2: XYY = assembly and date code.
Note 3: Sample stock is generally held on part numbers listed in BOLD.
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