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FUJI Power Supply Control IC
Power Factor Correction
FA5500AP/AN
FA5501AP/AN
November `02
Fuji Electric Co., Ltd.
Matsumoto Factory
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1.This Data Book contains the product specifications, characteristics, data, materials, and structures
as of November 2002. The contents are subject to change without notice for specification changes
or other reasons. When using a product listed in this Data Book, be sure to obtain the latest
specifications.
2. All applications described in this Data Book exemplify the use of Fuji's products for your reference
only. No right or license, either express or implied, under any patent, copyright, trade secret or other
intellectual property right owned by Fuji Electric Co., Ltd. is (or shall be deemed) granted. Fuji
makes no representation or warranty, whether express or implied, relating to the infringement or
alleged infringement of other's intellectual property rights which may arise from the use of the
applic at ions described herein.
3. Although Fuji Electric is enhancing product quality and reliability, a small percentage of
semiconductor products may become faulty. When using Fuji Electric semiconductor products in
your equipment, you are requested to take adequate safety measures to prevent the equipment
from causing a physical injury, fire, or other problem if any of the products become faulty. It is
recommende d t o make your design fai l-sa fe, f la me ret ardant , and free of malfunction.
4.The products introduced in this Data Book are intended for use in the following electronic and
electr ical equipment w hi ch has normal reli ability require ment s.
• Computers • OA equipme nt • Communicat ions equipment (terminal devices)
• Measurement equipment • Machine tools • Audiovisual equipment • Electrical home
appliances • Personal equipment • Industrial robots etc.
5.If you need to use a product in this Data Book for equipment requiring higher reliability than normal,
such as for the equipment listed below, it is imperative to contact Fuji Electric to obtain prior
approval. When using these products for such equipment, take adequate measures such as a
backup system to prevent the equipm ent from malfunctioning even if a Fuji's product incorporated in
the equipment becomes fault y.
• Tr ansportation equip me nt (mou nt ed on cars and ships) • Trunk co mmu nications equipment
• Tr affic-signal c ont rol equipment • Gas leakage detect ors w it h an auto-shut-of f feat ure
• Emergency equipment for responding to disasters and anti-burglary devices • Safety devices
6. Do not use products in this Data Book for the equipment requiring strict reliability such as (without
limitation)
• Space equipment • Aeronautic equipment • Atomic control equipment
• Submarine repeat er equipment • Medical equi pment
7. Copyright © 1995 by Fuji Electric Co., Ltd. All rights reserved. No part of this Data Book may be
reproduced in any form or by any means without the express p ermission of Fuji Electric.
8. If you have any question about any portion in this Data Book, ask Fuji Electric or its sales agents
before using the product. Neither Fuji nor its agents shall be liable for any injury caused by any use
of the products n ot in accordance with instructi ons set forth herein.
WARNING
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CONTENTS
Pages
1. Description ……………. 4
2. Features ……………. 4
3. Outline ……………. 4
4. Types of FA5500A/01A ……………. 4
5. Block diagram ……………. 5
6. Pin assignment ……………. 5
7. Ratings a nd ch aracteris tics ………… …. 6 – 8
8. Character ist ic c urves ………… …. 9 – 12
9. Descr ip ti o n of PFC c on v er ter ………… …. 13 – 1 4
10. Descr ip ti o n of e ac h c ircui t ………… …. 15 – 1 8
11. Design advice ……………. 19 –25
12. Exam pl e of a p pl ic at io n cir cui t ………… …. 26
Note
• Parts tolerance and characteristics are not defined in all application described in this Data book. When design an
actual circuit for a product, you must determine parts tolerances and characteristics for safe and economical
operation.
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1. Description
FA5500A/FA5501A are control ICs for a power factor correction converter using critical conduction mode of operation.
This IC uses a CMOS device with high dielectric strength (30V) to implement low power consumption. These ICs contain
compensated current sense comparator for light load and open/short protection at feedback (FB) pin. Compensated current
sense comparator for light load keeps output voltage constant from no-load to full-load. Open/short protection at FB pin
stops output pulses when voltage divider to detect output voltage becomes fault.
2. Features
• Low current consumption by CMOS process
Start-up : 20µA(max.), Operating : 1mA(typ.)
• Drive circuit for connecting a power MOSFET directly
• Output peak current, source : 500mA, sink : 1000mA
• Compensa ted curre nt sen se comparator for light load
• Open/short protection at feedback (FB) pin
• Undervoltage Lockout
FA5500A: 11.5V ON / 9V OFF FA5501A:13V ON / 9V OFF
• Overvoltage protection
• Restart timer
• Package: DIP-8 / SOP-8
3. Outline
SOP-8 DIP-8
1
8
4
5
0.18 ±0.08
0.65 ±0.25
1.27 0.4 ±0.1
4.9
6 ±0.2
3.9
0.20
+0.10
-0.05
1.8 MAX
oo 80 −
0.25- 0.05
+0.1
3 MIN 4.5 MAX 6.4
1.0 ±0.3
2.54×3=7.62
2.54
9.3
7.62
3.3
8
1
5
4
1.5 ±0.3
0.46 ±0.1
oo 150 −
4. Types of FA5500A/01A
Type Startup Threshold Package
FA5500AP 11.5V(typ.) DIP-8
FA5500AN 11.5V(typ.) SOP-8
FA5501AP 13V(typ.) DIP-8
FA5501AN 13V(typ.) SOP-8
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5. Block diagram
7
+
-
83
1
54
VREF(2.5V)
VOVP(1.09VREF)
VCC
FB
OUT
UVLO
REF
ERRAMP
S
RQ
VDD(5.0V)
-
+
-
VREF(2.5V)
MUL
VZCD(1.5V/1.33V)
TIMER
ZCDIS
MUL
VZCD(1.5V/1.33V)
OVP
+
-
VOS(2.0V)
AOC
VOS(2.0V)
VSP(0.3V)
SP
2
COMP
6
GND
VOVP
(1.09VREF)
VSP(0.3V)
OVP
SP
+
-
+
-
R
R
2.5µA
+
6. Pin assignment
1234
8765
OUTVCC GND ZCD
FB COMP MUL IS
Pin No. Pin
symbol Function Description
1 FB Voltage Feedback Input Input for monitoring PFC output voltage
2 COMP Compensation Output of error amplifier
3 MUL Multiplier Input Input of multiplier for monitoring sinusoidal
waveform
4 IS Current Sense Input Input for sensing MOSFET current signal
5 ZCD Zero Current Detect Input Input for detecting that the inductor current
reaches zero
6 GND Ground Ground
7 OUT Output Output for direct driving a power MOSFET
8 VCC Power Supply Power supply for IC
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7. Ratings and characteristics
The contents are subject to change without notice. When using a product, be sure to obtain the latest specifications.
(1) Absolute Maximum Ratings
Item Symbol
Ratings Unit
Total Power Supply and Zener Current Icc+Iz 30 mA
Supply
Voltage Zener Clamp (Icc+Iz<30mA) Vcc Self Limiting V
Output Current Sink
Source Io +1000
-500 mA
mA
Input voltage(IS,MUL,FB) Vin -0.3 to 5 V
Zero Current Detect Input
High State Forward Current
Low State Reverse Current Iin
-50
10 mA
DIP-8 Pd1 800 mW Power dissipation SOP-8 Pd2 400 mW
Operating Ambient Temperature Ta -30 to +105 °C
Operating Junction Temperature Tj +150 °C
Storage Temperature Tstg -55 to +150 °C
Maximum dissipation curve
-30 25 105 150
400mW(SOP)
800mW(DIP)
Maximum dissipation Pd [mW]
Ambience temperature Ta(°C)
(2) Recommended Operating Conditions
Item Symbol Min Typ Max Unit
Supply Voltage Vcc 10 12 28 V
ZCD pin current Izcd ±3 mA
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(3) Electrical Characteristics (Unl ess otherwise specified, Ta=25°C and Vcc=12V)
ERROR AMPLIFIER(FB,COMP Pin)
Item Symbol Condition Min Typ Max Unit
Voltage Feedback Input
Threshold Vfb Ta=25°C 2.465 2.500 2.535 V
Line Regulation Regline Vcc=12V to 28V
Ta=25°C -50 -20 - mV
Temperature stability VdT Ta=-30°C to +105°C ±0.5 mV/°C
Transconductance Gm Ta=25°C 70 90 120 µmho
Output Current Io Source(Vfb=2.3V)
Sink(Vfb=2.7V) -
- 10
10 -
- µA
OVERVOLTAGE COMPARATER (FB Pin)
Item Symbol Condition Min Typ Max Unit
Input Threshold Vthovp 1.075Vfb 1.09Vfb 1.105Vfb V
FB SHORT COMPARATOR(FB Pin)
Item Symbol Condition Min Typ Max Unit
Input Threshold Vthsht 0.1 0.3 0.5 V
Pulldown Current Ifb 0.5 2.5 5 µA
MULTIPLIER(COMP,MUL Pin)
Item Symbol Condition Min Typ Max Unit
Input Threshold
Pin2(COMP) Vthcomp 1.79 2.04 - V
Dynamic Input Voltage Range
Pin3(MUL)
Pin2(COMP)
Vpin3
Vpin2
0 to 2.5
Vthcomp to
Vthcomp
+1.0
0 to 3.5
Vthcomp to
Vthcomp
+1.5
-
V
Gain K
Vpin3=0.5V
Vpin2=Vthcomp
+1.0V 0.53 0.75 0.97 1/V
K=Pin4Threshold/{Vpin3(Vpin2-Vthcomp)}
ZERO CURRENT DETECTOR (ZCD Pin)
Item Symbol Condition Min Typ Max Unit
Input Threshold Voltage Vthzcd Vin increasing 1.33 1.50 1.87 V
Hysteresis Vh Vin decreasing 100 170 300 mV
Input Clamp Voltage
“H” state
“L” state
Vih
Vil
Idet=+3.0mA
Idet=-3.0mA
7.0
0.3
7.6
0.6
-
1.0
V
CURRENT SENSE COMPARATOR (IS Pin)
Item Symbol Condition Min Typ Max Unit
Maximum Current Sense
Input Threshold Vthis Vpin1=1.0V
Vpin3=3.0V 1.3 1.5 1.8 V
Delay to Output Tphl - 170 400 ns
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DRIVE OUTPUT (OUT Pin)
Item Symbol Condition Min Typ Max Unit
Output Voltage Low State Vol Vcc=12V
Isink=200mA - 1.2 3.3 V
Output Voltage High State Voh Vcc=12V
Isouce=200mA 7.8 8.4 V
Output Voltage Rise Time Tr CL=1.0nF - 50 120 ns
Output Voltage Fall Time Tf CL=1.0nF - 25 100 ns
RESTART TIMER
Item Symbol Condition Min Typ Max Unit
Restart Time Delay Tdly 100 200 - µs
UNDERVOLTAGE LOCKOUT (VCC Pin)
Item Symbol Condition Min Typ Max Unit
FA5500A 10 11.5 13 V
Startup Threshold Von FA5501A 11.5 13 14.5 V
Minimum Operating Voltage
After Turn-On Voff 8 9 10 V
FA5500A 1.8 2.5 3.2 V
Hysteresis Vhysvcc
FA5501A 3.3 4 4.7 V
TOTAL DEVICE (VCC Pin)
Item Symbol Condition Min Typ Max Unit
Power Supply Zener Voltage Vz Icc=25mA 30 33 36 V
Startup Power Supply Current Istart Vcc=8.0V - - 20 µA
Operating Power Supply
Current Icc Vcc=12V 1.0 2.0 mA
Dynamic Operating Power
Supply Current Iop 50kHz,CL=1.0nF 2.0 4.0 mA
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8. Characteristics curves
(Unless otherwise specified, Ta=25°C and Vcc=12V)
E rror ampl i fi er vol t age feedbac k i nput
t hres h old (Vfb) vs. s uppl y vol t age(V cc )
2.45
2.46
2.47
2.48
2.49
2.50
2.51
2.52
2.53
2.54
2.55
10 15 20 25 30
Vcc(V)
Vfb(V)
Overvol tage com parat or inpu t t hreshol d
(V thovp) vs. suppl y voltag e(V cc)
1.080
1.085
1.090
1.095
1.100
10 15 20 25 30
Vcc(V)
Vthovp(×Vfb(V))
E rror ampl i fi er t rans conduct ance(Gm ) and
phase vs. frequenc y(f)
0
20
40
60
80
100
120
1 10 100 1000 10000
f(kHz)
Gm(µmho)
0
30
60
90
120
150
180
Phase(deg)
Phase
Gm
RL=100kΩ
CL=10pF
E rror ampl i fi er vol t age feedbac k i nput
t hres h old (Vfb) vs. jun c t i on t em perature(Tj)
2.45
2.46
2.47
2.48
2.49
2.50
2.51
2.52
2.53
2.54
2.55
-50 0 50 100 150
Tj(°C)
Vfb(V)
Overvol tage com parat or inpu t t hreshol d
(V t hovp) vs. junct i on t em perat ure (Tj)
1.080
1.085
1.090
1.095
1.100
-50 0 50 100 150
Tj(°C)
Vthovp(×Vfb(V))
ZCD input hreshol d voltage (V thzcd) vs.
j unction tem p erat ure(Tj )
1.30
1.35
1.40
1.45
1.50
1.55
-50 0 50 100 150
Tj(°C)
Vthis(V)
Upper thr eshold
(Vin, inc r easing)
Lower thr eshold
(Vin, decr easing)
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FB short c om praor i nput t hreshol d(V t hsht) vs .
j unction tem p erat ure(Tj )
0.20
0.25
0.30
0.35
0.40
-50 0 50 100 150
Tj(°C)
Vthsht(V)
Current s ense c om parator t hershol d(V IS) vs.
MUL i nput vo ltage(V m ul )
-200
0
200
400
600
800
1000
1200
1400
1600
0.0 1.0 2.0 3.0 4.0
Vmul(V)
VIS(mV)
Vcom
p
=2.1V
Vcomp=2V
Vcom
p
=2.25
Vcom
p
=2.5
Vcom
p
=2.75V
Vcom
p
=3V
Vcom
p
=3.25V
Vcom
p
=4
Vcom
p
=3.5
Vcomp=1VVcomp=0V
Mult i plier gain(K ) vs .
j unction tem p erat ure(Tj )
0.4
0.5
0.6
0.7
0.8
0.9
1.0
-50 0 50 100 150
Tj(°C)
K
FB short com parator pul l down current(Ifb) vs .
j unction tem p erat ure(Tj )
2.40
2.45
2.50
2.55
2.60
2.65
-50 0 50 100 150
Tj(°C)
Ifb(µA)
Current sense c om parat or t hers hol d(V IS) vs.
M UL i nput vol tage(V mul ) (enl arged)
-100
-75
-50
-25
0
25
50
75
0.0 0.1 0.2 0.3 0.4
Vmul(V)
VIS(mV)
Vcom
p
=0
Vcomp=0.5
Vcom
p
=1
Vcomp=1.3
Vcom
p
=1.5
Vcom
p
=1.7
Vcomp=1.8
Vcom
=2
Vcom
p
=2.1
Vcomp=2.25
Vcomp=2.5V
Vcom
p
=3V
Vcomp=4V
Res tart t imer del ey ti m e(Tdl y) vs .
j unction tem p erat ure(Tj )
180
185
190
195
200
205
210
215
220
-50 0 50 100 150
Tj(°C)
Tdly(µs)
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Current s ense c om parator m ax i m um
t h res h ol d(V thi s) vs. suppl y voltage(V cc)
1.490
1.495
1.500
1.505
1.510
10 15 20 25 30
Vcc(V)
Vthis(V)
UV LO startup threshol d(V on ) vs.
j unction tem p erat ure(Tj )
10.0
10.5
11.0
11.5
12.0
12.5
13.0
-50 0 50 100 150
Tj(°C)
Von(V)
FA5500A
UV LO m i nim um operat i ng vol tage(V off) vs.
j unction tem p erat ure(Tj )
8.0
8.5
9.0
9.5
10.0
-50 0 50 100 150
Tj(°C)
Voff(V)
Current s ense c om parator m ax i m um
t h res h ol d(V thi s) vs. j uncti on tem perature(Tj)
1.495
1.500
1.505
1.510
1.515
1.520
1.525
-50 0 50 100 150
Tj(°C)
Vthis(V)
UV LO startup threshol d(V on ) vs.
j unction tem p erat ure(Tj )
11.0
11.5
12.0
12.5
13.0
13.5
14.0
-50 0 50 100 150
Tj(°C)
Von(V)
FA5501A
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OUT pin hi gh st ate vol t age(V O H) vs .
output current(Io)
0.0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
0 100 200 300
Io(mA)
Vcc-VOH(V)
Dy nami c operating power suppl y current (Iop)
vs . suppl y vol t ag e(V c c)
0
5
10
15
20
25
30
0 10203040
Vcc(V)
Iop(mA)
50kHz
CL=1nF
Operating power suppl y current(Icc) vs.
j unction tem p erat ure(Tj )
0.0
0.2
0.4
0.6
0.8
1.0
1.2
-50 0 50 100 150
Tj(°C)
Icc(mA)
OUTpi n low s tat e vol t a ge(V OL) vs.
output current(Io)
0
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
0 100 200 300
Io(mA)
VOL(V)
Dy nam ic operati ng power suppl y cu rrent (Iop)
vs. suppl y voltage(V cc) (enl arged)
0.0
0.5
1.0
1.5
2.0
2.5
579111315
Vcc(V)
Iop(mA)
50kHz
CL=1nF FA5500A FA5501A
Dy nami c operating power suppl y current (Iop)
vs . j unc ti on t em perat ure(Tj)
1.0
1.2
1.4
1.6
1.8
2.0
2.2
-50 0 50 100 150
Tj(°C)
Iop(mA)
50kHz
CL=1nF
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9. Description of PFC converter
FA5500A/FA5501A are control ICs for a power factor
correction converter using a boost type topology that
operates in critical conduction mode. The operations,
which are (1) Switching operation and (2) Power factor
correction operation, are described here with the circuit
shown in Fig. 1.
(1) Switching operation
This IC operates in critical conduction current mode
and does not use a fixed frequency oscillator for
switching operation. The waveform of each part in
switching operation in steady state is shown in Fig. 2.
The operation is described in detail below:
t1. When Q1 turns on, the inductor current (IL1) rises
from zero.
t2. When the inductor current reaches up to the
threshold of the current comparator (CUR.comp.)
set by the multiplier (MUL), CUR.comp. resets R-S
flip-flop and then Q1 turns off. When Q1 is off, the
voltage of L1 reverses polarity and the L1 current
(IL1) decreases supplying a current through D1 to
the output. During this period, the voltage of the
auxiliary winding (Vsub) also reverses polarity, then
the positive voltage occurs.
t3. When IL1 reaches zero, the voltage of L1 drops
rapidly. At the same time, Vsub also drops rapidly.
t4. When Vsub drops below 1.33V (the threshold of
ZCD. comp.), the output of zero current detector
(ZCD. comp.) turns to low and sets R-S flip-flop.
Then Q1 turns on, and the next switching cycle
starts. (Back to t1)
By repeating the steps from t1 to t4, the switching
operation co ntin ues in critic al cond uct ion mode.
In the PFC converter that operates in critical
conduction mode, the switching frequency always
changes according to the instantaneous AC line
voltage. In addition, the switching frequency also
changes when the AC line voltage or the load changes.
OUT
(Q1 gate)
Q1
Vds
I
L1
I
Q1
I
D1
CUR.comp.
output
(reset)
Vsub
ZCD.comp.
output
(set)
t1 t2 t3 t4
Fig.2 Timing chart of switching operation
AC
Iin I
L1
L1
C1 Q1 Vds
Rs
D1
Vsub
5 4
3
7
2
1
OUT
FB
2.5V
ERRAMP
COMP
ZCD.comp
CUR.comp R
S
Q
MUL
ZCD IS
1.5V/1.33V
Vo
MUL
FA5500A/01A
C3
Fig.1 Outline of PFC converter circuit
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(2) Power factor correction operation
As described in “(1) Switching operation”, inductor
current is repeated triangular waveform. The average
current (IL1(mean)) of this repeated triangular waveform
is one half of the peak current (IL1(peak)).
Then, the inductor peak current is controlled to be
sinusoidal and the high frequency content of inductor
current is filtered. As a result, it is possible to force the
AC input current into sinusoidal waveform.
enlarged
IL1
IL1(peak)
IL1(mean)
=1/2×IL1(peak)
IL1
Iin
2×Iin(peak)
Iin(peak)
filtered the high
frequency content
by C1
Fig.3 Outline of inductor and AC input current
In an actual circuit, the internal multiplier (MUL)
controls the inductor peak current as sinusoidal
waveform.
The voltage of COMP pin, which is the output of error
amplifier (ERRAMP), is almost DC voltage in steady
state by C3. This voltage is input to the multiplier. The
other input of multiplier monitors the rectified waveform
of AC line voltage. As a result, the multiplier outputs the
sinusoidal waveform that is proportional to AC line
voltage as the product of two input voltages.
This sinusoidal voltage is input to the current
comparator (CUR. comp.) as the threshold of inductor
current.
As a result, the inductor current becomes repeated
triangular waveform of which peak current envelope is
sinusoidal. The switching ripple of inductor current is
then filtered by C1 and AC input current becomes
sinusoidal waveform.
AC
L1
C1 Q1
Rs
4
3
2
1FB
ERRAMP
COMP
CUR.comp
MUL
IS
MUL
t
V
t
V
t
V
t
V
t
I
C3
sinusoidal
sinusoidal
Fig.4 Outline of waveform of each part
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10. Description of each circuit
(1) Error amplifier
The error amplifier controls the output voltage of PFC
converter to be constant. The amplifier is a
transconductance type, which has controlled
voltage-to-cu rrent gai n.
The non-inverting input is internally connected to the
reference voltage of 2.5 V (typ.) and the inverting input
is pinned out to FB pin. The output of PFC converter is
divided down by resistor and monitored by the FB pin.
In addition, 2.5µA of constant-current source is
internally connected to the FB pin for “Open/short
protection at FB pin”.
The output of error amplifier is connected to the
multiplier. According to the dynamic range of multiplier,
the output voltage of error amplifier ranges from 2.04 V
to 3.54 V (typ.) in normal operation. The lower output
voltage of error amplifier is limited by a diode
connected between the input and the output of error
amplifier, in order to prevent over drop in a transient
condition such as rapid change of the load.
The output voltage of PFC converter contains low
frequency ripple voltage associated with 2X the line
frequency. If too much ripples appear at error amplifier.
output, the PFC converter does not operate stable.
Therefore, a capacitor is connected between COMP
pin (the error amplifier output) and GND so that the
cutoff frequency is set to about 20Hz in order to
suppress the ripple voltage.
2
1
7
COMP
C3
ERRAMP
VREF
=2.5V(typ.) 2.5µA
FB
MUL
1.09VREF
OVP
SP
0.3V
OUT
R2
R1
Vo
Fig.5 Error amplifier circuit
(2) Overvoltage limiting circuit
This circuit prevents the PFC output voltage
exceeding the programmed voltage. The output voltage
may exceed the voltage programmed by error amplifier
when the converter starts up or the load changes
rappidly. This circuit limits rise of the output voltage in
such cases.
As shown in Fig. 5, the overvoltage limiting circuit
consists of a comparator (OVP) with threshold voltage,
which is set to 1.09 times of the reference voltage
(VREF).
In normal operation the FB pin voltage is
approximately 2.5 V, roughly the same as the reference
voltage VREF. If the PFC output voltage rises more
than normal voltage and then the FB pin voltage
reaches the threshold of OVP comparator, the output of
the comparator (OVP) turns to low and stops output
pulses.
When the output voltage comes back to normal,
output pulses appear again.
(3) Open/s hort protection at FB pin circuit
In the circuit shown in Fig. 6, if FB pin cannot monitor
the PFC output voltage because of a short-circuit
failure in voltage dividing resistor R2 or an open failure
in R1, the PFC output voltage abnormally rises. The
overvoltage limiting circuit does not operate either in
this case, becau se the output v oltage is not mon itore d.
To avoid these, this IC features a open/short
protection at FB pin circuit. This circuit consists of a
comparator (SP) with threshold voltage of 0.3V (typ.). If
the input voltage of FB pin drops below 0.3V due to a
short-circuit failure in R2 or an open failure in R1, the
output of comparator (SP) turns to low and stops the
output pulses.
In the PFC converter, because of a boost type
topology, the voltage rectified the AC line is supplied to
the PFC output even before the converter operates.
Therefore, if the PFC converter is normal, voltage is
always applied to FB pin and this protection circuit
does not operate.
If an open failure occurs between FB pin and the
voltage divider, the FB pin voltage is forced to lower by
the 2.5µA of constant current source internally
connected to FB pin. Then comparator (SP) stops the
output pulses in the same way.
If the FB pin voltage comes back to normal after this
protection circuit operates, output pulses appear again.
7
1
OUT
FB
2.5µA
0.3V
SP
VFB=0V
R2
R1
Vo
open
short
detect
shutdown
Fig.6 Open/short protection at FB pin
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(4) Multiplier
The multiplier is a circuit to control input current into
sinusoidal waveform.
One of the inputs is connected to MUL pin. The
rectified AC line voltage is divided down by resistor and
monitored by MUL pin. The other input is internally
connected to the output of error amplifier. Typically, the
output of error amplifier is almost DC over a given AC
line cycle. Therefore, the multiplier outputs the
sinusoidal voltage of which amplitude changes in
proportion to the output of error amplifier. This output
becomes the threshold of current comparator and the
AC input current is controlled into sinusoidal waveform.
Based on the dynamic range of multiplier, the peak
voltage applied to MUL pin should be within 2.5 V in
normal operation.
The rectified AC line voltage contains much
switching noises from Q1. To avoid the influence of the
noises, a capacitor (C6) is connected for a filter.
3MUL
CUR.comp
ERRAMP
MUL
R4
R3
L1
C1 Q1
D1
AC
C6
C2
Fig.7 Multiplier circuit
(5) Current sense comparator
One of the inputs is internally connected to the
output of multiplier as the threshold. The other input is
connected to IS pin to monitor the MOSFET source
current converted to voltage by current sense resistor
(Rs). In each switching cycle, when MOSFET current
reaches up to the threshold determined by the
multiplier, the output of current comparator turns high
and reset the RS flip-flop. As a result, MOSFET turns
off, and the on cycle of MOSFET is over.
The threshold voltage of current comparator is
internally clamped to 1.8V (max.). Therefore, when
PFC starts up or load and input voltage changes rapidly,
the maximum current of MOSFET is limited at the value
calculated with the following equation:
Rs
1.8
.)Id(max =
To prevent malfunction by noises, RC filter is typically
connected between IS pin and the current sense
resistor Rs.
4
L1 D1
C1 Q1 C2
Rs
R6
C4
IS
MUL 1.8V
(max)
CUR.comp
ZCD.comp
R
S
QOutput
circuit
Fig.8 Current sense comparator circuit
(6) Zero current detector
This IC operates in critical conduction current mode
without a fixed frequency oscillator. The zero current
detector circuit (ZCD) detects the inductor current
reaches zero to turn the MOSFET on at the next
switching cycle.
The voltage of auxiliary winding (sub) is monitored by
ZCD pin as shown in Fig. 9. During OFF period of
MOSFET, positive voltage occurs in the auxiliary
winding. When the inductor current reaches zero, the
voltage of auxiliary winding falls rapidly. ZCD.comp.
detects it and sets the RS flip-flop to turn the MOSFET
on at the next switching cycle.
The voltage of auxiliary winding varies significantly
according to input and output voltage. To protect the IC
against the various voltages, a clamp circuit is built in
with the upper limit of 7.6V(typ.) and the lower limit of
0.6V(typ.).
R
S
Q
Clamp
5
L1 D1
sub Q1
Rs
R5
ZCD
ZCD.comp
1.33/1.5V
C1
Clamp circuit
Fig.9 ZCD circuit
A resistor for current limit is typically connected
between the ZCD pin and the auxiliary winding
because of rating current of ZCD pin.
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A current out of or into the ZCD pin should be
within 3mA so that the IC will operate normally.
On the other hand, if the current out of or into the
ZCD pin is too small, unstable operation may occur.
Therefore, current limiting resistor of R5 should be
below 47kΩ.
While MOSFET is on, negative voltage is generated
in the auxiliary winding. A current flows out of the
clamp circuit and the ZCD pin voltage is clamped to
0.6V (typ.). While MOSFET is off, positive voltage is
generated in the auxiliary winding. A current flows into
the clamp circuit and the ZCD pin voltage is clamped to
7.6V (typ.).
Clamp
5
sub
R5
ZCD
ZCD.comp
0.6V
Q1 : ON
Clamp circuit
current
Fig.10 Clamp circuit of ZCD pin(1)
Clamp
5
sub
R5
ZCD
ZCD.comp
7.6V
Q1 : OFF
Clamp circuit
current
Fig.11 Clamp circuit of ZCD pin(2)
(7) Compensation circuit for light load
If the output of multiplier, which determines the
threshold of current comparator, does not have offset
voltage, the input current to the converter is
approximately zero under condition that the PFC
converter operates in no load. But an actual multiplier
may have offset voltage. If the offset voltage is positive,
the input current, which corresponds to the offset
voltage, flows into the converter even when the PFC
converter operates in no load. In this case, the PFC
output voltage rises abnormally because of too much
input current.
To avoid these, this IC has an automatic offset
correction circuit (AOC) for light load. The output
voltage of error amplifier is approximately 2V or higher
in normal operation. When the output voltage of error
amplifier drops below 2V, AOC circuit operates.
If the output of multiplier has a positive offset, the
output voltage of error amplifier falls below 2V in the
case that the PFC converter operates in no load or light
load. Then, the offset voltage is corrected in the current
comparator by AOC circuit. Because of this operation,
even in the no load or light load condition, the PFC
output voltage does not rise abnormally, but is always
kept constant. The amount of correction changes
linearly according to the output of error amplifier so that
the operation can be made stable.
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Input current
full load
no load
AC input current
offset currnt
0t
1/2 of line frequency
without compensation
result of compensattion
0
with compensation
AC input current
full load
no load
1/2 of line frequency t
Output voltage
0
PFC output voltage
PFC output power
without compensation
with compensation
Fig.12 Outline of operation when multiplier has a
positive offset
(8) Restart timer
In steady state, set signals from the ZCD circuit turns
MOSFET on at each switching cycles. But a trigger
signal is needed when starting up or stabilizing
operation in the light load condition. This IC includes a
restart timer. If off period of output pulse continues
200µs or more, it automatically generates a trigger
signal.
(9) Undervoltage lockout circuit
These IC contain an undervoltage lockout circuit to
prevent malfunction when the supply voltage drops.
W hen th e sup ply vo ltag e ris es f rom 0 V, FA55 00A st ar ts
operation at 11.5V(typ.) and FA5501A starts operation
at 13V(typ.). If the supply voltage drops after the IC
starts up, both IC stops operation at 9V(typ.). W hen IC
stops operation by undervoltage lock out circuit, OUT
pin voltage is kept in low state and the current
consumption of IC decreases below 20µA.
(10)Output circuit
This IC contains a push-pull output stage and can
directly drive the MOSFET. The peak current of output
stage is sink: 1.0A (max.), source: 0.5A (max.)
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11. Design advice
(1) Designing a PFC converter
The following description is a sample of designing of
a PFC converter with FA5500A/FA5501A using a circuit
shown in Fig. 13. However, this is just a sample of
calculating. If you want to use the components or
circuits calculated in this process, be sure to test and
determine in actual circuit. In addition, be sure to
consider and check the characteristics, the tolerance
and the rating of each component including this IC.
(1-1) Specification of PFC converter
To begin designing, the following specification of PFC
converter is determined.
Input voltage range (Vrms): Vac(min.) to Vac(max.)
Output voltage (V): Vo (> 2 ×Vac (max.) )
Maximum Output power(W ): Po
Output voltage (Vo) should be set higher than the
peak value of input voltage (= 2×Vac (max.)) because
the PFC converter is a boost type topology.
(1-2) Designing inductance of L1
The switching frequencies are determined with
input-output conditions and the value of inductor
because PFC converter operates in critical conduction
mode (see Supplement). Therefore, the value of
inductor L1 (Lp) can be determined with input-output
conditions and the minimum operating fr equ ency.
When efficiency of PFC is η and the minimum
operating frequency is fsw (min.), Lp is calculated by
following equ atio n.
Lp= VoPofsw2 )Vac2(VoVac
.)(min
.)(min
2
.)(min ××× η××−×
It is recommended to set fsw(min) between
20kHz-100kHz. Assume that the efficiency η is
approximate ly 90% in calcul ati ng.
Supplement: Inductance and switching frequencies
On and off period of each switching cycle can be
calculated with the following equation.
η×
××
=2
Vac PoLp2
Ton
−
ω××
×η×
××
=
1
tnsiVac2 Vo
Vac
PoLp2
Toff
2
where,
ω=2×π×fac
fac: AC line frequency (Hz)
In theory, according to the equation above, if
input-output conditions are constant, Ton is also
constant. On the other hand, Toff changes
corresponding to each instantaneous voltage of AC line,
maximum at ωt =90°, minimum at ωt =0°. Then,
switching frequencies can be calculated with the
following equation according to the relationships
described above:
(
)
VoPoLp2 tnsiVac2VoVac
fsw 2
××× η×ω××−×
=
The switching frequencies always change
corresponding to each instantaneous voltage of AC line.
Vac C1
L1 Np
Ns
R3 R6 R7 D2 R5 R8
FA5500A/01A
FB
COMP OUT
VCC
MUL GND
IS ZCD
C4
R4C6C3 C5
Rs
Q1
D1
C2 R1
R2
Po
Vo
Fig.13 Typical application circuit
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(1-3) Designing auxiliary winding of L1
The auxiliary winding typically has two functions:
-Detecting that inductor current reaches zero
-Supplying Vcc voltage of IC
To achieve these functions, you have to determine a
proper ratio of it to the main winding.
The voltage of auxiliary winding always changes
according to each instantaneous voltage of AC line. The
outline of the auxiliary winding voltage is shown in Fig.
14.
auxilliary winding
voltage
Np
Ns
)Vac2Vo( ××−
Np
Ns
Vo×
Np
Ns
Vac2 ××
1/2 of line frequency
0
envelope
Fig.14 Auxiliary winding voltage
The following conditions should be satisfied based on
this various voltage.
ZCD Threshold Voltage
The threshold voltage of ZCD comparator is
1.87V(max.) when ZCD pin voltage rises. It is
necessary for the minimum voltage of auxiliary winding
to exceed this threshold voltage. Therefore, the
following con dit ion must be satisfied.
()
()
.max
Vac2Vo 1.87
Np/Ns ×−
>
Vcc voltage
The following condition must be satisfied, so that Vcc
voltage will be set between 12V and 28V according to
the recommended condition.
Vo
28
Ns/Np
Vo
12 <<
The turns ratio Ns/Np must satisfy both two condition.
If the boost voltage ratio of PFC (the ratio of Vo to
Vac) is too small, the turns ratio can not satisfy both
condition. This problem can be solved with following
methods.
-Attach two auxiliary windings for both ZCD and Vcc
respectively.
-Set ZCD condition preceding Vcc condition. In this
case, there is possibility for Vcc to exceed the
recommended conditions. Therefore, clamp the Vcc
with internal ZD or additional ZD (Fig. 15). In this
case, a resistance for current limit (R11) is needed
between the auxiliary winding and Vcc pin. In
addition, especially when using internal ZD, mind
that “Total power supply and zener current” and
“Power dissipation” must not exceed the absolute
maximum rating value.
D2
R11
C5 sub
VCC8
internal
ZD
using internal ZD
D2
R11
C5 sub
VCC8
external
ZD
using external ZD
Fig.15 Vcc clamp circuit
(1-4) ZCD pin circuit
The auxiliary winding voltage is monitored by ZCD
pin in order to detect that the inductor current reaches
zero. A resistor for current limit (R5) is connected
between ZCD pin and the auxiliary winding because of
rating current of ZCD pin. The most appropriate value of
R5 is determined by evaluating in the actual circuit.
However, a current out of or into the ZCD pin
should be within 3mA as shown in the recommended
operating conditions so that the IC will operate
normally. Therefore, the following conditions should
be satisfied.
For lower clamp
3
103 Np
Ns
.)Vac(max20.1
5R −
×
××+
>
For upper clamp
3
103
0.7
Np
Ns
Vo
5R −
×
−×
>
On the other hand, if the current out of or into the
ZCD pin is too small, unstable operation may occur.
Therefore, current limiting resistor of R5 should be
below 47kΩ.
Ω< k475R
5ZCD
R5
L1 D1
Q1
Rs
Fig.16 ZCD pin circuit
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In actual circuit, the value of R5 also influences
MOSFET switching.
MOSFET(Q1) turns on when the current of inductor
L1 reaches zero. Just before turning on, the drain
voltage of MOSFET (Vds) begins sinusoidal oscillation
because of resonance of L1 and the parasitic capacitor.
If the value of R5 is set properly, MOSFET can be
turned on at the bottom of the voltage oscillation. This
can minimize the switching loss and surge current at
turn on. If the value of R5 is too small, MOSFET turns
on too early and if it is too large MOSFET turns on too
late. The adequate value of R5 depends on each
circuits or input and output conditions. Therefore,
determine the most appropriate value by evaluating the
operation in the actual circuit.
t
Vds
0
Fig.17 Vds waveform at turn on
(with adequate R5)
t
Vds
0t
Vds
0
R5 is too small. R5 is too large.
Fig.18 Vds waveform at turn on
(with inadequate R5)
(1-5) Vcc Pin circuit
The startup resistor R7 should satisfy the following
formula in order to supply with at least 20µA of IC
startup current.
6
1020 .)(maxVon.)Vac(min2
7R −
×−×
<
Where,
Von(max.): maximum voltage of startup threshold of
UVLO
FA5500A: Von(max.)=13V
FA5501A: Von(max.)=14.5V
This formula is, however, just the minimum condition
to start the IC. The startup time required for PFC
converter must also be decided on. The value of R7
should be tested and determined in actual circuit for
appropriate startup time.
8
L1
D2
R7
C1
VCC C5
Fig.19 Vcc pin circuit
In steady state, Vcc is supplied from the auxiliary
winding of inductor. When the IC is just starting up,
however, it takes time for the voltage from auxiliary
winding to rise enough. The value of capacitor C5
connected to Vcc pin should be determined to prevent
Vcc from falling below the UVLO threshold voltage
during the this period. The capacity of C5 should be
tested and determined in the actual circuit because the
time lag is different in each circuit.
UVLO
ON
UVLO
OFF
Auxiliary winding voltage
Vcc
Time t
Vcc must not drop
below UVLO OFF.
Fig.20 Vcc voltage at startup
Even after PFC starts up, Vcc may fall due to rapidly
changes of the load or inputs. To prevent the IC from
stopping in those cases, the circuit shown in Fig.21 is
effective to prolong the hold time of the Vcc voltage.
After the PFC converter starts up, Vcc is supplied
through C7. Therefore, you can prolong the hold time of
Vcc by using a large capacity for C7.
R7
D2 D3
C5 C7 sub
VCC
Fig.21 Vcc pin circuit (2)
In some case, the Vcc voltage cannot be supplied
enough in light load condition. In this case, the circuit
shown in Fig.22 may be effective to improve the Vcc. In
this circuit, R10 suppress the surge current of MOSFET
at turn on to prevent the malfunctions. (See (1-7) IS pin
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circuit ) The appropriate value of C8 and R10 should be
tested and determined in actual circuit because they
depend on each circuit.
R7
D2
D4
C5
C8
sub
VCC R10
Fig.22 Vcc pin circuit (3)
(1-6) MUL Pin circuit
The input voltage of MUL pin is related to IS pin
threshold voltage range. To prevent the distortion of AC
input current, the value of resistor divider R3 and R4
should be determined so that the maximum peak
voltage of MUL pin (VMUL-P(max)) is below 2.5V when
the AC line voltage is maximum.
2.5[V] 4R3R 4R
Vac(max)2V (max)PMUL
<+
××=
−
3
C1
R3
R4
C6
MUL
Fig.23 MUL pin circuit
In an actual circuit, the rectified voltage contains
many noises from switching. To avoid this influence, a
capacitor C6 is typically connected between MUL pin
and GND pin. If the capacity of C6 is too small, the
filtering is not effective. If the capacity is too large, the
input voltage of MUL pin is distorted and then AC input
current is also distorted. In calculating, the cutoff
frequencies determined with C6 and R3, R4 should be
set to about 1 or 2kHz.
2[kHz]or1
4)//R3(R6C2 1≈
××π×
Where;
R3//R4 represents the resistance of parallel
connect ion of R3 and R4.
(1-7) IS Pin circuit
The input current becomes the greatest when AC line
voltage is minimum (Vac(min.)). Even in this case, it is
necessary to set the current detector resistance Rs so
that required input current can be supplied.
After setting a voltage divider connected to MUL pin,
the threshold voltage range of IS pin is calculated as
follows.
When AC line voltage is minimum, the minimum
clamp voltage of IS pin thresh old volt age
(VthIS-P(min)) can be calculated according to the
characteristics of multiplier and the input voltage range.
()()()
1V53.0 V1VVK
V
(min)PMUL
thcompthcomp(min)PMUL(min)
(min)pthIS
××= −+××=
−
−
−
Where,
VMUL-P(min): MUL pin peak voltage at minimum AC
line voltage
K(min.): multiplier gain
Note:
When VthIS-P(min) >1.3V, use VthIS-P(min) =1.3V.
Set the current sense resistance Rs in order to flow
necessary current even when clamp voltage is
VthIS-P(min). The maximum of the inductor peak current
(ILP(max.)) is approximately expressed with the following
equation.
.)Vac(min
Po22
.)(maxILP ×η ××
=
Therefore, the value of Rs can be calculated with the
following equ atio n.
.)(maxI
V
Rs LP
(min)pthIS−
=
When MOSFET turns on, surge current caused by
driving MOSFET or discharging of parasitic capacitor
flows to Rs. This IC controls the peak current of
MOSFET. Therefore if this surge current is too large,
the AC input current can be distorted by malfunctions.
In addition, depending on the magnitude or timing of
surge current, irregular narrow pulses may appear on
the output pulses when OUT pin goes high. Therefore,
a RC filter R6 and C4 is typically connected. In order
not to influence normal operation, it is necessary to set
the cutoff frequency of RC filter higher than the
switching frequency. In this calculation, the cutoff
frequency is assumed about 1 or 2 MHz.
]MHz[2or1
6R4C2 1≈
××π×
4
L1 D1
C1 Q1 C2
Rs
R6
C4
IS
Fig.24 IS pin circuit
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If the effect of RC filter is not enough, connect OUT
pin and MOSFET as shown in Fig. 25 in order to reduce
driving current to turn the MOSFET on. In this circuit,
drive currents to turn the MOSFET on and off can be
set independently.
OUT7R8 R9
Rs
or
OUT7R8
R9 Rs
Fig.25 Gate drive circuit
The inductor current reaches zero just before the
MOSFET turns on and MOSFET current rises from
around zero when MOSFET is on. Therefore, even if
the driving current to turn on is set small and the
switching speed becomes a little slow, the loss of
MOSFET does not increase extremely.
(1-8) Input/output of error amplifier
PFC output voltage Vo is divided down and input to
FB pin. Vo is controlled so that the FB pin voltage is
equal to the internal reference. This IC has a current
source (IFB) of 2.5µA(typ.) connected FB pin internally.
Therefore, the relationship between Vo and the voltage
divider resistor can be expressed with the following
equation.
amplifiererrorofcetancTranscondu:Gm,where
I1R
Gm
I
Vref
2R 2R1R
Vo FB
FB ×+
+×
+
=
PFC output voltage contains ripple voltage
associated with twice the line frequency. If this ripple
voltage appears at the output of error amplifier, PFC
does not operate stably. To avoid this, a capacitor
should be inserted between COMP pin and GND so
that the bandwidth is set to about 20Hz. The bandwidth
can be expressed with the following equation.
3C2 Gm
BW ×π×
=
1
2
MUL
ERRAMP
Vref
=2.5V(typ) =2.5µA
I
FB
COMP
C3
FB
R1
R2
Vo
(typ)
Fig.26 Input/output of error amplifier circuit
(1-9) Input/output capacitor
The input capacitor C1 rejects the switching ripples of
inductor current and prevents it from flowing to AC line.
Therefore, the larger C1 is, the smaller the switching
ripples contained in AC input current are. But larger C1
may causes of lowering power factor.
In calculation, capacity of C1 is assumed as 1µF per
1A of maximum AC input current. The most appropriate
capacity should be determined by evaluating power
factor and AC line noises in the actual circuit.
switching
ripple current L1
Q1
Rs
C1
D1
C2
Fig.27 Input capacitor circuit
PFC output contains ripple voltage of twice the line
frequency. The output capacitor C2 suppresses this
ripple voltage.
The ripple voltage appearing on the output voltage
can be expressed by the following equation.
2C2 oI
Vp)ripple(0 ×ω×
≈
−
where, fac2 ×π×=ω
fac: AC line frequency [Hz]
If the output voltage including ripple voltage reaches
up to the overvoltage threshold, the IC cannot operate
properly. Therefore, C2 should be selected satisfying
the following equation.
V
ripple(0-p)<0.075×Vo
2×fac
V
ripple(0-p)
Vo
Fig.28 Output ripple voltage
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(2) Improving operation around
zero-crossing
The dead time of AC input current may appear
around zero crossing. A high value resistor R12
(several 100k or several MegΩ) connected between
MUL pin and Vcc pin may reduce the dead time. But too
much correction, which means connecting too small
resistance, causes distortion of AC input current or
overvoltage at light load. Be careful when R12 is
connected.
0t
Iin
Fig.29 Input current including dead time
3
C1 R3
R4
C6 MUL
8
VCC
R12
Fig.30 Compensation circuit of dead time
On the other hand, surge current may appear around
zero crossing in some application.
This surge current can influence harmonic currents. In
this case, a high value resistor R13 (several 100k or
several MegΩ) connected between IS pin and Vcc pin
may suppress this surge current.
0
Fig.31 Input current including surge current
4
L1 D1
C1 Q1 C2
Rs
R6
C4
IS
8
VCC R13
Fig.32 Compensation circuit of surge current
(3) Prevent malfunction caused by negative
voltage applied to a pin
When large negative voltage is applied to each IC pin,
a parasitic element in the IC may operate and cause
malfunction. Be careful not to allow the voltage applied
to each pin to drop below -0.3V. Especially for the OUT
pin, voltage oscillation caused after the MOSFET turns
off may be applied to the OUT pin via the parasitic
capacitance of the MOSFET, causing the negative
voltage to be applied to the OUT pin. If the voltage falls
below -0.3V, add a Schottky diode between the OUT
pin and the ground. The forward voltage of the Schottky
diode can suppress the voltage applied to the OUT pin.
Use the low forward voltage of the Schottky diode.
OUT
SBD
7R8
Rs
Fig.33 Protection circuit of OU T pin against the
negative voltage
Similarly, be careful not to cause the voltages at other
pins to fall below -0.3V.
(4) Prevent malfunction caused by noise
Noise applied to each pin may causes malfunction of
IC. Capacitor of RC filter for IS pin and MUL pin should
be connected as close as possible to suppress noise
effectively.
Noise applied to COMP pin may also cause
malfunction. The capacitor between COMP and GND
pin should be connected as close as possible, too.
(5) Open/ short protection at FB pin
This IC has Open/short protection at FB pin circuit,
which shuts off output, if complete open circuit or short
circuit failures may occur on voltage divider for
monitoring PFC output voltage. But, if voltage divider
resistance varies because of degradation, this circuit
may not protect enough. Therefore, be sure to consider
and evaluate your set, component characteristics and
the like sufficiently, and then design an additional
protection circuit if needed.
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(6) ON/OFF operation by external signal
The following methods make it possible to turn on or
off the PFC by external signal.
(i) Shut down supply voltage to Vcc pin
To shut down supply voltage to Vcc pin by external
signals leads IC’s shut down.
(ii) Lower COMP pin voltage below Vthcomp
It can stop the output pulses to lower COMP pin
voltage below Vthcomp. In this case, lower COMP pin
voltage below 1V, considering temperature
characteristic and so on. An example circuit is shown
in Fig. 34.
ON/OFF
signal
R16
R17
2
COMP
Q3
C3
Fig.34 ON/OFF control circuit (1)
If the discharging current of capacitor C3 should be
limited, connect a resistor R19 as shown in Fig. 35.
The value of R19 should be selected 1kΩ or smaller.
In addition, check that COMP pin voltage is lowered
below 1V.
R19
ON/OFF
signal
R16
R17
2
COMP
Q3
C3
Fig.35 ON/OFF control circuit (2)
When lowering COMP pin voltage, in addition to the
output current of error amplifier, current, which flows
voltage divider connected FB pin, appears at COMP
pin through diode connected between input and output
of error amplifier. When designing and evaluating the
circuit, consider this current sufficiently, too. (See 10.
Description of Each Circuit (1) Error amplifier)
Do not use “Open/short protection at FB pin” as
ON/OFF control by lowering FB pin voltage. In this case,
there is a possibility of an abnormal rise of PFC output
voltage at the turning on and off.
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12. Example of application circuit
80 to 264Vac
3A
0.22µF
2200pF
0.22µF 2200pF
5D11
600V4A
0.47µF
390µH ERC25-06
2SK3520
47k
0.1
ERA91-02
220
22
100k
100k
33
680k
680k
47k
5.6
0.1µF
ERA91-02
ERA91-02
100µF
FA5501A
2200pF
0.01µF
9.1k
0.47µF
100µF
680k
470k
470k
10k
410V
100W
FB
COMP
MUL
IS
VCC
OUT
GND
ZCD
Note
This application circuit exemplifies the use of IC for your reference only. Parts tolerance, parts characteristics,
influence of noise, etc. are not defined in this application circuit. W hen design an actual circuit for a product, you must
determine parts tolerance, parts characteristics, influence of noise, etc. for safe and economical operation. Neither Fuji
nor its agents shall be liable for any injury caused by any use of this circuit.
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