0 1 2 3 3.5
-20
-15
-10
-5
0
5
INPUT BIAS (fA)
VCM (V)
V+ = 5V
V- = 0V
TA = 25°C
1.50.5 2.5
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LMP7721
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LMP7721 3-Femtoampere Input Bias Current Precision Amplifier
1 Features 3 Description
The LMP7721 is the industry’s lowest specified input
1• Unless Otherwise Noted, Typical Values at TA=bias current precision amplifier. The ultra-low input
25°C, VS= 5 V. bias current is 3 fA, with a specified limit of ±20 fA at
• Input Bias Current (VCM = 1 V) 25°C and ±900 fA at 85°C. This is achieved with the
– Maximum at 25°C ±20 fA latest patent-pending technology of input bias current
cancellation amplifier circuitry. This technology also
– Maximum at 85°C ±900 fA maintains the ultra-low input bias current over the
• Offset Voltage ±26 µV entire input common-mode voltage range of the
• Offset Voltage Drift −1.5 μV/°C amplifier.
• DC Open-Loop Gain 120 dB Other outstanding features, such as low voltage noise
• DC CMRR 100 dB (6.5 nV/√Hz), low DC-offset voltage (±150 µV
maximum at 25°C) and low-offset voltage
• Input Voltage Noise (at f = 1 kHz) 6.5 nV/√Hz temperature coefficient (−1.5 µV/°C), improve system
• THD 0.0007% sensitivity and accuracy in high-precision
• Supply Current 1.3 mA applications. With a supply voltage range of 1.8 V to
5.5 V, the LMP7721 is the ideal choice for battery-
• GBW 17 MHz operated, portable applications. The LMP7721 is part
• Slew Rate (Falling Edge) 12.76 V/μsof the LMP™ precision amplifier family.
• Supply Voltage 1.8 V to 5.5 V As part of Texas Instruments' PowerWise™ products,
• Operating Temperature Range −40°C to 125°C the LMP7721 provides the remarkably wide-gain
• 8-Pin SOIC bandwidth product (GBW) of 17 MHz while
consuming only 1.3 mA of current. This wide GBW
2 Applications along with the high open-loop gain of 120 dB enables
accurate signal conditioning. With these
• Photodiode Amplifier specifications, the LMP7721 has the performance to
• High Impedance Sensor Amplifier excel in a wide variety of applications such as
• Ion Chamber Amplifier electrochemical cell amplifiers and sensor interface
circuits.
• Electrometer Amplifier
• pH Electrode Amplifier The LMP7721 is offered in an 8-pin SOIC package
with a special pinout that isolates the amplifier’s input
• Transimpedance Amplifier from the power supply and output pins. With proper
board layout techniques, the unique pinout of the
Ultra-Low Input Bias Current LMP7721 will prevent PCB leakage current from
reaching the input pins. Thus system error will be
further reduced.
Device Information(1)
PART NUMBER PACKAGE BODY SIZE (NOM)
LMP7721 SOIC (8) 4.90 mm × 3.90 mm
(1) For all available packages, see the orderable addendum at
the end of the datasheet.
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
LMP7721
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Table of Contents
7.3 Feature Description................................................. 16
1 Features.................................................................. 17.4 Device Functional Modes........................................ 17
2 Applications ........................................................... 18 Application and Implementation ........................ 20
3 Description............................................................. 18.1 Application Information............................................ 20
4 Revision History..................................................... 28.2 Typical Application ................................................. 22
5 Pin Configuration and Functions......................... 39 Power Supply Recommendations...................... 25
6 Specifications......................................................... 410 Layout................................................................... 25
6.1 Absolute Maximum Ratings ...................................... 410.1 Layout Guidelines ................................................. 25
6.2 ESD Ratings.............................................................. 410.2 Layout Example .................................................... 25
6.3 Recommended Operating Conditions....................... 411 Device and Documentation Support................. 26
6.4 Thermal Information.................................................. 411.1 Device Support...................................................... 26
6.5 Electrical Characteristics: 2.5 V................................ 511.2 Documentation Support ........................................ 26
6.6 Electrical Characteristics: 5 V................................... 611.3 Trademarks........................................................... 26
6.7 Typical Characteristics.............................................. 811.4 Electrostatic Discharge Caution............................ 26
7 Detailed Description............................................ 16 11.5 Glossary................................................................ 26
7.1 Overview................................................................. 16 12 Mechanical, Packaging, and Orderable
7.2 Functional Block Diagram....................................... 16 Information........................................................... 26
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision D (March 2013) to Revision E Page
• Added Pin Configuration and Functions section, ESD Ratings table, Feature Description section, Device Functional
Modes,Application and Implementation section, Power Supply Recommendations section, Layout section, Device
and Documentation Support section, and Mechanical, Packaging, and Orderable Information section .............................. 1
Changes from Revision C (March 2013) to Revision D Page
• Changed layout of National Data Sheet to TI format ........................................................................................................... 25
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N/C
1
2
3
4 5
6
7
8
IN+
N/C
V-
N/C
IN-
V+
VOUT
+
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5 Pin Configuration and Functions
8-Pin
SOIC Package
Top View
Note: Non-standard single pinout. Substitutions may require a new layout.
Pin Functions
PIN I/O DESCRIPTION
NAME NO.
IN+ 1 I Non-Inverting Input
N/C 2 - No Internal Connection (1)
V- 3 P Negative Power Supply
VOUT 4 O Output
N/C 5 - No Internal Connection
V+ 6 P Positive Power Supply
N/C 7 - No Internal Connection (1)
IN- 8 I Inverting Input
(1) Recommeded to connect to system guard trace.
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6 Specifications
6.1 Absolute Maximum Ratings(1)(2)
MIN MAX UNIT
VIN Differential –0.3 0.3 V
Supply Voltage (VS= V+– V−)(3) –0.3 6.0 V
Voltage on Input/Output Pins V++ 0.3 V−−0.3 V
Junction Temperature (4) 150 °C
Soldering Information
Infrared or Convection (20 sec) 235 °C
Wave Soldering Lead Temp. (10 sec) 260 °C
Storage temperature, Tstg −65 150 °C
(1) Absolute Maximum Ratings(1)(2) indicate limits beyond which damage to the device may occur. Recommended Operating Conditions
indicate conditions for which the device is intended to be functional, but specific performance is not ensured. For ensured specifications
and the test conditions, see the Electrical Characteristics Tables.
(2) If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/Distributors for availability and
specifications.
(3) The voltage on any pin should not exceed 6V relative to any other pins.
(4) The maximum power dissipation is a function of TJ(MAX),θJA. The maximum allowable power dissipation at any ambient temperature is
PD= (TJ(MAX) - TA)/θJA. All numbers apply for packages soldered directly onto a PC Board.
6.2 ESD Ratings VALUE UNIT
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001(1) ±2000
V(ESD) Electrostatic discharge V
Charged-device model (CDM), per JEDEC specification JESD22- ±200
C101(2)
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions MIN MAX UNIT
Temperature Range(1) –40 125 °C
Supply Voltage (VS= V+– V−):
0°C ≤TA≤125°C 1.8 5.5 V
−40°C ≤TA≤125°C 2.0 5.5 V
(1) The maximum power dissipation is a function of TJ(MAX),θJA. The maximum allowable power dissipation at any ambient temperature is
PD= (TJ(MAX) - TA)/θJA. All numbers apply for packages soldered directly onto a PC Board.
6.4 Thermal Information LMP7721
THERMAL METRIC(1) D UNIT
8 PINS
RθJA Junction-to-ambient thermal resistance 190 °C/W
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
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6.5 Electrical Characteristics: 2.5 V
Unless otherwise specified, all limits are specified for TA= 25°C, V+= 2.5 V, V−= 0 V, VCM = (V++ V−)/2.
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
VOS Input Offset Voltage –180 ±50 180 μV
–40°C ≤TJ≤125°C –480 480
TC VOS Input Offset Voltage Drift –1.5 –4 μV/°C
(3)
IBIAS Input Bias Current VCM = 1 V(4) (5) 25°C –20 ±3 20 fA
−40°C to 85°C –900 900
−40°C to 125°C –5 5 pA
IOS Input Offset Current VCM = 1 V(5) ±6 ±40 fA
CMRR Common-Mode Rejection Ratio 0 V ≤VCM ≤1.4 V 83 100 dB
0 V ≤VCM ≤1.4 V, –40°C ≤TJ≤125°C 80
PSRR Power Supply Rejection Ratio 1.8 V ≤V+≤5.5 V, V−= 0 V, VCM = 0 84 92 dB
1.8 V ≤V+≤5.5 V, V−= 0 V, VCM = 0, 80
–40°C ≤TJ≤125°C
CMVR Input Common-Mode Voltage CMRR ≥80 dB −0.3 1.5 V
Range CMRR ≥78 dB, –40°C ≤TJ≤125°C –0.3 1.5
AVOL Large Signal Voltage Gain VO= 0.15 V to 2.2 V, RL= 2 kΩto V+/2 88 107
VO= 0.15 V to 2.2 V, RL= 2 kΩto V+/2, 82
–40°C ≤TJ≤125°C dB
VO= 0.15 V to 2.2 V, RL= 10 kΩto V+/2 92 120
VO= 0.15 V to 2.2 V, RL= 10 kΩto V+/2, 88
–40°C ≤TJ≤125°C
VOOutput Swing High RL= 2 kΩto V+/2 70 25
RL= 2 kΩto V+/2, –40°C ≤TJ≤125°C 77 mV
from V+
RL= 10 kΩto V+/2 60 20
RL= 10 kΩto V+/2, –40°C ≤TJ≤125°C 66
Output Swing Low RL= 2 kΩto V+/2 30 70
RL= 2 kΩto V+/2, –40°C ≤TJ≤125°C 73 mV
RL= 10 kΩto V+/2 15 60
RL= 10 kΩto V+/2, –40°C ≤TJ≤125°C 62
IOOutput Short Circuit Current Sourcing to V−, VIN = 200 mV (6) 36 46
Sourcing to V−, VIN = 200 mV (6), –40°C ≤30
TJ≤125°C mA
Sinking to V+, VIN =−200 mV (6) 7.5 15
Sinking to V+, VIN =−200 mV (6), –40°C ≤5.0
TJ≤125°C
ISSupply Current 1.1 1.5 mA
–40°C ≤TJ≤125°C 1.75
SR Slew Rate AV= +1, Rising (10% to 90%) 9.3 V/μs
AV= +1, Falling (90% to 10%) 10.8
GBW Gain Bandwidth Product 15 MHz
enInput-Referred Voltage Noise f = 400 Hz 8 nV/
f = 1 kHz 7
(1) Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlations using the
Statistical Quality Control (SQC) method.
(2) Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary
over time and will also depend on the application and configuration. The typical values are not tested and are not specified on shipped
production material.
(3) Offset voltage average drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change.
(4) Positive current corresponds to current flowing into the device.
(5) This parameter is specified by design and/or characterization and is not tested in production.
(6) The short circuit test is a momentary open loop test.
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Electrical Characteristics: 2.5 V (continued)
Unless otherwise specified, all limits are specified for TA= 25°C, V+= 2.5 V, V−= 0 V, VCM = (V++ V−)/2.
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
InInput-Referred Current Noise f = 1 kHz 0.01 pA/
THD+N Total Harmonic Distortion + f = 1 kHz, AV= 2, RL= 100 kΩ0.003%
Noise VO= 0.9 VPP
f = 1 kHz, AV= 2, RL= 600 Ω0.003%
VO= 0.9 VPP
6.6 Electrical Characteristics: 5 V
Unless otherwise specified, all limits are specified for TA= 25°C, V+= 5 V, V−= 0 V, VCM = (V++ V−)/2.
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
VOS Input Offset Voltage –150 ±26 150 μV
–40°C ≤TJ≤125°C 450 450
TC VOS Input Offset Average Drift –1.5 –4 μV/°C
(3)
IBIAS Input Bias Current VCM = 1 V(4) (5) 25°C –20 ±3 20 fA
−40°C to 85°C –900 900
−40°C to 125°C –5 5 pA
IOS Input Offset Current (5) ±6 ±40 fA
CMRR Common-Mode Rejection Ratio 0 V ≤VCM ≤3.7 V 84 100 dB
0 V ≤VCM ≤3.7 V, –40°C ≤TJ≤125°C 82
PSRR Power Supply Rejection Ratio 1.8 V ≤V+≤5.5 V, V−= 0 V, VCM = 0 84 96 dB
1.8 V ≤V+≤5.5 V, V−= 0 V, VCM = 0, 80
–40°C ≤TJ≤125°C
CMVR Input Common-Mode Voltage CMRR ≥80 dB −0.3 4 V
Range CMRR ≥78 dB, –40°C ≤TJ≤125°C –0.3 4
AVOL Large Signal Voltage Gain VO= 0.3 V to 4.7 V, RL= 2 kΩto V+/2 88 111
VO= 0.3 V to 4.7 V, RL= 2 kΩto V+/2, 82
–40°C ≤TJ≤125°C dB
VO= 0.3 V to 4.7 V, RL= 10 kΩto V+/2 92 120
VO= 0.3 V to 4.7 V, RL= 10 kΩto V+/2, 88
–40°C ≤TJ≤125°C
VOOutput Swing High RL= 2 kΩto V+/2 70 30
RL= 2 kΩto V+/2, –40°C ≤TJ≤125°C 77 mV
from V+
RL= 10 kΩto V+/2 60 20
RL= 10 kΩto V+/2, –40°C ≤TJ≤125°C 66
Output Swing Low RL= 2 kΩto V+/2 31 70
RL= 2 kΩto V+/2, –40°C ≤TJ≤125°C 73 mV
RL= 10 kΩto V+/2 20 60
RL= 10 kΩto V+/2, –40°C ≤TJ≤125°C 62
(1) Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlations using the
Statistical Quality Control (SQC) method.
(2) Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary
over time and will also depend on the application and configuration. The typical values are not tested and are not specified on shipped
production material.
(3) Offset voltage average drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change.
(4) Positive current corresponds to current flowing into the device.
(5) This parameter is specified by design and/or characterization and is not tested in production.
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Electrical Characteristics: 5 V (continued)
Unless otherwise specified, all limits are specified for TA= 25°C, V+= 5 V, V−= 0 V, VCM = (V++ V−)/2.
PARAMETER TEST CONDITIONS MIN(1) TYP(2) MAX(1) UNIT
IOOutput Short Circuit Current Sourcing to V−, VIN = 200 mV (6) 46 60
Sourcing to V−, VIN = 200 mV (6), –40°C ≤38
TJ≤125°C mA
Sinking to V+, VIN =−200 mV (6) 10.5 22
Sinking to V+, VIN =−200 mV (6), –40°C ≤6.5
TJ≤125°C
ISSupply Current 1.3 1.7 mA
–40°C ≤TJ≤125°C 1.95
SR Slew Rate AV= +1, Rising (10% to 90%) 10.43 V/μs
AV= +1, Falling (90% to 10%) 12.76
GBW Gain Bandwidth Product 17 MHz
enInput-Referred Voltage Noise f = 400 Hz 7.5 nV/
f = 1 kHz 6.5
InInput-Referred Current Noise f = 1 kHz 0.01 pA/
THD+N Total Harmonic Distortion + f = 1 kHz, AV= 2, RL= 100 kΩ0.0007%
Noise VO= 4 VPP
f = 1 kHz, AV= 2, RL= 600Ω0.0007%
VO= 4 VPP
(6) The short circuit test is a momentary open loop test.
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0 0.5 1 1.5 2 2.5 3 3.5 4
-10
8
INPUT BIAS CURRENT (pA)
VCM (V)
-8
-6
-4
-2
0
2
4
6V+ = +5V
V- = 0V
TA = 125°C
PERCENTAGE (%)
-200 -100 0 100
OFFSET VOLTAGE (PV)
0
5
10
20
25 V+ = 2.5V
V - = 0V
200
15
0 0.5 1 1.5 2 2.5 3 3.5
-400
400
INPUT BIAS CURRENT (fA)
VCM (V)
-300
-200
-100
0
100
200
300 V+ = +5V
V- = 0V
TA = 85°C
0 0.5 1 1.5 2 2.5 3 3.5 4
-1.2
0.4
INPUT BIAS CURRENT (pA)
VCM (V)
-1
-0.8
-0.6
-0.4
-0.2
0
0.2 V+ = +5V
V- = 0V
TA = 85°C
0 1 2 3 3.5
-20
-15
-10
-5
0
5
INPUT BIAS (fA)
VCM (V)
V+ = 5V
V- = 0V
TA = 25°C
1.50.5 2.5
0 1 2 3 4
-50
-40
-30
-20
-10
0
10
INPUT BIAS (fA)
VCM (V)
V+ = 5V
V- = 0V
TA = 25°C
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6.7 Typical Characteristics
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 1. Input Bias Current vs. VCM Figure 2. Input Bias Current vs. VCM
Figure 3. Input Bias Current vs. VCM Figure 4. Input Bias Current vs. VCM
Figure 6. Offset Voltage Distribution
Figure 5. Input Bias Current vs. VCM
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OFFSET VOLTAGE (PV)
-0.3 0 0.3 0.6 0.9 1.2 1.5
VCM (V)
-400
-300
-200
-100
0
100
200
300
400
2.11.8
125°C
25°C
-40°C
V+ = +2.5V
V- = 0V
OFFSET VOLTAGE (PV)
-0.3 0.7 1.7 2.7 3.7
VCM (V)
-400
-300
-200
-100
0
100
200
300
400
4.7
125°C
25°C
-40°C
V+ = +5V
V- = 0V
OFFSET VOLTAGE (PV)
-0.3 0 0.3 0.6 0.9 1.2 1.5
VCM (V)
-400
-300
-200
-100
0
100
200
300
400
125°C
25°C
-40°C
V+ = 1.8V
V- = 0V
PERCENTAGE (%)
-4 -3 -2 -1
TCVOS DISTRIBUTION (PV/qC)
0
5
10
20
25 V+ = 5.0V
V- = 0V
0
15
PERCENTAGE (%)
-4 -3 -2 -1
TCVOS DISTRIBUTION (PV/qC)
0
5
10
20
25 V+ = 2.5V
V- = 0V
0
15
PERCENTAGE (%)
-200 -100 0 100
OFFSET VOLTAGE (PV)
0
5
10
20
25 V+ = 5.0V
V - = 0V
200
15
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Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 7. Offset Voltage Distribution Figure 8. TCVOS Distribution
Figure 9. TCVOS Distribution Figure 10. Offset Voltage vs. VCM
Figure 11. Offset Voltage vs. VCM Figure 12. Offset Voltage vs. VCM
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140
1k 100k 100M
FREQUENCY (Hz)
-20
40
GAIN (dB)
10M
1M
10k
100
80
20
0
60
120
158
-23
45
113
90
23
0
68
135
PHASE (°)
V+ = +2.5V
V- = -2.5V
CL = 20 pF
GAIN
PHASE
RL = 100 k:, 10 k:, 10 M:, 600:
0
5
15
20
25
35
40
45
PHASE MARGIN (°)
10
30
20 200
CAPACITIVE LOAD (pF)
RL = 600:
RL = 10 M:
RL = 10 k:
VS = 2.5V
1.5 2.5 3.5 4.5 5.5
0
0.4
0.8
1.2
1.6
2
SUPPLY CURRENT (mA)
VS (V)
125°C
25°C
-40°C
140
1k 100k 100M
FREQUENCY (Hz)
-20
40
GAIN (dB)
10M
1M
10k
100
80
20
0
60
120
158
-23
45
113
90
23
0
68
135
PHASE (°)
20 pF
50 pF
100 pF
50 pF
100 pF
V+ = +2.5V
V- = -2.5V
RL = 10 M:
1.5 2.5 3.5 4.5 5.5 6
-400
-300
-200
-100
0
100
400
OFFSET VOLTAGE (PV)
VS (V)
200
300 -40°C
25°C
125°C
-40 -20 0 20 40 60 80 100 125
-200
-150
-100
0
50
100
150
200
OFFSET VOLTAGE (PV)
TEMPERATURE (°C)
-50
V+ = +2.5V
V- = 0V
V+ = +5V
V- = 0V
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Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 13. Offset Voltage vs. Supply Voltage Figure 14. Offset Voltage vs. Temperature
Figure 16. Open-Loop Frequency Response Gain and Phase
Figure 15. Supply Current vs. Supply Voltage
Figure 18. Phase Margin vs. Capacitive Load
Figure 17. Open-Loop Frequency Response Gain and Phase
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10 mV/DIV
200 ns/DIV
V+ = +2.5V
V- = -2.5V
VIN = 20 mVPP
f = 1 MHz
AV = +1
CL = 10 pF
RL = 1 M:
1s/DIV
1 PV/DIV
V+ = +2.5V
V- = -2.5V
120
10 1k 100k 10M
FREQUENCY (Hz)
0
80
PSRR (dB)
1M10k
100
100
60
40
20
+PSRR
-PSRR
V+ = +2.5V
V- = -2.5V
0.1 10 1k 100k
FREQUENCY (Hz)
1
10
100
1000
10k100
1
VS = 5V
VS = 2.7V
VOLTAGE NOISE (nV/
Hz)
0
5
15
20
25
35
40
45
PHASE MARGIN (°)
10
30
20 200
CAPACITIVE LOAD (pF)
RL = 600:
RL = 10 M:
RL = 10 k:
VS = 5V
10 1k 1M
FREQUENCY (Hz)
40
60
100
CMRR (dB)
100k
10k
100
90
70
50
80
V+ = +2.5V
V- = -2.5V
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Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 19. Phase Margin vs. Capacitive Load Figure 20. CMRR vs. Frequency
Figure 22. Input-Referred Voltage Noise vs. Frequency
Figure 21. PSRR vs. Frequency
Figure 23. Time Domain Voltage Noise Figure 24. Small Signal Step Response
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0.001 0.01 0.1 10
OUTPUT AMPLITUDE (VPP)
-120
-100
-80
-60
-40
-20
0
THD+N (dB)
1
V+ = +2.5V
V- = -2.5V
f = 1 kHz
AV = +2
RL = 100 k:
RL = 600:
10 100 1k 10k 100k
FREQUENCY (Hz)
0
0.001
0.002
0.003
0.004
0.005
0.006
THD+N (%)
RL = 100 k:
RL = 600:
V+ = +1.2V
V- = -0.6V
VCM = 0V
VO = 0.9 VPP
AV = +2
0.01 0.1 1 10
OUTPUT AMPLITUDE (VPP)
-100
-90
-80
-70
-60
-50
-40
THD+N (dB)
RL = 100 k:
RL = 600:
V+ = +1.2V
V- = -0.6V
f = 1 kHz
AV = +2
VCM = 0V
200 mV/DIV
1 Ps/DIV
V+ = +1.25V
V- = -1.25V VIN = 1 VPP
f = 200 kHz CL = 10 pF
RL = 1 M:
AV = +1
10 mV/DIV
200 ns/DIV
V+ = +1.25V
V- = -1.25V
VIN = 20 mVPP
f = 1 MHz
AV = +1
CL = 10 pF
RL = 1 M:
200 mV/DIV
1 Ps/DIV
V+ = +2.5V
V- = -2.5V VIN = 1 VPP
f = 200 kHz CL = 10 pF
RL = 1 M:
AV = +1
LMP7721
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www.ti.com
Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 26. Large Signal Step Response
Figure 25. Small Signal Step Response
Figure 27. Large Signal Step Response Figure 28. THD+N vs. Output Voltage
Figure 30. THD+N vs. Frequency
Figure 29. THD+N vs. Output Voltage
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Product Folder Links: LMP7721
-40°C
0 1 2 3 4 5
0
10
20
30
40
50
60
70
ISOURCE (mA)
VOUT (V)
125°C
25°C
V+ = +5V
V- = 0V
-40°C
0 0.5 1 1.5 2 2.5
0
5
10
15
20
25
30
35
ISINK (mA)
VOUT (V)
125°C 25°C
V+ = +2.5V
V- = 0V
-40°C
0 0.5 1 1.5 2 2.5
0
10
20
30
40
50
60
70
ISOURCE (mA)
VOUT (V)
125°C
25°C
V+ = +2.5V
V- = 0V
1.5 2.5 3.5 4.5 5.5
0
5
10
15
20
25
30
35
ISINK (mA)
VS (V)
125°C 25°C
-40°C
1.5 2.5 3.5 4.5 5.5
0
10
20
30
40
50
60
70
80
ISOURCE (mA)
VS (V)
125°C
25°C
-40°C
10 100 1k 10k 100k
FREQUENCY (Hz)
0
0.001
0.002
0.003
0.004
0.005
0.006
0.007
0.008
THD+N (%)
RL = 100 k:
RL = 600:
V+ = +2.5V
V- = -2.5V
VO = 4 VPP
AV = +2
LMP7721
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SNOSAW6E –JANUARY 2008–REVISED DECEMBER 2014
Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 31. THD+N vs. Frequency Figure 32. Sourcing Current vs. Supply Voltage
Figure 33. Sinking Current vs. Supply Voltage Figure 34. Sourcing Current vs. Output Voltage
Figure 35. Sourcing Current vs. Output Voltage Figure 36. Sinking Current vs. Output Voltage
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Product Folder Links: LMP7721
1.5 2.5 3.5 4.5 5.5
0
10
20
30
40
50
VOUT FROM RAIL (mV)
VS (V)
125°C
25°C
-40°C
RL = 2 k:
1.5 2.5 3.5 4.5 5.5
0
10
20
40
60
70
VOUT FROM RAIL (mV)
VS (V)
25°C -40°C
125°C
RL = 600:
50
30
1.5 2.5 3.5 4.5 5.5
0
10
20
30
40
50
VOUT FROM RAIL (mV)
VS (V)
125°C
25°C
-40°C
RL = 10 k:
1.5 2.5 3.5 4.5 5.5
0
10
20
30
40
50
VOUT FROM RAIL (mV)
VS (V)
125°C 25°C
-40°C
RL = 2 k:
1.5 2.5 3.5 4.5 5.5
0
10
20
30
40
50
VOUT FROM RAIL (mV)
VS (V)
125°C 25°C
-40°C
RL = 10 k:
-40°C
0 1 2 3 4 5
0
5
10
15
20
25
30
35
ISINK (mA)
VOUT (V)
125°C
25°C
V+ = +5V
V- = 0V
LMP7721
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Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 37. Sinking Current vs. Output Voltage Figure 38. Output Swing High vs. Supply Voltage
Figure 39. Output Swing Low vs. Supply Voltage Figure 40. Output Swing High vs. Supply Voltage
Figure 41. Output Swing Low vs. Supply Voltage Figure 42. Output Swing High vs. Supply Voltage
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1.5 2.5 3.5 4.5 5.5
0
20
40
80
120
140
VOUT FROM RAIL (mV)
VS (V)
25°C
-40°C
125°C
RL = 600:
100
60
LMP7721
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SNOSAW6E –JANUARY 2008–REVISED DECEMBER 2014
Typical Characteristics (continued)
Unless otherwise specified: TA= 25°C, VCM = (V++ V−)/2.
Figure 43. Output Swing Low vs. Supply Voltage
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7 Detailed Description
7.1 Overview
The LMP7721 combines a patented input bias current cancelling circuitry along with an optimized pinout to
provide and ultra-low maximum specified bias current of ±20 fA.
7.2 Functional Block Diagram
7.3 Feature Description
7.3.1 Ultra-Low Input Bias Current
The LMP7721 has the industry’s lowest specified input bias current. The ultra-low input bias current is typically 3
fA, with a specified limit of ±20 fA at 25°C, ±900 fA at 85°C and ±5 pA at 125°C when VCM = 1 V with a 5-V or a
2.5-V power supply.
7.3.2 Wide Bandwidth at Low-Supply Current
The LMP7721 is a high-performance amplifier that provides a 17-MHz unity gain bandwidth while drawing only
1.3 mA of current. This makes the LMP7721 ideal for wideband amplification in portable applications.
7.3.3 Low Input Referred Noise
The LMP7721 has a low input-referred voltage noise density (6.5 nV at 1 kHz with 5-V supply). Its MOS input
stage ensures a very low input-referred current noise density (0.01 pA/ ).
The low input-referred noise and the ultra-low input bias current make the LMP7721 stand out in maintaining
signal fidelity. This quality makes the LMP7721 a suitable candidate for sensor-based applications.
7.3.4 Low-Supply Voltage
The LMP7721 has performance specified at 2.5-V and 5-V power supplies. The LMP7721 is ensured to be
functional at all supply voltages between 2 V to 5.5 V, for ambient temperatures ranging from −40°C to 125°C.
This means that the LMP7721 has a long operational span over the battery's lifetime. The LMP7721 is also
specified to be functional at 1.8-V supply voltage, for ambient temperatures ranging from 0°C to 125°C. This
makes the LMP7721 ideal for use in low-voltage commercial applications.
7.3.5 Rail-to-Rail Output and Ground Sensing
Rail-to-rail output swing provides the maximum possible output dynamic range. This is particularly important
when operating at low-supply voltages. An innovative positive feedback scheme is created to boost the
LMP7721’s output current drive capability. This allows the LMP7721 to source 30 mA to 40 mA of current at 1.8-
V power supply.
The LMP7721’s input common-mode range includes the negative supply rail which makes direct sensing at
ground possible in single-supply operation.
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ESD R1
IN+
ESD
D1
D2
R2ESD
IN-
ESD
V+
V-V-
V+
LMP7721
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Feature Description (continued)
7.3.6 Unique Pinout
The LMP7721 has been designed with the IN+ and IN−, V+and V−pins on opposite sides of the package. There
are isolation pins between IN+ and V−, IN−and V+. This unique pinout makes it easy to guard the LMP7721’s
input. This pinout design reduces the input bias current’s dependence on common mode or supply bias.
The SOIC package features low leakage and it has large pin spacing. This lowers the probability of dust particles
settling down between two pins thus reducing the resistance between the pins which can be a problem.
The two No Connect (N/C) isolation pins are not internally connected and may be tied to the guard trace to
provide down-into-the-package level guarding of the inputs.
7.3.7 Input Protection
The LMP7721 input stage is protected from seeing excessive differential input voltage by a pair of back-to-back
diodes attached between the inputs. This limits the differential voltage and hence prevents phase inversion as
well as any performance drift. These diodes can conduct current when the input signal has a really fast edge,
and, if necessary, should be isolated (using a resistor or a current follower) in such cases. Under normal
feedback operation, the average differential voltage is less than 1 mV and these diodes do not affect the normal
operation of the device. This clamp also limits the use as a comparator, which is not a recommended function for
operational amplifiers.
Figure 44. Input Protection Diodes
7.4 Device Functional Modes
7.4.1 Compensating Input Capacitance
The high-input resistance of the LMP7721 allows the use of large feedback and source resistor values without
losing gain accuracy due to loading. However, the circuit will be especially sensitive to its layout when these
large-value resistors are used.
Figure 45. General Operational Amplifier Circuit
Every amplifier has some capacitance between each input and AC ground, and also some differential
capacitance between the inputs. When the feedback network around an amplifier is resistive, this input
capacitance (along with any additional capacitance due to circuit board traces, the socket, etc.) and the feedback
resistors create a pole in the feedback path. This pole can cause gain "peaking" or outright oscillations.
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Device Functional Modes (continued)
In the General Operational Amplifier circuit, Figure 45 the frequency of this pole is:
(1)
where:
• CSis the total capacitance at the inverting input, including amplifier input capacitance and any stray
capacitance from the circuit board traces.
• RPis the parallel combination of RFand RIN
The typical input capacitance of the LMP7721 is about 11pF. This formula, as well as all formulas derived below,
apply to inverting and non-inverting op amp configurations.
When the feedback resistors are smaller than a few kΩ, the frequency of the feedback pole will be quite high,
since CSis generally less than 15 pF. If the frequency of the feedback pole is much higher than the “ideal”
closed-loop bandwidth (the nominal closed-loop bandwidth in the absence of CS), the pole will have a negligible
effect on stability, as it will add only a small amount of phase shift.
However, if the feedback pole is less than approximately 6 to 10 times the “ideal” −3 dB frequency, a feedback
capacitor, CF, should be connected between the output and the inverting input of the op amp. This condition can
also be stated in terms of the amplifier’s low-frequency noise gain: To maintain stability a feedback capacitor will
probably be needed if
(2)
where
(3)
is the amplifier’s low-frequency noise gain and GBW is the amplifier’s gain bandwidth product. An amplifier’s low-
frequency noise gain is represented by the formula
(4)
regardless of whether the amplifier is being used in inverting or noninverting mode. Note that a feedback
capacitor is more likely to be needed when the noise gain is low and/or the feedback resistor is large.
If the above condition is met (indicating a feedback capacitor will probably be needed), and the noise gain is
large enough that:
(5)
the following value of feedback capacitor is recommended:
(6)
If
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Device Functional Modes (continued)
(7)
the feedback capacitor should be:
(8)
Note that these capacitor values are usually significant smaller than those given by the older, more conservative
formula:
(9)
NOTE
CSconsists of the amplifier’s input capacitance plus any stray capacitance from the circuit
board. CFcompensates for the pole caused by CSand the feedback resistors.
Using the smaller capacitors will give much higher bandwidth with little degradation of transient response. It may
be necessary in any of the above cases to use a somewhat larger feedback capacitor to allow for unexpected
stray capacitance, or to tolerate additional phase shifts in the loop, or excessive capacitive load, or to decrease
the noise or bandwidth, or simply because the particular circuit implementation needs more feedback
capacitance to be sufficiently stable. For example, a printed circuit board’s stray capacitance may be larger or
smaller than the breadboard’s, so the actual optimum value for CFmay be different from the one estimated using
the breadboard. In most cases, the values of CFshould be checked on the actual circuit, starting with the
computed value.
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Product Folder Links: LMP7721
+
-
Guard
OUT
+1
IN
VREF +
-
Guard
Input
Rleak Cstray
Ground
2.5V
ûV = 2.5V!
2.5V
ûV = 0V! CstrayRleak
0V
High Impedance
Input Amplifer
Guard
Driver
Vcm
Leakage
Path
Leakage
Path
LMP7721
SNOSAW6E –JANUARY 2008–REVISED DECEMBER 2014
www.ti.com
8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The LMP7721 is specified for operation from 1.8 V to 5.5 V. Many of the specifications apply from –40°C to
125°C. Parameters that can exhibit significant variance with regard to operating voltage or temperature are
presented in the Typical Characteristics section.
8.1.1 Using a Guard
In order to take full advantage of the LMP7721’s ultra-low input bias current, a "Guard" trace is recommended
when designing sub-nanoamp systems.
Figure 46. Guarding Theory
A "Guard" is a driven trace or shield that physically surrounds the input trace and feedback circuitry that is held at
a potential equal to the average input signal potential. Since the input circuitry and the guard are kept at the
same potential, the leakage current between the two nodes is practically zero. The guard is a low-impedance
node, so any external leakages will "leak" into the guard and not into the protected input. One benefit of using a
guard is it cancels the effect of the added stray and cable capacitance at low frequencies (but cannot cancel the
sensor or amplifier input capacitance).
The guard potential may be taken from the inverting input (summing node) in noninverting and buffer
applications. An example of this is shown in Figure 47 If the guarding needs to extend beyond the immediate
local area around the IC, then a buffer should be used to drive the guard to prevent adding additional
capacitance to the inverting node.
Figure 47. Guarding the Noninverting Configuration
The guard potential may be taken from the noninverting input or reference voltage in inverting or transimpedance
applications. An example of this is shown in Figure 48
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1
OUTER SHIELD/GROUND
SIGNAL CONDUCTOR
GUARD
+
-
+1
IN
Guard
Guard
Driver VREF +
-
OUT
LMP7721
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SNOSAW6E –JANUARY 2008–REVISED DECEMBER 2014
Application Information (continued)
Figure 48. Guarding the Inverting or Transimpedance Configuration
The gain of the buffer should be slightly less than one to prevent oscillations and should be current limited to
protect against short circuits. The buffer amplifier should also be capable of driving large capacitive loads. To
satisfy these two requirements, a small series output resistor is usually placed on the buffer output in the range
of 100 Ωto 1 kΩ.
For optimum results, the guard should completely enclose the input circuitry within a conductive "cocoon",
including above and below the circuitry. A cover or shield connected to the guard should protect the circuitry
above (or below) the PC board. Do not forget about thru-hole devices (like leaded photodiodes or connectors)
that may expose high-impedance nodes to the opposite side of the board.
The guard trace should not be relied upon as the only method of shielding. A ground plane or shield should
surround and protect the guard from large external leakages and noise, as the guard trace has the potential to
couple noise back into the input. For more information on guarding, please see the articles referenced in Related
Documentation.
8.1.2 Use Triaxial Cable
A triaxial cable or connector is similar to a coaxial cable or connector and is often referred to as “triax”. The
triaxial cable extends the guard protection through the length of the cable by adding a second internal guard
"shield" around the center conductor in addition to the outer ground shield. Figure 49 shows the structure of the
triax connector.
Figure 49. The Structure of a Triax
8.1.3 Properly Clean the Assembly
Proper cleaning of the board is very critical to providing the expected sub-picoamp performance. Properly
cleaning the board and components takes a few extra steps over conventional board cleaning methods. Leftover
flux residue, moisture and cleaning solvent residues will severely degrade the low-current performance.
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Product Folder Links: LMP7721
pH ELECTRODE
RF
Vout
100:
V+
V-
0.1 µF
0.1 µF
0.1 µF
0.1 µF
TRIAX
RG-
+
-
+
LMP7721
LMP7715
LMP7721
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Application Information (continued)
If using "water soluble" or "no clean" flux, a second cleaning step is needed. These fluxes still leave a film behind
that can attract contaminates and dust. The board should be washed with fresh isopropyl alcohol or methanol
and baked to make sure all remaining traces of moisture are removed from the board. Areas between the
component leads should be scrubbed and areas under surface mount devices thoroughly flushed. The board
should be re-cleaned after any rework to components within the guarded areas. Boards should be handled by the
edges and stored in sealed containers with desiccant.
8.2 Typical Application
The following application examples highlight only a few of the circuits where the LMP7721 can be used.
A CMOS input stage with ultra-low input bias current, negligible input current noise, and low input voltage noise
allows the LMP7721 to provide high fidelity amplification. In addition, the LMP7721 has a 17 MHz gain bandwidth
product, which enables high gain at wide bandwidth. A rail-to-rail output swing at 5.5-V power supply allows
detection and amplification of a wide range of input currents. These properties make the LMP7721 ideal for
transimpedance amplification.
Figure 50. LMP7721 as pH Electrode Amplifier
8.2.1 Design Requirements
The output of a pH electrode is typically 59.16 mV per pH unit at 25°C, for an output range of 414 mV to −414
mV as the pH changes from 0 to 14 at 25°C.
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+
-
LMP7721
Ibias
RSV+
V-
VS
Vin
+
-
Vin = VS ± (Ibias x RS)
Error
1
2
3
4
5 7
8
9
10
11
12
13
14
600
500
400
300
200
100
0
-100
-200
-300
-400
-500
-600
pH
mV
100°C (74.04 mV/pH)
25°C (59.16 mV/pH)
0°C (54.20 mV/pH)
LMP7721
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SNOSAW6E –JANUARY 2008–REVISED DECEMBER 2014
Typical Application (continued)
Figure 51. pH Electrode Transfer Function
The output impedance of a pH electrode is extremely high, ranging from 10 MΩto 1000 MΩ. The ultra low input
bias current of the LMP7721 allows the voltage error produced by the input bias current and electrode resistance
to be minimal. For example, the output impedance of the pH electrode used is 10 MΩ, if an op amp with 3 nA of
Ibias is used, the error caused due to this amplifier’s input bias current and the source resistance of the pH
electrode is 30 mV! This error can be greatly reduced to 30 nV by using the LMP7721.
Figure 52. Error Caused by Amplifier’s Input Bias Current and Sensor Source Impedance
8.2.2 Detailed Design Procedure
The output voltage of the pH electrode will range from 54.2 mV/pH at 0°C, to 74.04 mV/pH at 100°C. The
maximum input voltage will then be ±74.04 mV * 7 = ±518.3 mV. Allowing for output swing and offset headroom,
the maximum output swing should be limited to ±2.4V. The amplifier gain would then be 2.4 V / 0.5183 V = 4.6
V/V.
With RF= 3.57 kΩand RG=1kΩ, the gain would be 4.57 V/V.
The output voltage from the pH electrode is fed to the signal conductor of the triax and then sent to the non-
inverting input of the LMP7721. In this application, the inverting input is a low impedance node and hence is used
to drive the LMP7715 which acts as a guard driver. The output of the guard driver is connected to the guard of
the triax through a 100-Ωisolation resistor.
Figure 50 is an example of the LMP7721 used as a pH sensor amplifier.
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Product Folder Links: LMP7721
-2.5
-2.0
-1.5
-1.0
-0.5
0.0
0.5
1.0
1.5
2.0
2.5
-7 -6 -5 -4 -3 -2 -1 0 1 2 3 4 5 6 7
OUTPUT VOLTAGE (V)
pH LEVEL
0°C
25°C
100°C
C002
GAIN = 4.6 V/V
LMP7721
SNOSAW6E –JANUARY 2008–REVISED DECEMBER 2014
www.ti.com
Typical Application (continued)
8.2.3 Application Curve
Figure 53. Output Voltage vs. pH Level
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IN-
IN+ N/C
V-VOUT
N/C
V+
N/C
GUARD
GUARD
LMP7721
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9 Power Supply Recommendations
For high-sensitivity applications, the power supply rails should be as clean as possible.
Noise on the power supply lines can modulate the tiny capacitance (about 0.5 pF) of the ESD structure on each
input. While this is not a major concern for most applications, charge-sensitive or high-gain, high-impedance
applications can be affected. Common results are power line "hum" or high-frequency switcher "hash" imposed
on the signal.
TI recommends using a very low noise linear regulator and add a dedicated filter network to the LMP7721 power
supply pins consisting of a series resistor of about 100 Ω, and a bypass capacitor of 100 uF or larger. Series
inductors or ferrite beads may be required if high frequency switcher noise is present.
10 Layout
10.1 Layout Guidelines
In order to capitalize on the LMP7721’s ultra-low input bias current, careful circuit layout and assembly are
required. Guarding techniques are highly recommended to reduce parasitic leakage current by isolating the
LMP7721’s input from large voltage gradients across the PC board. A guard is a low-impedance conductor that
surrounds an input line and its potential is raised to the input line’s voltage. The input pins should be fully
guarded as shown in Figure 54. The guard traces should completely encircle the input connections. In addition,
they should be located on both sides of the PCB and be connected together.
To further guard the inputs from the supply pins, the two N/C pins may be connected to the guard trace which
will provide guarding down to the leadframe level.
Solder mask should not cover the input and the guard area including guard traces on either side of the PCB.
Keep switching power supplies and other noise-producing devices away from the input area.
10.2 Layout Example
Figure 54. Layout Example Showing Guard Trace
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11 Device and Documentation Support
11.1 Device Support
11.1.1 Development Support
• LMP7721 PSPICE Model, SNOM096
• TINA-TI SPICE Based Circuit Simulation Software (free download), http://www.ti.com/tool/tina-ti
• TI FilterPro Filter Design software, http://www.ti.com/tool/filterpro
11.2 Documentation Support
11.2.1 Related Documentation
For related documentation, see the following:
• LMP7721 Multi-Function Evaluation Board (current evaluation board), SNOU004
• AN-1796 LMP7721 Evaluation Board (obsolete evaluation board - for reference only), SNOA513
• AN-1798 Designing with Electro-Chemical Sensors, SNOA514
• AN-1803 Design Considerations for a Transimpedance Amplifier, SNOA515
• AN-1852 Designing With pH Electrodes, SNOA529
• Compensate Transimpedance Amplifiers Intuitively, SBOA055
• Transimpedance Considerations for High-Speed Operational Amplifiers, SBOA112
• Noise Analysis of FET Transimpedance Amplifiers, SBOA060
• Circuit Board Layout Techniques - SLOA089
• Handbook of Operational Amplifier Applications - SBOA092
• Low Level Measurements Handbook, Keithley Instruments, Inc., Latest Edition. Available: www.keithley.com
• Grohe, P., "Design femtoampere circuits with low leakage, Part 1", EDN Magazine, November 7, 2011.
Available: www.edn.com
• Grohe, P., "Design femtoampere circuits with low leakage, Part 2", EDN Magazine, June 15, 2012. Available:
www.edn.com
• Grohe, P., "Design femtoampere circuits with low leakage, Part 3", EDN Magazine, September 7, 2012.
Available: www.edn.com
11.3 Trademarks
LMP, PowerWise are trademarks of Texas Instruments.
All other trademarks are the property of their respective owners.
11.4 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.5 Glossary
SLYZ022 —TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
www.ti.com 21-Oct-2014
Addendum-Page 1
PACKAGING INFORMATION
Orderable Device Status
(1)
Package Type Package
Drawing Pins Package
Qty Eco Plan
(2)
Lead/Ball Finish
(6)
MSL Peak Temp
(3)
Op Temp (°C) Device Marking
(4/5)
Samples
LMP7721MA/NOPB ACTIVE SOIC D 8 95 Green (RoHS
& no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 125 LMP77
21MA
LMP7721MAX/NOPB ACTIVE SOIC D 8 2500 Green (RoHS
& no Sb/Br) CU SN Level-1-260C-UNLIM -40 to 125 LMP77
21MA
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6) Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
PACKAGE OPTION ADDENDUM
www.ti.com 21-Oct-2014
Addendum-Page 2
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device Package
Type Package
Drawing Pins SPQ Reel
Diameter
(mm)
Reel
Width
W1 (mm)
A0
(mm) B0
(mm) K0
(mm) P1
(mm) W
(mm) Pin1
Quadrant
LMP7721MAX/NOPB SOIC D 8 2500 330.0 12.4 6.5 5.4 2.0 8.0 12.0 Q1
PACKAGE MATERIALS INFORMATION
www.ti.com 21-Oct-2014
Pack Materials-Page 1
*All dimensions are nominal
Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)
LMP7721MAX/NOPB SOIC D 8 2500 367.0 367.0 35.0
PACKAGE MATERIALS INFORMATION
www.ti.com 21-Oct-2014
Pack Materials-Page 2
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