FEATURES PIN CONFIGURATION Wide bandwidth AD9631, G = +1 AD9632, G = +2 Small signal AD9631, 320 MHz AD9632, 250 MHz Large signal (4 V p-p) AD9631, 175 MHz AD9632, 180 MHz Ultralow distortion (SFDR), low noise -113 dBc typical @ 1 MHz -95 dBc typical @ 5 MHz -72 dBc typical @ 20 MHz 46 dBm third-order intercept @ 25 MHz 7.0 nV/Hz spectral noise density High speed Slew rate: 1300 V/s Settling time to 0.01%, 2 V step: 16 ns 3 V to 5 V supply operation 17 mA supply current NC 1 NC 8 -INPUT 2 7 +VS +INPUT 3 6 OUTPUT -VS 4 TOP VIEW 5 NC (Not to Scale) NOTES 1. NC = NO CONNECT. Figure 1. 8-Lead PDIP (N) and SOIC (R) Packages A proprietary design architecture has produced an amplifier that combines many of the best characteristics of both current feedback and voltage feedback amplifiers. The AD9631/AD9632 exhibit exceptionally fast and accurate pulse response (16 ns to 0.01%) as well as extremely wide small signal and large signal bandwidth and ultralow distortion. The AD9631 achieves -72 dBc at 20 MHz, 320 MHz small signal bandwidth, and 175 MHz large signal bandwidths. These characteristics position the AD9631/AD9632 ideally for driving flash as well as high resolution ADCs. Additionally, the balanced high impedance inputs of the voltage feedback architecture allow maximum flexibility when designing active filters. APPLICATIONS The AD9631/AD9632 are offered in the industrial (-40C to +85C) temperature range. They are available in PDIP and SOIC. -30 GENERAL DESCRIPTION The AD9631/AD9632 are very high speed and wide bandwidth amplifiers. The AD9631 is unity gain stable. The AD9632 is stable at gains of 2 or greater. Using a voltage feedback architecture, the exceptional settling time, bandwidth, and low distortion of the AD9631/AD9632 meet the requirements of many applications that previously depended on current feedback amplifiers. Its classical op amp structure works much more predictably in many designs. HARMONIC DISTORTION (dBc) -40 VS = 5V RL = 500 VOUT = 2V p-p -50 -60 -70 -80 -90 SECOND HARMONIC -100 -110 THIRD HARMONIC -120 -130 10k 100k 1M 10M 100M FREQUENCY (Hz) 00601-002 ADC input driver Differential amplifiers IF/RF amplifiers Pulse amplifiers Professional video DAC current to voltage Baseband and video communications Pin diode receivers Active filters/integrators/log amps Rev. D AD9631/ AD9632 00601-001 Data Sheet Ultralow Distortion, Wide Bandwidth Voltage Feedback Op Amps AD9631/AD9632 Figure 2. AD9631 Harmonic Distortion vs. Frequency, G = +1 Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 (c)2014 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com AD9631/AD9632 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 General......................................................................................... 15 Applications ....................................................................................... 1 Feedback Resistor Choice.......................................................... 15 General Description ......................................................................... 1 Pulse Response ........................................................................... 16 Pin Configuration ............................................................................. 1 Large Signal Performance ......................................................... 16 Revision History ............................................................................... 2 Power Supply Bypassing ............................................................ 16 Specifications..................................................................................... 3 Driving Capacitive Loads .......................................................... 16 Electrical Characteristics ............................................................. 3 Applications Information .............................................................. 17 Absolute Maximum Ratings ............................................................ 5 Operation as a Video Line Driver ............................................ 17 Metallization Photo ...................................................................... 5 Active Filters ............................................................................... 17 Thermal Resistance ...................................................................... 5 Analog-to-Digital Converter (ADC) Driver .......................... 18 Maximum Power Dissipation ..................................................... 5 Layout Considerations ............................................................... 18 ESD Caution .................................................................................. 5 Outline Dimensions ....................................................................... 19 Typical Performance Characteristics ............................................. 6 Ordering Guide .......................................................................... 20 Theory of Operation ...................................................................... 15 REVISION HISTORY 2/14--Rev. C to Rev. D Changes to Figure 33 ...................................................................... 10 Changes to Analog-to-Digital Converter (ADC) Driver Section and Figure 66 ................................................................................... 18 Updated Outline Dimensions ....................................................... 19 Changes to Ordering Guide .......................................................... 20 7/03--Rev. B to Rev. C Deleted Evaluation Boards information .......................... Universal Deleted military CERDIP version .................................... Universal Change to Absolute Maximum Ratings ......................................... 3 Change to TPC 4 ............................................................................... 4 Change to TPC 10............................................................................. 5 Change to Figure 6 ......................................................................... 14 Updated Outline Dimensions ....................................................... 17 1/03--Rev. A to Rev. B Deleted DIP (N) Inverter, SOIC (R) Inverter, and DIP (N) Noninverter Evaluation Boards in Figures 12-14 ...................... 17 Updated Outline Dimensions ....................................................... 18 Rev. D | Page 2 of 20 Data Sheet AD9631/AD9632 SPECIFICATIONS ELECTRICAL CHARACTERISTICS VS = 5 V; RLOAD = 100 ; AV = 1 (AD9631); AV = 2 (AD9632), unless otherwise noted. Table 1. Parameter DYNAMIC PERFORMANCE Bandwidth (-3 dB) Small Signal Large Signal 1 Bandwidth for 0.1 dB Flatness Slew Rate, Average Rise/Fall Time Settling Time To 0.1% To 0.01% HARMONIC/NOISE PERFORMANCE Second Harmonic Distortion Third Harmonic Distortion Third-Order Intercept Noise Figure Input Voltage Noise Input Current Noise Average Equivalent Integrated Input Noise Voltage Differential Gain Error (3.58 MHz) Differential Phase Error (3.58 MHz) Phase Nonlinearity DC PERFORMANCE 2 Input Offset Voltage 3 Test Conditions/Comments Min VOUT 0.4 V p-p VOUT = 4 V p-p VOUT = 300 mV p-p RF = 140 (AD9631); RF = 425 (AD9632) VOUT = 4 V step VOUT = 0.5 V step VOUT = 4 V step 220 150 AD9631 Typ Max 320 175 180 155 130 1000 1300 1.2 2.5 1200 AD9632 Typ Max Unit 250 180 MHz MHz 130 MHz 1500 1.4 2.1 V/s ns ns 11 16 ns ns VOUT = 2 V step VOUT = 2 V step 11 16 2 V p-p; 20 MHz, RL = 100 RL = 500 2 V p-p; 20 MHz, RL = 100 RL = 500 25 MHz RS = 50 1 MHz to 200 MHz 1 MHz to 200 MHz 0.1 MHz to 200 MHz -64 -72 -76 -81 46 18 7.0 2.5 100 -57 -65 -69 -74 -54 -72 -74 -81 41 14 4.3 2.0 60 -47 -65 -67 -74 dBc dBc dBc dBc dBm dB nA/Hz pA/Hz V rms RL = 150 RL = 150 DC to 100 MHz RL = 150 0.03 0.02 1.1 0.06 0.04 0.02 0.02 1.1 0.04 0.04 % Degree Degree 3 10 13 2 5 8 mV mV V/C A A A A dB dB dB TMIN - TMAX Offset Voltage Drift Input Bias Current 10 2 TMIN - TMAX Input Offset Current Common-Mode Rejection Ratio Open-Loop Gain Min 0.1 TMIN - TMAX VCM = 2.5 V VOUT = 2.5 V TMIN - TMAX 70 46 40 INPUT CHARACTERISTICS Input Resistance Input Capacitance Input Common-Mode Voltage Range 90 52 500 1.2 3.4 Rev. D | Page 3 of 20 10 2 7 10 3 5 0.1 70 46 40 90 52 500 1.2 3.4 7 10 3 5 k pF V AD9631/AD9632 Parameter OUTPUT CHARACTERISTICS Output Voltage Range Output Current Output Resistance Short Circuit Current POWER SUPPLY Operating Range Quiescent Current Power Supply Rejection Ratio Data Sheet AD9631 Typ Max Test Conditions/Comments Min RL = 150 3.2 3.9 70 0.3 240 3.0 5.0 17 50 60 TMIN - TMAX TMIN - TMAX See the Absolute Maximum Ratings and Theory of Operation sections of this data sheet. Measured at AV = 50. 3 Measured with respect to the inverting input. 1 2 Rev. D | Page 4 of 20 6.0 18 21 Min AD9632 Typ Max 3.2 3.9 70 0.3 240 3.0 5.0 16 56 66 Unit V mA mA 6.0 17 20 V mA mA dB Data Sheet AD9631/AD9632 ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 2. Table 3. Rating 12.6 V 550 V x MHz Storage Temperature Range Operating Temperature Range (A Grade) Lead Temperature Range (Soldering 10 sec) Package Type1 8-Lead PDIP (N) 8-Lead SOIC (R) 1.3 W 0.9 W VS 1.2 V Observe Power Derating Curves -65C to +125C -40C to +85C 300C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. METALLIZATION PHOTO MAXIMUM POWER DISSIPATION The maximum power that can be safely dissipated by these devices is limited by the associated rise in junction temperature. The maximum safe junction temperature for plastic encapsulated devices is determined by the glass transition temperature of the plastic, approximately 150C. Exceeding this limit temporarily may cause a shift in parametric performance due to a change in the stresses exerted on the die by the package. Exceeding a junction temperature of 175C for an extended period can result in device failure. While the AD9631 and AD9632 are internally short circuit protected, this may not be sufficient to guarantee that the maximum junction temperature (150C) is not exceeded under all conditions. To ensure proper operation, it is necessary to observe the maximum power derating curves. 2.0 TJ = 150C 8-LEAD PDIP PACKAGE MAXIMUM POWER DISSIPATION (W) 0.046 (1.17) 6 OUT 0.050 (1.27) -IN 2 1.5 1.0 8-LEAD SOIC PACKAGE 0.5 0 -50 -40 -30 -20 -10 AD9631 4 -VS AD9632 00601-003 6 OUT 4 -VS 10 20 30 40 50 60 70 80 Figure 4. Maximum Power Dissipation vs. Temperature ESD CAUTION 3 +IN 0 AMBIENT TEMPERATURE (C) +VS 7 0.046 (1.17) Unit C/W C/W For device in free air. +VS 7 -IN 2 3 +IN 1 JA 90 140 Figure 3. Dimensions shown in inches and (millimeters) Connect Substrate to -VS Rev. D | Page 5 of 20 90 00601-004 Parameter Supply Voltage (+VS to -VS) Voltage Swing x Bandwidth Product Internal Power Dissipation PDIP (N) SOIC (R) Input Voltage (Common Mode) Differential Input Voltage Output Short Circuit Duration AD9631/AD9632 Data Sheet TYPICAL PERFORMANCE CHARACTERISTICS RF RF 10F +VS +VS PULSE GENERATOR TR/TF = 350ps 0.1F AD9631 VOUT RL = 100 0.1F RT 49.9 10F -VS Figure 8. AD9631 Inverting Configuration, G = -1 00601-006 5ns 1V 5ns Figure 9. AD9631 Large Signal Transient Response; VOUT = 4 V p-p, G = -1, RF = RIN = 267 00601-007 Figure 6. AD9631 Large Signal Transient Response; VOUT = 4 V p-p, G = +1, RF = 250 5ns 00601-008 10F Figure 5. AD9631 Noninverting Configuration, G = +1 100mV RL = 100 0.1F 100 -VS 1V VOUT AD9631 00601-009 130 267 RT 49.9 00601-005 VIN VIN 0.1F 100mV Figure 7. AD9631 Small Signal Transient Response; VOUT = 400 mV p-p, G = +1, RF = 140 5ns 00601-010 PULSE GENERATOR TR/TF = 350ps 10F Figure 10. AD9631 Small Signal Transient Response; VOUT = 400 mV p-p, G = -1, RF = RIN = 267 Rev. D | Page 6 of 20 Data Sheet AD9631/AD9632 RF RF 10F +VS PULSE GENERATOR TR/TF = 350ps RIN 0.1F VIN 0.1F RT 49.9 RT 49.9 VOUT AD9632 RL = 100 0.1F 100 -VS 1V 5ns Figure 15. AD9632 Large Signal Transient Response; VOUT = 4 V p-p, G = -1, RF = RIN = 422 , RT = 56.2 00601-013 Figure 12. AD9632 Large Signal Transient Response; VOUT = 4 V p-p, G = +2, RF = RIN = 422 100mV Figure 13. AD9632 Small Signal Transient Response; VOUT = 400 mV p-p, G = +2, RF = RIN = 274 5ns 00601-015 Figure 14. AD9632 Inverting Configuration, G = -1 00601-012 5ns 00601-014 10F 5ns 00601-016 10F Figure 11. AD9632 Noninverting Configuration, G = +2 100mV VOUT AD9632 RL = 100 -VS 1V 0.1F RIN 00601-011 VIN 130 10F +VS PULSE GENERATOR TR/TF = 350ps Figure 16. AD9632 Small Signal Transient Response; VOUT = 400 mV p-p, G = -1, RF = RIN = 267 , RT = 61.9 Rev. D | Page 7 of 20 AD9631/AD9632 Data Sheet 1 475 RF = 150 0 -1 -3dB BANDWIDTH (MHz) 425 RF = 100 -3 -4 -5 -6 375 N PACKAGE 350 358 R PACKAGE VS = 5V RL = 100 VOUT = 300mV p-p 10M 100M 1G FREQUENCY (Hz) 250 20 140 160 180 200 220 240 RF = 250 -1 -0.3 RF = 120 -0.4 RF = 50 TO 250 BY 50 -2 RF = 100 OUTPUT (dB) -0.5 -3 -4 -5 -6 -0.6 -7 VS = 5V RL = 100 G = +1 VOUT = 300mV p-p 10M 100M 500M FREQUENCY (Hz) 100 1 80 80 0 70 60 -1 60 40 50 20 40 0 PHASE MARGIN (Degrees) PHASE -3 -5 -40 10 -60 0 -80 -7 -100 -8 1M 10M 100M -6 -120 1G 00601-019 100k RF = 267 -4 20 -10 500M -2 GAIN (dB) -20 100M Figure 21. AD9631 Large Signal Frequency Response, G = +1 90 GAIN 10M FREQUENCY (Hz) Figure 18. AD9631 0.1 dB Flatness, N Package (for R Package Add 20 to RF) 30 VS = 5V RL = 100 VOUT = 4V p-p -9 1M 00601-018 -0.9 1M -8 00601-021 GAIN (dB) 120 0 RF = 140 -0.2 GAIN (dB) 100 1 -0.1 -20 10k 80 Figure 20. AD9631 Small Signal -3 dB Bandwidth vs. RF RF = 150 0 60 VALUE OF FEEDBACK RESISTOR, RF () Figure 17. AD9631 Small Signal Frequency Response, G = +1 0.1 40 00601-020 -9 1M 275 00601-017 -8 -0.8 RL 300 -7 -0.7 AD9631 130 400 FREQUENCY (Hz) Figure 19. AD9631 Open-Loop Gain and Phase Margin vs. Frequency, RL = 100 Rev. D | Page 8 of 20 VS = 5V RL = 100 VOUT = 300mV p-p -9 1M 10M 100M 1G FREQUENCY (Hz) Figure 22. AD9631 Small Signal Frequency Response, G = -1 00601-022 GAIN (dB) RF = 200 RF = 50 -2 RF VS = 5V RL = 100 G = +1 450 Data Sheet -60 -70 SECOND HARMONIC -80 -90 -100 THIRD HARMONIC -110 -130 10k 100k 1M 10M 100M FREQUENCY (Hz) 00601-023 -120 -50 -0.05 -0.10 0.10 0.05 0 -0.05 -0.10 1ST 2ND 3RD 4TH 5TH 6TH 7TH 8TH 9TH 10TH 11TH 0.3 VS = 5V RL = 100 G = +1 VOUT = 2V p-p 0.2 -60 0.1 -70 -80 ERROR (%) HARMONIC DISTORTION (dBc) -40 0 Figure 26. AD9631 Differential Gain and Phase Error, G = +2, RL = 150 Figure 23. AD9631 Harmonic Distortion vs. Frequency, RL = 500 -30 0.05 00601-026 -50 DIFFERENTIAL PHASE (Degrees) HARMONIC DISTORTION (dBc) -40 0.10 VS = 5V RL = 500 G = +1 VOUT = 2V p-p DIFFERENTIAL GAIN (%) -30 AD9631/AD9632 SECOND HARMONIC -90 0 -0.1 -100 THIRD HARMONIC -110 -0.2 100k 1M 10M 100M FREQUENCY (Hz) -0.3 00601-024 -130 10k 0 10 20 30 40 50 60 70 80 SETTLING TIME (ns) Figure 24. AD9631 Harmonic Distortion vs. Frequency, RL = 100 00601-027 -120 Figure 27. AD9631 Short-Term Settling Time, 2 V Step, RL = 100 0.3 60 55 0.2 ERROR (%) 45 40 35 0.1 0 30 -0.1 20 10 100 FREQUENCY (MHz) Figure 25. AD9631 Third Order Intercept vs. Frequency -0.2 0 1 2 3 4 5 6 7 8 9 10 SETTLING TIME (s) Figure 28. AD9631 Long-Term Settling Time, 2 V Step, RL = 100 Rev. D | Page 9 of 20 00601-028 25 00601-025 INTERCEPT (dBm) 50 AD9631/AD9632 Data Sheet 375 7 RF = 325 6 VS = 5V RL = 100 G = +2 350 RF = 425 325 -3dB BANDWIDTH (MHz) RF = 125 RF = 225 4 2 1 0 -1 VS = 5V RL = 100 VOUT = 300mV p-p -3 1M 10M 100M 1G FREQUENCY (Hz) RF 225 RIN R PACKAGE 200 175 100 150 49.9 100 AD9632 150 RL 200 250 300 350 400 450 500 550 600 VALUE OF RF, RIN () Figure 32. AD9632 Small Signal -3 dB Bandwidth vs. RF, RIN 0.1 7 0 6 RF = 275 OUTPUT (dB) -0.4 RF = 425 -0.5 1 -2 10M 100M FREQUENCY (Hz) VS = 5V RL = 100 VOUT = 4V p-p -3 1M 10M 100M 500M FREQUENCY (Hz) 00601-033 -0.9 1M Figure 33. AD9632 Large Signal Frequency Response, G = +2 Figure 30. AD9632 0.1 dB Flatness, N Package (for R Package Add 20 to RF) 1 150 0 100 0 -50 GAIN -100 -150 -2 GAIN (dB) 50 PHASE MARGIN (Degrees) -1 PHASE -3 RF, RIN = 267 -4 -5 -6 -7 -200 100k 1M 10M 100M -8 -250 1G 00601-031 65 60 55 50 45 40 35 30 25 20 15 10 5 0 -5 -10 -15 10k 2 -1 VS = 5V RL = 100 G = +2 VOUT = 300mV p-p 00601-030 -0.8 3 0 -0.6 -0.7 RF = 125 TO 425 BY 100 4 RF = 375 -0.3 RF = 425 5 RF = 325 -0.2 OUTPUT (dB) 250 Figure 29. AD9632 Small Signal Frequency Response, G = +2 -0.1 AOL (dB) 275 125 50 00601-029 -2 N PACKAGE FREQUENCY (Hz) Figure 31. AD9632 Open-Loop Gain and Phase Margin vs. Frequency, RL = 100 Rev. D | Page 10 of 20 VS = 5V RL = 100 VOUT = 300mV p-p -9 1M 10M 100M 1G FREQUENCY (Hz) Figure 34. AD9632 Small Signal Frequency Response, G = -1 00601-034 GAIN (dB) 3 300 00601-032 5 Data Sheet -60 -70 -80 SECOND HARMONIC -90 -100 THIRD HARMONIC -110 -130 10k 100k 1M 10M 100M FREQUENCY (Hz) 00601-035 -120 -50 -0.02 -0.04 0.04 0.02 0 -0.02 -0.04 1ST 2ND 3RD 4TH 5TH 6TH 7TH 8TH 9TH 10TH 11TH 0.2 VS = 5V RL = 100 G = +2 VOUT = 2V p-p 0.1 -60 SECOND HARMONIC -70 ERROR (%) HARMONIC DISTORTION (dBc) -40 0 Figure 38. AD9632 Differential Gain and Phase Error G = +2, RL = 150 Figure 35. AD9632 Harmonic Distortion vs. Frequency, RL = 500 -30 0.02 00601-038 -50 DIFFERENTIAL PHASE (Degrees) HARMONIC DISTORTION (dBc) -40 0.04 VS = 5V RL = 500 G = +2 VOUT = 2V p-p DIFFERENTIAL GAIN (%) -30 AD9631/AD9632 -80 -90 0 -0.1 THIRD HARMONIC -100 -110 -0.2 100k 1M 10M 100M FREQUENCY (Hz) -0.3 00601-036 -130 10k 0 10 20 30 40 50 60 70 80 SETTLING TIME (ns) Figure 36. AD9632 Harmonic Distortion vs. Frequency, RL = 100 00601-039 -120 Figure 39. AD9632 Short-Term Settling Time, 2 V Step, RL = 100 50 0.3 45 0.2 ERROR (%) 35 30 25 0.1 0 20 -0.1 10 10 100 FREQUENCY (MHz) Figure 37. AD9632 Third Order Intercept vs. Frequency -0.2 0 1 2 3 4 5 6 7 8 9 10 SETTLING TIME (s) Figure 40. AD9632 Long-Term Settling Time, 2 V Step, RL = 100 Rev. D | Page 11 of 20 00601-040 15 00601-037 INTERCEPT (dBm) 40 AD9631/AD9632 17 VS = 5V 15 INPUT NOISE VOLTAGE (nVHz) 18 15 12 9 9 7 5 100 1k 10k 3 10 00601-041 3 10 11 100k FREQUENCY (Hz) PSRR (dB) 10M 100M 1G FREQUENCY (Hz) 00601-042 PSRR (dB) +PSRR 1M 80 75 70 65 60 55 50 45 40 35 30 25 20 15 10 5 0 10k CMRR (dB) 70 60 50 30 30 FREQUENCY (Hz) 10M 100M 1G 1G VS = 5V VCM = 1V RL = 100 50 40 100M 1M 60 40 00601-043 CMRR (dB) 70 10M 100k 90 80 1M +PSRR 100 80 20 100k -PSRR Figure 45. AD9632 PSRR vs. Frequency VS = 5V VCM = 1V RL = 100 90 100k FREQUENCY (Hz) Figure 42. AD9631 PSRR vs. Frequency 100 10k Figure 44. AD9632 Noise vs. Frequency -PSRR 100k 1k FREQUENCY (Hz) Figure 41. AD9631 Noise vs. Frequency 80 75 70 65 60 55 50 45 40 35 30 25 20 15 10 5 0 10k 100 00601-044 6 13 00601-045 INPUT NOISE VOLTAGE (nVHz) 21 VS = 5V Figure 43. AD9631 CMRR vs. Frequency 20 100k 1M 10M 100M FREQUENCY (Hz) Figure 46. AD9632 CMRR vs. Frequency Rev. D | Page 12 of 20 1G 00601-046 24 Data Sheet Data Sheet 1350 VS = 5V G = +1 1250 1150 OPEN-LOOP GAIN (V/V) ROUT () 100 10 1 0.1 +AOL AD9632 1050 950 -AOL 850 750 650 550 +AOL AD9631 450 100k 1M 10M 100M FREQUENCY (Hz) 350 -60 00601-047 0.01 10k -40 -20 0 20 40 60 80 100 120 140 JUNCTION TEMPERATURE (C) Figure 47. AD9631 Output Resistance vs. Frequency 1k -AOL 00601-050 1k AD9631/AD9632 Figure 50. Open-Loop Gain vs. Temperature 76 VS = 5V G = +1 74 100 AD9632 -PSRR 72 PSRR (dB) ROUT () 70 10 1 +PSRR 68 AD9632 66 -PSRR 64 AD9631 62 0.1 60 +PSRR 100k 1M 10M 100M FREQUENCY (Hz) 56 -60 00601-048 0.01 10k -40 20 40 60 80 100 120 140 100 120 140 Figure 51. PSRR vs. Temperature 98 VS = 5V +VOUT 4.0 96 RL = 150 |-VOUT| 3.9 94 CMRR (dB) 3.8 3.7 3.6 -40 -20 0 20 40 60 80 100 JUNCTION TEMPERATURE (C) 120 140 Figure 49. Output Swing vs. Temperature 86 -60 -40 -20 0 20 40 60 80 JUNCTION TEMPERATURE (C) Figure 52. CMRR vs. Temperature Rev. D | Page 13 of 20 00601-052 3.3 -60 -CMRR +CMRR 88 |-VOUT| 3.4 92 90 RL = 50 +VOUT 3.5 00601-049 OUTPUT SWING (V) 0 JUNCTION TEMPERATURE (C) Figure 48. AD9632 Output Resistance vs. Frequency 4.1 -20 00601-051 AD9631 58 AD9631/AD9632 Data Sheet 21 250 AD9631 6V AD9631 240 SHORT CIRCUIT CURRENT (mA) 19 AD9632 6V 18 AD9631 5V 17 AD9632 5V 16 SINK SOURCE 230 220 210 SOURCE 200 0 20 40 60 80 100 120 140 JUNCTION TEMPERATURE (C) 180 -60 -40 -1.5 1.5 INPUT BIAS CURRENT (A) AD9632 VS = 5V -3.0 VS = 6V AD9631 -4.0 VS = 5V -4.5 -40 -20 0 20 40 60 80 100 120 140 JUNCTION TEMPERATURE (C) 1.0 +IB 0.5 -IB CUMULATIVE +IB -2.0 -60 -40 160 40 0 0 1 2 3 4 5 6 INPUT OFFSET VOLTAGE (mV) 60 80 100 120 140 7 100 3 WAFER LOTS COUNT = 573 90 80 70 50 80 60 40 FREQUENCY DISTRIBUTION 30 40 20 20 10 20 -1 40 60 20 40 -2 20 100 30 60 -3 0 120 COUNT FREQUENCY DISTRIBUTION -4 -20 140 PERCENT 50 -5 AD9632 CUMULATIVE 00601-055 COUNT 90 60 -6 AD9631 -1.5 180 120 0 -7 140 -IB 100 70 140 80 120 JUNCTION TEMPERATURE (C) 80 160 100 100 Figure 57. Input Bias Current vs. Temperature 3 WAFER LOTS COUNT = 1373 180 80 -1.0 Figure 54. Input Offset Voltage vs. Temperature 200 60 -0.5 VS = 6V -5.0 -60 40 0 00601-054 INPUT OFFSET VOLTAGE (mV) 2.0 -3.5 20 Figure 56. Short Circuit Current vs. Temperature -1.0 -2.5 0 JUNCTION TEMPERATURE (C) Figure 53. Supply Current vs. Temperature -2.0 -20 00601-057 -20 Figure 55. AD9631 Input Offset Voltage Distribution 0 -7 10 0 -6 -5 -4 -3 -2 -1 0 1 2 3 4 5 6 INPUT OFFSET VOLTAGE (mV) Figure 58. AD9632 Input Offset Voltage Distribution Rev. D | Page 14 of 20 PERCENT -40 00601-053 14 -60 00601-056 190 15 220 SINK AD9632 7 00601-058 SUPPLY CURRENT (mA) 20 Data Sheet AD9631/AD9632 THEORY OF OPERATION GENERAL The AD9631/AD9632 are wide bandwidth, voltage feedback amplifiers. Because their open-loop frequency response follows the conventional 6 dB/octave roll-off, their gain bandwidth product is basically constant. Increasing their closed-loop gain results in a corresponding decrease in small signal bandwidth. This can be observed by noting the bandwidth specification between the AD9631 (gain of +1) and AD9632 (gain of +2). The AD9631/AD9632 typically maintain 65 of phase margin. This high margin minimizes the effects of signal and noise peaking. FEEDBACK RESISTOR CHOICE The value of the feedback resistor is critical for optimum performance on the AD9631 (gain of +1) and less critical as the gain increases. Therefore, this section is specifically targeted at the AD9631. At the minimum stable gain (+1), the AD9631 provides optimum dynamic performance with RF = 140 . This resistor acts as a parasitic suppressor only against damped RF oscillations that can occur due to lead (input, feedback) inductance and parasitic capacitance. This value of RF provides the best combination of wide bandwidth, low parasitic peaking, and fast settling time. When the AD9631 is used in the transimpedance (I to V) mode, such as in photodiode detection, the value of RF and diode capacitance (CI) are usually known. Generally, the value of RF selected will be in the k range, and a shunt capacitor (CF) across RF will be required to maintain good amplifier stability. The value of CF required to maintain optimal flatness (<1 dB peaking) and settling time can be estimated by C F [(2OC I RF - 1) / O 2 RF 2 ] 1 2 where: O is equal to the unity gain bandwidth product of the amplifier in rad/sec. CI is the equivalent total input capacitance at the inverting input. Typically O = 800 x 106 rad/sec (see Figure 19). As an example, choosing RF = 10 k and CI = 5 pF requires CF to be 1.1 pF (Note that CI includes both source and parasitic circuit capacitance). The bandwidth of the amplifier can be estimated using CF: f 3dB 1.6 2RF C F RF In fact, for the same reasons, place a 100 to 130 resistor in series with the positive input for other AD9631 noninverting and all AD9631 inverting configurations. The correct connection is shown in Figure 59 and Figure 60. CF CI AD9631 VOUT 00601-061 II +VS G=1+ RF RG 10F Figure 61. Transimpedance Configuration 100 TO 130 VIN RTERM RIN For general voltage gain applications, the amplifier bandwidth can be closely estimated as 0.1F AD9631/ AD9632 VOUT f 3dB RF RG 00601-059 0.1F 10F -VS Figure 59. Noninverting Operation RF RG RIN This estimation loses accuracy for gains of +2/-1 or lower due to the damping factor of the amplifier. For these low gain cases, the bandwidth will actually extend beyond the calculated value (see Figure 17 and Figure 29). (R 10F 100 TO 130 0.1F AD9631/ AD9632 RF 10F -VS 00601-060 0.1F RTERM F ) RG x C I NG 4O where NG is the noise gain (1 + RF/RG) of the circuit. For most voltage gain applications, this should be the case. VOUT RG VIN 2 (1 + RF / RG ) As a general rule, Capacitor CF will not be required if +VS G=1- O Figure 60. Inverting Operation Rev. D | Page 15 of 20 AD9631/AD9632 Data Sheet PULSE RESPONSE DRIVING CAPACITIVE LOADS Unlike a traditional voltage feedback amplifier, where the slew speed is dictated by its front end dc quiescent current and gain bandwidth product, the AD9631/AD9632 provide on-demand current that increases proportionally to the input step signal amplitude. This results in slew rates (1300 V/s) comparable to wideband current feedback designs. This, combined with relatively low input noise current (2.0 pA/Hz), gives the AD9631/AD9632 the best attributes of both voltage and current feedback amplifiers. The AD9631/AD9632 were designed primarily to drive nonreactive loads. If driving loads with a capacitive component is desired, the best frequency response is obtained by the addition of a small series resistance as shown in Figure 62. Figure 63 shows the optimum value for RSERIES vs. capacitive load. It is worth noting that the frequency response of the circuit when driving large capacitive loads will be dominated by the passive roll-off of RSERIES and CL. RF LARGE SIGNAL PERFORMANCE RIN RIN RSERIES AD9631/ AD9632 RL 1k CL 00601-062 The outstanding large signal operation of the AD9631 and AD9632 is due to a unique, proprietary design architecture. To maintain this level of performance, the maximum 550 V x MHz product must be observed (for example, @ 100 MHz, VOUT 5.5 V p-p). Figure 62. Driving Capacitive Loads POWER SUPPLY BYPASSING 40 30 RSERIES () 20 10 0 5 10 15 20 CL (pF) Figure 63. Recommended RSERIES vs. Capacitive Load Rev. D | Page 16 of 20 25 00601-063 Adequate power supply bypassing can be critical when optimizing the performance of a high frequency circuit. Inductance in the power supply leads can form resonant circuits that produce peaking in the amplifier's response. In addition, if large current transients must be delivered to the load, then bypass capacitors (typically greater than 1 F) will be required to provide the best settling time and lowest distortion. A parallel combination of at least 4.7 F, and between 0.1 F and 0.01 F, is recommended. Some brands of electrolytic capacitors will require a small series damping resistor 4.7 for optimum results. Data Sheet AD9631/AD9632 APPLICATIONS INFORMATION Figure 65 is an example of a 20 MHz low-pass multiple feedback active filter using an AD9632. R4 154 VIN R1 154 100 274 -5V Choose FO = cutoff frequency = 20 MHz = damping ratio = 1/Q = 2 H = absolute value of circuit gain = 10F Then k = 2FOC1 75 75 CABLE AD9631/ AD9632 0.1F 75 AD9632 VOUT 75 00601-064 10F -VS VOUT 10F 0.1F VIN 0.1F Figure 65. Active Filter Circuit The AD9631/AD9632 have been designed to offer outstanding performance as video line drivers. The important specifications of differential gain (0.02%) and differential phase (0.02) meet the most exacting HDTV demands for driving video loads. 75 CABLE 10F 0.1F OPERATION AS A VIDEO LINE DRIVER +VS +5V R3 78.7 C2 100pF With a settling time of 16 ns to 0.01% and 11 ns to 0.1%, the devices are an excellent choice for DAC I/V conversion. The same characteristics along with low harmonic distortion make them a good choice for ADC buffering/amplification. With superb linearity at relatively high signal frequencies, the AD9631/AD9632 are ideal drivers for ADCs up to 12 bits. 274 C1 50pF 00601-065 The AD9631/AD9632 are voltage feedback amplifiers well suited for applications such as photodetectors, active filters, and log amplifiers. The wide bandwidth (320 MHz), phase margin (65), low current noise (2.0 pA/Hz), and slew rate (1300 V/s) of the devices give higher performance capabilities to these applications over previous voltage feedback designs. C2 = R1 = R3 = Figure 64. Video Line Driver ACTIVE FILTERS The wide bandwidth and low distortion of the AD9631/ AD9632 are ideal for the realization of higher bandwidth active filters. These characteristics, while being more common in many current feedback op amps, are offered in the AD9631/ AD9632 in a voltage feedback configuration. Many active filter configurations are not realizable with current feedback amplifiers. A multiple feedback active filter requires a voltage feedback amplifier and is more demanding of op amp performance than other active filter configurations, such as the Sallen-Key. In general, the amplifier should have a bandwidth that is at least 10 times the bandwidth of the filter if problems due to phase shift of the amplifier are to be avoided. Rev. D | Page 17 of 20 4C1(H + 1) 2 2HK 2K (H + 1) R4 = H (R1) -R4 =1 R1 AD9631/AD9632 Data Sheet ANALOG-TO-DIGITAL CONVERTER (ADC) DRIVER LAYOUT CONSIDERATIONS As ADCs move toward higher speeds with higher resolutions, there becomes a need for high performance drivers that will not degrade the analog signal to the converter. It is desirable from a system's standpoint that the ADC be the element in the signal chain that ultimately limits overall distortion. Figure 66 is such an example. The specified high speed performance of the AD9631/AD9632 requires careful attention to board layout and component selection. Proper RF design techniques and low-pass parasitic component selection are mandatory. 140 +5V 130 ADC -5V Figure 66. AD9631 Used as Driver for an ADC Signal Chain 00601-066 ANALOG IN AD9631 The PCB should have a ground plane covering all unused portions of the component side of the board to provide a low impedance path. Remove the ground plane from the area near the input pins to reduce stray capacitance. Use chip capacitors for supply bypassing (see Figure 59 and Figure 60). Connect one end to the ground plane, and the other within 1/8 inch of each power pin. Connect an additional large (0.47 F to 10 F) tantalum electrolytic capacitor in parallel, though not necessarily so close, to supply current for fast, large signal changes at the output. The feedback resistor should be located close to the inverting input pin to keep the stray capacitance at this node to a minimum. Capacitance variations of less than 1 pF at the inverting input will significantly affect high speed performance. Use stripline design techniques for long signal traces (greater than about 1 inch). These should be designed with a characteristic impedance of 50 or 75 and be properly terminated at each end. Rev. D | Page 18 of 20 Data Sheet AD9631/AD9632 OUTLINE DIMENSIONS 0.400 (10.16) 0.365 (9.27) 0.355 (9.02) 8 5 1 4 0.280 (7.11) 0.250 (6.35) 0.240 (6.10) 0.100 (2.54) BSC 0.325 (8.26) 0.310 (7.87) 0.300 (7.62) 0.060 (1.52) MAX 0.210 (5.33) MAX 0.015 (0.38) MIN 0.150 (3.81) 0.130 (3.30) 0.115 (2.92) SEATING PLANE 0.022 (0.56) 0.018 (0.46) 0.014 (0.36) 0.195 (4.95) 0.130 (3.30) 0.115 (2.92) 0.015 (0.38) GAUGE PLANE 0.014 (0.36) 0.010 (0.25) 0.008 (0.20) 0.430 (10.92) MAX 0.005 (0.13) MIN 0.070 (1.78) 0.060 (1.52) 0.045 (1.14) 070606-A COMPLIANT TO JEDEC STANDARDS MS-001 CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. CORNER LEADS MAY BE CONFIGURED AS WHOLE OR HALF LEADS. Figure 67. 8-Lead Plastic Dual In-Line Package [PDIP] Narrow Body (N-8) Dimensions shown in inches and (millimeters) 5.00 (0.1968) 4.80 (0.1890) 1 5 4 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) COPLANARITY 0.10 SEATING PLANE 6.20 (0.2441) 5.80 (0.2284) 1.75 (0.0688) 1.35 (0.0532) 0.51 (0.0201) 0.31 (0.0122) 0.50 (0.0196) 0.25 (0.0099) 45 8 0 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) COMPLIANT TO JEDEC STANDARDS MS-012-AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 68. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches) Rev. D | Page 19 of 20 012407-A 8 4.00 (0.1574) 3.80 (0.1497) AD9631/AD9632 Data Sheet ORDERING GUIDE Model1 AD9631ANZ AD9631AR AD9631AR-REEL AD9631AR-REEL7 AD9631ARZ AD9631ARZ-REEL AD9631ARZ-REEL7 AD9631AR-EBZ AD9631ACHIPS AD9632ANZ AD9632AR AD9632ARZ AD9632ARZ-REEL AD9632ARZ-REEL7 AD9632AR-EBZ 1 Temperature Range -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C -40C to +85C Package Description 8-Lead Plastic Dual In-Line Package [PDIP] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] AD9631 Evaluation Board Die 8-Lead Plastic Dual In-Line Package [PDIP] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] 8-Lead Standard Small Outline Package [SOIC_N] AD9632 Evaluation Board Z = RoHS Compliant Part. (c)2014 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D00601-0-2/14(D) Rev. D | Page 20 of 20 Package Option N-8 R-8 R-8 R-8 R-8 R-8 R-8 N-8 R-8 R-8 R-8 R-8 Mouser Electronics Authorized Distributor Click to View Pricing, Inventory, Delivery & Lifecycle Information: Analog Devices Inc.: AD9632AR-EBZ AD9631AR-EBZ