X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
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P
PF
FE
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May 2018
Rev. 1.1.1
1/12 Rev. 1.1.1
GENERAL DESCRIPTION
The XRP6124 is a non synchronous step down
(buck) controller for up to 5Amps point of
loads. A wide 3V to 30V input voltage range
allows for single supply operations from
industry standard 3.3V, 5V, 12V and 24V
powe r rails.
With a proprietary Constant On-Time (COT)
control scheme, the XRP6124 provides
extremely fast line and load transient response
while the operating frequency remains nearly
constant. It requires no loop compensation
hence simplifying circuit implementation and
reducing overall component count. The
XRP76124 also implements an emulated ESR
circuitry allowing usage of ceramic output
capacitors and insuring stable operations
without the u se of extra external components.
Built-in sof t start prevents high inrush currents
while under voltage lock-out and output short
protections insure safe operations under
abnormal operating conditions.
The XRP6124 is avail able in a RoHS compliant,
green/halogen free space-saving 5-pin SOT23
package.
APPLICATIONS
• Point of Load Conversions
• Audio-Video Equipment
• Industrial and Medical Equipment
• Distributed Power Architecture
FEATURES
• 5A Point-of-Load Capable
− Down to 1.2V Output Voltage Conversion
• Wide Input Voltage Range
− 3V to 18V: XRP6124
− 4.5V to 30V: XRP6124HV
• Constant On-Time Operations
− Constant Fre quency Operations
− No External Compensation
− Supports Ceram ic Output Capacitors
• Built-in 2ms Soft Start
• Short Circuit Protection
• <1µA shutdown current
• RoHS Compliant, Green/Halogen Free
5-pin SOT23 Package
TYPICAL APPLICATION DIAGRAM
Figure 1: XRP6124 Application Diagr a m
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
n-
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Sy
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hr
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no
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P
PF
FE
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2/12 Rev. 1.1.1
ABSOLUTE MAXIMUM RATINGS
These are stress ratings only and functional operation of
the device at these ratings or any other above those
indicated in the operation sections of the specifications
below is not implied. Exposure to absolute maximum
rating conditions for extended periods of time may affect
reliability.
VIN (XRP6124) ............................................ -0.3V to 20V
VIN (XRP6124HV) ........................................ -0.3V to 32V
GATE ...................................................... VIN-GATE<8V
FB, EN ..................................................... -0.3V to 5.5V
Stor age Temperature .............................. -65°C to 150°C
Power Dissipation ................................ I nte rnally Limited
Lead Tempera tur e (Soldering, 10 sec) ................... 300°C
ESD Rating (HBM - Human Body Model) .................... 2kV
OPERATING RATINGS
Input Voltage Range VIN (XRP6124) ................ 3.0V to 18V
Input Voltage Range VIN (XRP6124HV) ............ 4.5V to 30 V
Junction Temperature Range .................... -40°C to 125°C
Thermal Resistance θJA .....................................191°C/W
ELECTRICAL SP ECIFICATIONS
Spec ificatio ns are for an Operating Junction Temp erature of TJ = 25°C only; limits applying ov er the full Oper ating Junction
Temperature range are denoted by a “•”. Minimum and Maximum limits are guaranteed through test, design, or statistical
corre lation. Typical value s represent the most likely par ametric norm at TJ = 25°C, and are provided for reference purposes
only. Unle s s other w ise indicated, VIN = 3.0V to 18V, TJ = –40°C to 125°C.
Parameter Min. Typ. Max. Units Conditions
UVLO Turn-On Thr eshold
2.5
2.8
3.0
V
•
XRP6124
UVLO Turn-On Thr eshold
3.8
4.2
4.5
V
•
XRP6124HV
UVLO Hysteresis
0.1
V
Operating Input Voltage Range
3.0
18
V
•
XRP6124
4.5 30 V • XRP6124HV
Shutdown VIN Current
1.5
3
µA
EN=0V, V
IN
=12V
Operating VIN Current
0.5
1
mA
VFB=1 .2V and after fault
Reference Voltage
0.792
0.8
0.808
V
0.784
0.8
0.816
V
•
VSC_TH, Fe edb ack pin S hor t
Circuit La tc h Threshold 0.50 0.55 0.65 V •
T
ON
, Switch On-Time
0.4
0.5
0.6
µs
•
V
IN
=12V, XR P 6124
T
ON
, Switch On-Time
0.4
0.5
0.6
µs
•
V
IN
=24V, XRP6124HV
TOFF_MIN, Minimum Off-Time
250
350
ns
•
VIN=12V
Soft Start Time
2
ms
EN Turn-On Thres hold 2 V
EN Turn-Off Threshold
1
V
EN Bias Current
0.01
0.1
µA
Gate Driver Pull-Down
Resistance
6 9 Ω
Gate Driver Pull-up Resistance
5
8
Ω
tr, gate ris e time
45
ns
CGATE=1nF
tf, gate fall tim e
35
ns
C
GATE
=1nF
VIN - GATE voltag e di fference
5.5
6.4
8
V
•
VIN=12V
VIN - GATE voltag e di fference
2.6
V
•
VIN=3.0V
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
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-S
Sy
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no
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P
PF
FE
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3/12 Rev. 1.1.1
BLOCK DIAGRAM
VREF
0.8V
Enable
FB
+
-
+
-
0.55V
UVLO
FAULT
BIAS
SS Done
GATE
VIN
GND
Improved COT with
Emulated ESR
VIN-6V
Figure 2: XRP6124 Block Dia gram
PIN ASSIGNMENT
Figure 3: XRP6124 Pin Assignment
PIN DESCRIPTION
Name P in Numb er Description
EN
1
Enable Pin. Ac tive ly pull hig h to enable the part.
GND
2
Ground
FB
3
Feedback pin
GATE 4
Gate Pin. Connec t to gate of PFET. This pin pulls the gate of the PFET appro x im ate ly
6V below Vin in order to tur n on the FET. For 6V>VIN>3 V the gate pulls to w ithin 0 .4V
of ground . Ther efore a PFET with a gate rating of 2.6V or lower should be used.
VIN
5
Input Voltage
ORDERING INFORMATION(1)
Part Number Operating
Temperature Range Lead-Free Package Pack in g Met hod Note 1
XRP6124ESTR0.5-F
-40°C≤TJ≤125°C Yes(2) 5-pin SOT23 Tape & Reel
0.5µs/18 V m ax
XRP6124HVESTR0.5-F
0.5µs/30 V m ax
XRP6124EVB XRP6124 Evaluation Board
XRP6124HVEVB
XRP6124HV Evaluation Board
NOTES:
1.Refer to www.exar.com/XRP6124 for most up-to-date Ordering Information
2. Visit www.exar.com for additional info rmation on Environmental Rating.
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
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Sy
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hr
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no
ou
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s
P
PF
FE
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4/12 Rev. 1.1.1
TYPICA L P ERFORMANCE CHARACTERISTICS
All data taken at TJ = TA = 25°C, unless otherwise specified – Curves are based on Schematic and BOM from Application
Information section of this datasheet. Refer to figure 20 for XRP6124 and to figure 21 for XRP6124HV.
Fig. 4: Efficiency versus IOUT, VIN=12V
Fig. 5: Efficiency versus IOUT, VIN=24V
Fig. 6: TON ver sus VIN
Fig. 7: TON ver sus VIN
Fig. 8: Load Regulation
Fig. 9: Load Regulation
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
n-
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Sy
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hr
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no
ou
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s
P
PF
FE
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5/12 Rev. 1.1.1
Fig. 10: Line Regulation
Fig. 11: Line Regulation
Fig. 12: Steady state, VIN = 12V, VOUT = 3.3V, IOU T= 3A
Fig. 13: Steady state, VIN = 24V, VOUT = 5.0V, IOUT = 3A
Fig. 14: Load step transient response, 1.4A-3A-1.4A
Fig. 15: Load step transient resp onse, 1.4A-3A-1.4A
XRP6124HVES0.5-F
XRP6124ES0.5-F
V
OUT
AC coupled
10mV/div
LX
10V/div
IL
2A/div
LX
20V/div
V
OUT
AC coupled
20mV/div
IL
2A/div
XRP6124ES0.5-F
1µs/div
2µs/div
XRP6124ES0.5-F
XRP6124HVES0.5-F
V
OUT
AC coupled
100mV/div
V
OUT
AC coupled
200mV/div
I
OUT
1A/div
I
OUT
1A/div
10µs/div
20µs/div
90mV
180mV
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
n-
-S
Sy
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nc
ch
hr
ro
on
no
ou
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s
P
PF
FE
ET
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6/12 Rev. 1.1.1
Fig. 16: Load step transient resp onse corresponding to a
CCM-DCM transition, 0.05A-1.6A-0.05A
Fig. 17: Load step transient resp onse corresponding to a
CCM-DCM transition, 0.05A-1.6A-0.05A
Fig. 18: Shutdown current versus VIN, VEN = 0V
Fig. 19: Shutdown current versus VIN, VEN = 0V
XRP6124ES0.5-F
XRP6124HVES0.5-F
V
OUT
AC coupled
100mV/div
V
OUT
AC coupled
200mV/div
I
OUT
1A/div
I
OUT
1A/div
50µs/div
50µs/div
90mV
180mV
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
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Sy
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no
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P
PF
FE
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7/12 Rev. 1.1.1
THEORY OF OPERATION
THEORY OF OPERATION
The XRP6124 utilizes a proprietary Constant
On-Time (COT) control with emulated ESR.
The on-t ime i s intern ally set and automatically
adjusts during operation, inversely with the
voltage VIN, in order to maintain a constant
frequency. Therefore the switching frequency
is independent of the inductor and capacitor
size, unlike hysteretic controllers. The
emulated ESR ramp allows the use of ceramic
capaci t ors fo r output filtering.
At the beginning of each cycle, the XRP6124
turns on the P-Channel FET for a fixed
duration. The on-time is internally set and
adjusted by VIN. At the end of the on-time the
FET is turned off, for a predetermined
minimum off time TOFF-MIN (nominally 250ns).
After the TOFF-MIN has expired the voltage at
feedback pin FB is compared to a voltage
ramp at the feedback comparators positive
input. Once VFB drops below the ramp voltage,
the FET is turned on and a new cycle starts.
This voltage ramp constitutes an emulated
ESR and makes possible the use of ceramic
capacitors, in addition to other capacitors, as
output filter for the buck converter.
VOLTAGE OPTIONS
The XRP6124 is available in two voltage
options as shown in table 1. The low-voltage
and high-voltage options have TON of 0.5µs at
12VIN and 24VIN respectively. Note that TON is
inversely proportional to VIN. The constant of
proportionality K, for each voltage option is
shown in table 1. Vari ation of TON versu s VIN is
shown g raphically i n figures 6 and 7.
Voltage
rating (V) Part Number TON (µs) K=TONxVIN
(μs.V)
3-18
XRP6124ES0.5-F
0.5 @ 12VIN
6
4.5-30
XRP6124HVES0.5-F
0.5 @ 24VIN
12
Table 1 : XRP6124 voltage options
For a buck co nverter the switching frequency
fs can be expressed in terms of VIN, VOUT and
TON as follows:
ONIN
OUT
TV V
fs ×
=
Since for each voltage option, the product of
VIN and TON is the constant K shown in table 1,
then switching frequency is determined by
VOUT as shown in table 2.
VOUT Switching frequency fs(kHz)
XRP6124ES0.5-F XRP6124HVES0.5-F
1.2
200
100
1.5
250
125
1.8
300
150
2.5
417
208
3.3 550 275
5.0
833
417
12
---
1000
Table 2: Switching fr eque nc y fs
for the XRP6124 voltage options
Where it is advantageous, the high-voltage
option may be used for low-voltage
applications. For example a 12VIN to 5VOUT
conversion using a low-voltage option will
result in switching frequency of 833kHz as
shown in table 2. If it is desired to increase
the converter efficiency, then switching losses
can be reduced in half by using a high-voltage
option operating at a switching frequency of
417kHz.
VOUT Max imum Output Current IOUT(A)
XRP6124ES0.5-F XRP6124HVES0.5-F
3.3VIN
5.0VIN
12VIN
18VIN
24VIN
1.2 5 5 4 --- ---
1.5
5
5
4
4
---
1.8
5
5
4
4
4
2.5
4
4
4
4
4
3.3
---
4
3
4
4
5.0
---
---
3
3
3
12
---
---
---
2
2
Table 3: Maximum recommended IOUT
SHORT-CIRCUIT PROTECTION
The purpose of this feature is to prevent an
accidental short-circuit at the output from
damaging the converter. The XRP6124 has a
short-circuit comparator that constantly
monitors the feedback node, after soft-start is
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
n-
-S
Sy
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hr
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on
no
ou
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P
PF
FE
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8/12 Rev. 1.1.1
finished. If the feedback voltage drops below
0.55V, equivalent to output voltage dropping
below 69% of nominal, the comparator will
trip causing the IC to latch off. In order to
restart the XRP6124, the input voltage has to
be reduced below UVLO threshold and then
increased to its normal operating point.
SOFT-START
To limit in-rush current the XRP6124 has an
internal soft-start. The nominal soft-start time
is 2ms and commences when VIN exceeds the
UVLO threshold. As explained above, the
short-circuit comparator is enabled as soon as
soft-start is complete. Therefore if the input
voltage has a very slow rising edge such that
at the end of soft-start the output voltage has
not reached 69% of its final value then the
XRP6124 will latch-off.
ENABLE
By applying a logic-level signal to the enable
pin EN the XRP6124 can be turned on and off.
Pulling the enable below 1V shuts down the
controller and reduces the VIN leakage current
to 1.5µA nominal as seen in figure 18. Enable
signal should always be applied after the input
voltage or concurrent with it. Otherwise
XRP6124 will latch up. In applications where
an independent enable signal is not available,
a Zener diode can be used to derive VEN from
VIN.
DISCONTINUOUS CONDUCTION MODE, DCM
Because XRP6124 is a non-synchronous
contr oll er, when l oad curr ent IOUT is redu ced to
less than half of peak-to-peak i ndu ctor cu rrent
ripple ΔIL, the converter enters DCM mode of
operation. The switching frequency fs is now
IOUT dependent and no longer g overned by the
relationship shown in table 2. As IOUT is
decreased so does fs until a minimum
switching frequency, typically in the range of
few h undred Hertz , is reached at n o load. This
contributes to good converter efficiency at
light load as seen in figures 4 and 5. The
reduced fs corresponding to light load,
however, increases the output voltage ripple
and causes a slight increase in output voltage
as seen in figures 8 and 9. Another effect of
reduced fs at light load is slow down of
transient response when a load step
transitions from a high load to a light load.
This is shown in figures 16 and 17.
APPLICATION INFORMATION
SETTING THE OUTP UT VOLTAGE
Use an external resistor divider to set the
output voltage. Program the output voltage
from:
−×= 1
8.0
21
OUT
V
RR
where:
R1 is the resisto r between VOUT and FB
R2 is the resistor between FB and GND
(nominally 2kΩ)
0.8V is the nominal fee db a ck voltage.
FEED-FORW ARD CAPACITOR CFF
CFF, which is placed in parallel with R1,
provides a low-impedance/high-frequency
path for the output voltage ripple to be
transmitted to FB. It also helps get an
optimum transient response. An initial value
for CFF can be calculated from:
11.
02 1Rfs
CFF ××××
=
π
where:
fs is the switching frequency from table 2
This value can be adjusted as necessary to
provide an optimum load step transient
response.
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
n-
-S
Sy
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no
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PF
FE
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9/12 Rev. 1. 1.1
OUTPUT INDUCTOR
Select the output inductor L1 for inductance L,
DC current rating IDC and saturation current
rating ISAT. IDC should be larger than regulator
output current. ISAT, as a rule of thumb, should
be 50% higher than the regulator output
current. Calculate the inductance from:
( )
××∆
−=
INL
OUT
OUTIN
VfsIV
VVL
Where:
ΔIL is peak-to-peak inductor current ripple
nominally set to 30% of IOUT
fS is no minal switching frequency from table 2
OUTPUT CAPACITOR COUT
Select the output capacitor for voltage rating,
capacitance COUT and Equivalent Series
Resistance ESR. The voltage rating, as a rule
of thumb, should be twice the output voltage.
When calculating the required capacitance,
usually the overriding requirement is current
load-step transient. If the unloading transient
requirement (i.e., when IOUT transitions from a
high to a low current) is met, then usually the
loading transient requirement (when IOUT
transitions fr om a low to a high current) is me t
as well. Therefore calculate the COUT
capacitance based on the unloading transient
requirement from:
( )
−+
−
×=
22
22
OUT
transientOUT
LOWHigh
OUT
VVV
II
LC
Where:
L is the inductance calculated in the preceding
step
IHigh is the value of IOUT prior to unloading. This
is nominally set equal to regulator current
rating.
ILow is t he value of IOUT after unloading. This is
nominally set equal to 50% of regulator
current rating.
Vtransient is the maximum permissible voltage
transient corresponding to the load step
ment ioned a bove. Vtransient is typically specified
from 3% to 5% of VOUT.
ESR of the capacitor has to be selected such
that the output voltage ripple requirement
VOUT(ripple), nominally 1% of VOUT, is met.
Voltage ripple VOUT(ripple) is composed mainly of
two components: the resistive ripple due to
ESR and capacitive ripple due to COUT charge
transfer. For applications requiring low voltage
ripple, ceramic capacitors are recommended
because of their low ESR which is typically in
the range of 5mΩ. Therefore VOUT(ripple) is
mainly capacitive. For ceramic capacitors
calculate the VOUT(ripple) from:
fsCI
OUT
L
××
∆
=8
V
)OUT(ripple
Where:
COUT is the va lue calculated above
If tantalum or electrolytic capacitors are used
then VOUT(ripple) is essential ly a function of ESR:
ESR
IL×
∆
=
V)
OUT(ripple
INPUT CAPACITOR CIN
Select the input capacitor for voltage rating,
RMS current rating and capacitance. The
voltage rating, as a rule of thumb, should be
50% higher than the regulator’s maximum
input voltage. Calculate the capacitor’s current
rating from:
( )
DDI
OUT
−××= 1 I
RMSCIN,
Where:
IOUT is regulator’s maximum current
D is duty cycle (D=VOUT/VIN)
Calculate the CIN capacitance from:
( )
ININ
OUTINOUTOUT
VVfs
VVVI
∆××
−××
=
2
IN
C
Where:
ΔVIN is the permissible input voltage ripple,
nominally set to 1% of VIN.
X
X
R
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P
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6
1
1
2
2
4
4
N
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on
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-S
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PF
FE
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10/12 Rev . 1.1.1
TYPICAL APPLICATIONS
12V TO 3.3V / 3A CONVERSION
XRP6124ES
VIN
GND
GATEFB
EN
D1
MBRA340
L1, 4.7uH
DR74-4R7-R
M1
IRF9335
R1, 1%
6.34k
R2, 1%
2k
CFF
1nF
1
2
3 4
5
COUT, X5R
2x22uF, 10V
CIN, X5R
22uF, 25V
VIN 6V to 18V
VOUT 3.3V/3A
Fig. 20: 12V to 3.3V/3A regulator
24V TO 5V / 3A CONVERSION
XRP6124HVES
VIN
GND
GATEFB
EN
D1
MBRA340
L1, 8.2uH
HCM0730
M1
DMP4050SSS
R1, 1%
10.5k
R2, 1%
2k
CFF
0.47nF
1
2
3 4
5
C
OUT
, X5R
2x22uF, 16V
C
IN
, X5R
10uF, 50V
V
IN
8V to 30V
V
OUT
5.0V/3A
Fig. 21: 24V to 5V/3A regulator
X
X
R
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P
P
6
6
1
1
2
2
4
4
N
No
on
n-
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Sy
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PF
FE
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r
r
11/12 Rev . 1.1.1
MECHANICAL DIMENSIONS
5-PIN SOT23
X
X
R
R
P
P
6
6
1
1
2
2
4
4
N
No
on
n-
-S
Sy
yn
nc
ch
hr
ro
on
no
ou
us
s
P
PF
FE
ET
T
S
St
te
ep
p-
-D
Do
ow
wn
n
C
Co
on
nt
tr
ro
ol
ll
le
e
r
r
12/12 Rev . 1.1.1
REVISION HISTORY
Revision Date Description
1.0.0
01/26/2011
Initial r e le as e of datas he e t
1.1.0 01/31/2011 Correcte d ty po (c hanged V to I) on formula under Input C apacitor CIN paragraph
1.1.1
05/24/2018
Updated to MaxLinear logo . Updated forma t and Ordering Information.
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