LTC2367IDE-16#PBF - ANALOG DEVICES

LTC2367-16

236716fa

16-Bit, 500ksps, Pseudo-

Differential Unipolar SAR

ADC with 94.7dB SNR

TYPICAL APPLICATION

FEATURES DESCRIPTION

The LTC

2367-16 is a low noise, low power, high speed

16-bit successive approximation register (SAR) ADC.

Operating from a 2.5V supply, the LTC2367-16 has a 0V

to VREF pseudo-differential unipolar input range with VREF

ranging from 2.5V to 5.1V. The LTC2367-16 consumes

only 6.8mW and achieves ±0.75LSB INL maximum, no

missing codes at 16 bits with 94.7dB SNR.

The LTC2367-16 has a high speed SPI-compatible serial

interface that supports 1.8V, 2.5V, 3.3V and 5V logic

while also featuring a daisy-chain mode. The fast 500ksps

throughput with no cycle latency makes the LTC2367-16

ideally suited for a wide variety of high speed applications.

An internal oscillator sets the conversion time, easing exter-

nal timing considerations. The LTC2367-16 automatically

powers down between conversions, leading to reduced

power dissipation that scales with the sampling rate.

32k Point FFT fS = 500ksps, fIN = 2kHz

APPLICATIONS

n 500ksps Throughput Rate

n ±0.75LSB INL (Max)

n Guaranteed 16-Bit No Missing Codes

n Low Power: 6.8mW at 500ksps, 6.8µW at 500sps

n 94.7dB SNR (Typ) at fIN = 2kHz

n –119dB THD (Typ) at fIN = 2kHz

n Guaranteed Operation to 125°C

n 2.5V Supply

n Pseudo-Differential Unipolar Input Range: 0V to VREF

n VREF Input Range from 2.5V to 5.1V

n No Pipeline Delay, No Cycle Latency

n 1.8V to 5V I/O Voltages

n SPI-Compatible Serial I/O with Daisy-Chain Mode

n Internal Conversion Clock

n 16-Lead MSOP and 4mm × 3mm DFN Packages

n Medical Imaging

n High Speed Data Acquisition

n Portable or Compact Instrumentation

n Industrial Process Control

n Low Power Battery-Operated Instrumentation

n ATE

L, LT, LTC, LTM , Linear Technology and the Linear logo are registered trademarks and

SoftSpan is a trademark of Linear Technology Corporation. All other trademarks are the

property of their respective owners. Protected by U.S. Patents, including 7705765.

10Ω

VREF

10nF

–

SAMPLE CLOCK

236716 TA01a

10µF 0.1µF

2.5V

REF

1.8V TO 5V

2.5V TO 5.1V 47µF

(X5R, 0805 SIZE)

REF GND

CHAIN

RDL/SDI

SDO

SCK

BUSY

CNV

LTC2367-16

LT®6202

VDD OVDD

IN+

IN–

FREQUENCY (kHz)

0 50 100 150 200 250

–180

AMPLITUDE (dBFS)

–60

–40

–20

–80

–100

–120

–140

–160

236716 TA01b

SNR = 94.7dB

THD = –119dB

SINAD = 94.7dB

SFDR = 123dB

LTC2367-16

236716af

PIN CONFIGURATION

ABSOLUTE MAXIMUM RATINGS

Supply Voltage (VDD) ...............................................2.8V

Supply Voltage (OVDD) ................................................6V

Reference Input (REF) .................................................6V

Analog Input Voltage (Note 3)

IN+, IN– .........................(GND – 0.3V) to (REF + 0.3V)

Digital Input Voltage

(Note 3) .......................... (GND – 0.3V) to (OVDD + 0.3V)

Digital Output Voltage

(Note 3) .......................... (GND – 0.3V) to (OVDD + 0.3V)

(Notes 1, 2)

GND

OVDD

SDO

SCK

RDL/SDI

BUSY

GND

CNV

CHAIN

VDD

GND

IN+

IN–

GND

REF

TOP VIEW

DE PACKAGE

16-LEAD (4mm × 3mm) PLASTIC DFN

TJMAX = 150°C, θJA = 40°C/W

EXPOSED PAD (PIN 17) IS GND, MUST BE SOLDERED TO PCB

CHAIN

VDD

GND

IN+

IN–

GND

REF

GND

OVDD

SDO

SCK

RDL/SDI

BUSY

GND

CNV

TOP VIEW

MS PACKAGE

16-LEAD PLASTIC MSOP

TJMAX = 150°C, θJA = 110°C/W

ORDER INFORMATION

LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE

LTC2367CMS-16#PBF LTC2367CMS-16#TRPBF 236716 16-Lead Plastic MSOP 0°C to 70°C

LTC2367IMS-16#PBF LTC2367IMS-16#TRPBF 236716 16-Lead Plastic MSOP –40°C to 85°C

LTC2367HMS-16#PBF LTC2367HMS-16#TRPBF 236716 16-Lead Plastic MSOP –40°C to 125°C

LTC2367CDE-16#PBF LTC2367CDE-16#TRPBF 23676 16-Lead (4mm × 3mm) Plastic DFN 0°C to 70°C

LTC2367IDE-16#PBF LTC2367IDE-16#TRPBF 23676 16-Lead (4mm × 3mm) Plastic DFN –40°C to 85°C

Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping

container.

Consult LTC Marketing for information on non-standard lead based finish parts.

For more information on lead free part marking, go to: http://www.linear.com/leadfree/

For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/

Power Dissipation .............................................. 500mW

Operating Temperature Range

LTC2367C ................................................ 0°C to 70°C

LTC2367I .............................................–40°C to 85°C

LTC2367H .......................................... –40°C to 125°C

Storage Temperature Range .................. –65°C to 150°C

LTC2367-16

236716fa

DYNAMIC ACCURACY

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

SINAD Signal-to-(Noise + Distortion) Ratio fIN = 2kHz, VREF = 5V l91.9 94.7 dB

fIN = 2kHz, VREF = 5V, (H-Grade) l91.7 94.7 dB

SNR Signal-to-Noise Ratio fIN = 2kHz, VREF = 5V

fIN = 2kHz, VREF = 2.5V

92.5

87.7

94.7

90.7

fIN = 2kHz, VREF = 5V, (H-Grade)

fIN = 2kHz, VREF = 2.5V, (H-Grade)

92.2

87.3

94.7

90.7

THD Total Harmonic Distortion fIN = 2kHz, VREF = 5V

fIN = 2kHz, VREF = 2.5V

–119

–102

SFDR Spurious Free Dynamic Range fIN = 2kHz, VREF = 5V l103 122 dB

–3dB Input Bandwidth 34 MHz

Aperture Delay 500 ps

Aperture Jitter 4 ps

Transient Response Full-Scale Step 1.46 µs

The l denotes the specifications which apply over the full operating temperature range,

otherwise specifications are at TA = 25°C and AIN = –1dBFS. (Notes 4, 8)

ELECTRICAL CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VIN+ Absolute Input Range (IN+) (Note 5) l–0.1 VREF + 0.1 V

VIN– Absolute Input Range (IN–) (Note 5) l–0.1 0.1 V

VIN+ – VIN– Input Differential Voltage Range VIN = VIN+ – VIN–l0 VREF V

IIN Analog Input Leakage Current l±1 µA

CIN Analog Input Capacitance Sample Mode

Hold Mode

CMRR Input Common Mode Rejection Ratio fIN = 250kHz 80 dB

The l denotes the specifications which apply over the full operating

temperature range, otherwise specifications are at TA = 25°C. (Note 4)

CONVERTER CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

Resolution l16 Bits

No Missing Codes l16 Bits

Transition Noise 0.5 LSBRMS

INL Integral Linearity Error (Note 6) l–0.75 ±0.1 0.75 LSB

DNL Differential Linearity Error l–0.5 ±0.1 0.5 LSB

ZSE Zero-Scale Error (Note 7) l–4 0 4 LSB

Zero-Scale Error Drift 4 mLSB/°C

FSE Full-Scale Error (Note 7) l–20 ±2 20 LSB

Full-Scale Error Drift ±0.1 ppm/°C

The l denotes the specifications which apply over the full operating

temperature range, otherwise specifications are at TA = 25°C. (Note 4)

LTC2367-16

236716af

REFERENCE INPUT

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VREF Reference Voltage (Note 5) l2.5 5.1 V

IREF Reference Input Current (Note 9) l0.24 0.32 mA

The l denotes the specifications which apply over the full operating temperature range, otherwise

specifications are at TA = 25°C. (Note 4)

DIGITAL INPUTS AND DIGITAL OUTPUTS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VIH High Level Input Voltage l0.8 • OVDD V

VIL Low Level Input Voltage l0.2 • OVDD V

IIN Digital Input Current VIN = 0V to OVDD l–10 10 µA

CIN Digital Input Capacitance 5 pF

VOH High Level Output Voltage IO = –500µA lOVDD – 0.2 V

VOL Low Level Output Voltage IO = 500µA l0.2 V

IOZ Hi-Z Output Leakage Current VOUT = 0V to OVDD l–10 10 µA

ISOURCE Output Source Current VOUT = 0V –10 mA

ISINK Output Sink Current VOUT = OVDD 10 mA

The l denotes the specifications which apply over the

full operating temperature range, otherwise specifications are at TA = 25°C. (Note 4)

ADC TIMING CHARACTERISTICS

The l denotes the specifications which apply over the full operating

temperature range, otherwise specifications are at TA = 25°C. (Note 4)

POWER REQUIREMENTS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VDD Supply Voltage l2.375 2.5 2.625 V

OVDD Supply Voltage l1.71 5.25 V

IVDD

IOVDD

IPD

Supply Current

Power Down Mode

500ksps Sample Rate

500ksps Sample Rate (CL = 20pF)

Conversion Done (IVDD + IOVDD + IREF, VREF > 2V)

Conversion Done (IVDD + IOVDD + IREF, VREF > 2V, H-Grade)

2.7

0.1

0.9

3.2

140

µA

PDPower Dissipation

Power Down Mode

500ksps Sample Rate

Conversion Done (IVDD + IOVDD + IREF, VREF > 2V)

Conversion Done (IVDD + IOVDD + IREF, VREF > 2V, H-Grade)

6.75

2.25

225

315

µW

The l denotes the specifications which apply over the full operating temperature

range, otherwise specifications are at TA = 25°C. (Note 4)

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

fSMPL Maximum Sampling Frequency l500 ksps

tCONV Conversion Time l1 1.5 µs

tACQ Acquisition Time tACQ = tCYC – tHOLD (Note 10) l1.460 µs

tHOLD Maximum Time Between Acquisitions l540 ns

tCYC Time Between Conversions l2 µs

tCNVH CNV High Time l20 ns

tBUSYLH CNV↑ to BUSY Delay CL = 20pF l13 ns

tCNVL Minimum Low Time for CNV (Note 11) l20 ns

tQUIET SCK Quiet Time from CNV↑(Note 10) l20 ns

LTC2367-16

236716fa

ADC TIMING CHARACTERISTICS

The l denotes the specifications which apply over the full operating

temperature range, otherwise specifications are at TA = 25°C. (Note 4)

Note 1: Stresses beyond those listed under Absolute Maximum Ratings

may cause permanent damage to the device. Exposure to any Absolute

Maximum Rating condition for extended periods may effect device

reliability and lifetime.

Note 2: All voltage values are with respect to ground.

Note 3: When these pin voltages are taken below ground or above REF or

OVDD, they will be clamped by internal diodes. This product can handle

input currents up to 100mA below ground or above REF or OVDD without

latch-up.

Note 4: VDD = 2.5V, OVDD = 2.5V, REF = 5V, fSMPL = 500kHz.

Note 5: Recommended operating conditions.

Note 6: Integral nonlinearity is defined as the deviation of a code from a

straight line passing through the actual endpoints of the transfer curve.

The deviation is measured from the center of the quantization band.

Note 7: Zero-scale error is the offset voltage measured from 0.5LSB

when the output code flickers between 0000 0000 0000 0000 and

0000 0000 0000 0001. Full-scale error is the deviation of the last code

transition from ideal and includes the effect of offset error.

Note 8: All specifications in dB are referred to a full-scale 5V input with a

5V reference voltage.

Note 9: fSMPL = 500kHz, IREF varies proportionately with sample rate.

Note 10: Guaranteed by design, not subject to test.

Note 11: Parameter tested and guaranteed at OVDD = 1.71V, OVDD = 2.5V

and OVDD = 5.25V.

Note 12: tSCK of 10ns maximum allows a shift clock frequency up to

100MHz for rising capture.

Figure 1. Voltage Levels for Timing Specifications

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

tSCK SCK Period (Notes 11, 12) l10 ns

tSCKH SCK High Time l4 ns

tSCKL SCK Low Time l4 ns

tSSDISCK SDI Setup Time From SCK↑(Note 11) l4 ns

tHSDISCK SDI Hold Time From SCK↑(Note 11) l1 ns

tSCKCH SCK Period in Chain Mode tSCKCH = tSSDISCK + tDSDO (Note 11) l13.5 ns

tDSDO SDO Data Valid Delay from SCK↑CL = 20pF (Note 11) l9.5 ns

tHSDO SDO Data Remains Valid Delay from SCK↑CL = 20pF (Note 10) l1 ns

tDSDOBUSYL SDO Data Valid Delay from BUSY↓CL = 20pF (Note 10) l5 ns

tEN Bus Enable Time After RDL↓(Note 11) l16 ns

tDIS Bus Relinquish Time After RDL↑ (Note 11) l13 ns

0.8*OVDD

0.2*OVDD

50% 50%

236716 F01

0.2*OVDD

0.8*OVDD

0.2*OVDD

0.8*OVDD

tDELAY

tWIDTH

tDELAY

LTC2367-16

236716af

TYPICAL PERFORMANCE CHARACTERISTICS

32k Point FFT fS = 500ksps,

fIN = 2kHz SNR, SINAD vs Input Frequency

THD, Harmonics

vs Input Frequency

SNR, SINAD vs Input level,

fIN = 2kHz

SNR, SINAD vs Reference

Voltage, fIN = 2kHz

THD, Harmonics vs Reference

Voltage, fIN = 2kHz

Integral Nonlinearity

vs Output Code

Differential Nonlinearity

vs Output Code DC Histogram

TA = 25°C, VDD = 2.5V, OVDD = 2.5V, REF = 5V,

fSMPL = 500ksps, unless otherwise noted.

CODE

32676

COUNTS

20000

30000

40000

50000

60000

70000

32677 32678

236716 G03

80000

90000

100000

σ = 0.5

10000

32679 32680

REFERENCE VOLTAGE (V)

2.5

HARMONICS, THD (dBFS)

–120

–110

3RD

–100

4.5

236716 G09

–130

–140

–125

–115

–105

–135

–145

–150 33.5 45

2ND

THD

OUTPUT CODE

0 16384 32768 49152 65536

–1.0

INL ERROR (LSB)

0.0

0.4

0.2

0.6

0.8

–0.2

–0.4

–0.8

–0.6

1.0

236716 G01

OUTPUT CODE

–0.5

DNL ERROR (LSB)

0.4

0.3

0.2

0.1

0.0

–0.4

–0.3

–0.2

–0.1

0.5

236716 G02

0 16384 32768 49152 65536

FREQUENCY (kHz)

0 50 100 150 200 250

–180

AMPLITUDE (dBFS)

–60

–40

–20

–80

–100

–120

–140

–160

236716 G04

SNR = 94.7dB

THD = –119dB

SINAD = 94.7dB

SFDR = 123dB

FREQUENCY (kHz)

SNR, SINAD (dBFS)

50 100 150 200

236716 G05

100

SNR

25 75 125 175

SINAD

FREQUENCY (kHz)

–160

HARMONICS, THD (dBFS)

–150

–130

–120

–110

–60

THD

2ND

3RD

–90

50 100 125

236716 G06

–140

–80

–70

–100

25 75 150 175 200

INPUT LEVEL (dB)

–40

93.0

SNR, SINAD (dBFS)

93.5

94.0

94.5

95.0

SINAD

95.0

95.5

–30 –20 –10 0

236716 G07

SNR

REFERENCE VOLTAGE (V)

2.5

SNR SINAD

4.5

236716 G08

3 3.5 4 5

SNR, SINAD (dBFS)

LTC2367-16

236716fa

SNR, SINAD vs Temperature,

fIN = 2kHz

THD, Harmonics vs Temperature,

fIN = 2kHz

TYPICAL PERFORMANCE CHARACTERISTICS

Supply Current vs Temperature

Shutdown Current vs Temperature CMRR vs Input Frequency

Reference Current

vs Reference Voltage

INL/DNL vs Temperature

Full-Scale Error vs Temperature Offset Error vs Temperature

TA = 25°C, VDD = 2.5V, OVDD = 2.5V, REF = 5V,

fSMPL = 500ksps, unless otherwise noted.

TEMPERATURE (°C)

–55

SNR, SINAD (dBFS)

94.0

94.5

95.0

105

236716 G10

93.5

93.0 –15 25 65

–35 125

545 85

96.0

95.5

SNR

SINAD

TEMPERATURE (°C)

–55

–145

HARMONICS, THD (dBFS)

–140

–130

–125

–120

–110

–35 45 85

236716 G11

–135

–115

25 125

–15 565 105

3RD

2ND

THD

TEMPERATURE (°C)

–55

–1.0

INL/DNL ERROR (LSB)

–0.5

0.5

1.0

–35 –15 5 25

236716 G12

45 65 85 105 125

MAX DNL

MIN DNL

MIN INL

MAX INL

TEMPERATURE (°C)

–55

–10

FULL-SCALE ERROR (LSB)

–2

–4

–6

–8

–35 –15 5 25

236716 G13

45 65 85 105 125

TEMPERATURE (°C)

–55

OFFSET ERROR (LSB)

–4

–2

–15 25 45 125

236716 G14

–35 5 65 85 105

–3

–1

TEMPERATURE (°C)

–55

POWER SUPPLY CURRENT (mA)

2.0

2.5

105

236716 G15

1.5

1.0

0–15 25 65

–35 125

545 85

0.5

3.0

IVDD

IREF IOVDD

TEMPERATURE (°C)

POWER-DOWN CURRENT (µA)

236716 G16

–55 –35 –15 5 25 45 65 85 105 125

IVDD + IOVDD + IREF

FREQUENCY (kHz)

0 50 100 200150 250

CMRR (dB)

100

236716 G17

REFERENCE VOLTAGE (V)

2.5

REFERENCE CURRENT (mA)

0.1

3.5 4.5 5

0.3

236716 G18

3 4

0.2

LTC2367-16

236716af

CHAIN (Pin 1): Chain Mode Selector Pin. When low, the

LTC2367-16 operates in normal mode and the RDL/SDI

input pin functions to enable or disable SDO. When high,

the LTC2367-16 operates in chain mode and the RDL/SDI

pin functions as SDI, the daisy-chain serial data input.

Logic levels are determined by OVDD.

VDD (Pin 2): 2.5V Power Supply. The range of VDD is

2.375V to 2.625V. Bypass VDD to GND with a 10µF ceramic

capacitor.

GND (Pins 3, 6, 10 and 16): Ground.

IN+ (Pin 4): Analog Input. IN+ operates differential with

respect to IN– with an IN+-IN– range of 0V to VREF.

IN– (Pin 5): Analog Ground Sense. IN– has an input range

of ±100mV with respect to GND and must be tied to the

ground plane or a remote ground sense.

REF (Pins 7, 8): Reference Inputs. The range of REF is 2.5V

to 5.1V. This pin is referred to the GND pin and should be

decoupled closely to the pin with a 47µF ceramic capacitor

(X5R, 0805 size).

CNV (Pin 9): Convert Input. A rising edge on this input

powers up the part and initiates a new conversion. Logic

levels are determined by OVDD.

BUSY (Pin 11): BUSY Indicator. Goes high at the start of

a new conversion and returns low when the conversion

has finished. Logic levels are determined by OVDD.

RDL/SDI (Pin 12): When CHAIN is low, the part is in nor-

mal mode and the pin is treated as a bus enabling input.

When CHAIN is high, the part is in chain mode and the

pin is treated as a serial data input pin where data from

another ADC in the daisy chain is input. Logic levels are

determined by OVDD.

SCK (Pin 13): Serial Data Clock Input. When SDO is enabled,

the conversion result or daisy-chain data from another

ADC is shifted out on the rising edges of this clock MSB

first. Logic levels are determined by OVDD.

SDO (Pin 14): Serial Data Output. The conversion result

or daisy-chain data is output on this pin on each rising

edge of SCK MSB first. The output data is in straight binary

format. Logic levels are determined by OVDD.

OVDD (Pin 15): I/O Interface Digital Power. The range of

OVDD is 1.71V to 5.25V. This supply is nominally set to

the same supply as the host interface (1.8V, 2.5V, 3.3V,

or 5V). Bypass OVDD to GND with a 0.1µF capacitor.

GND (Exposed Pad Pin 17, DFN Package Only): Ground.

Exposed pad must be soldered directly to the ground plane.

PIN FUNCTIONS

LTC2367-16

236716fa

FUNCTIONAL BLOCK DIAGRAM

TIMING DIAGRAM

Conversion Timing Using the Serial Interface

REF = 5V

IN+

= 2.5V

OVDD = 1.8V to 5V

IN–

CHAIN

CNV

GND

BUSY

SDO

SCK

RDL/SDI

CONTROL LOGIC

16-BIT SAMPLING ADC SPI

PORT

–

236716 BD

POWER-DOWN

CONVERT

ACQUIRE

HOLD

D13D15 D14 D2 D1 D0

SDO

SCK

CNV

CHAIN, RDL/SDI = 0

BUSY

236716 TD01

LTC2367-16

236716af

OVERVIEW

The LTC2367-16 is a low noise, low power, high speed

16-bit successive approximation register (SAR) ADC.

Operating from a single 2.5V supply, the LTC2367-16

supports a 0V to VREF pseudo-differential unipolar input

range with VREF ranging from 2.5V to 5.1V, making it ideal

for high performance applications which require a wide

dynamic range. The LTC2367-16 achieves ±0.75LSB INL

max, no missing codes at 16 bits and 94.7dB SNR.

Fast 500ksps throughput with no cycle latency makes

the LTC2367-16 ideally suited for a wide variety of high

speed applications. An internal oscillator sets the con-

version time, easing external timing considerations. The

LTC2367-16 dissipates only 6.8mW at 500ksps, while an

auto power-down feature is provided to further reduce

power dissipation during inactive periods.

CONVERTER OPERATION

The LTC2367-16 operates in two phases. During the ac-

quisition phase, the charge redistribution capacitor D/A

converter (CDAC) is connected to the IN+ and IN– pins to

sample the pseudo-differential analog input voltage. A ris-

ing edge on the CNV pin initiates a conversion. During the

conversion phase, the 16-bit CDAC is sequenced through a

successive approximation algorithm, effectively comparing

the sampled input with binary-weighted fractions of the

reference voltage (e.g. VREF/2, VREF/4 … VREF/65536) using

the differential comparator. At the end of conversion, the

CDAC output approximates the sampled analog input. The

ADC control logic then prepares the 16-bit digital output

code for serial transfer.

TRANSFER FUNCTION

The LTC2367-16 digitizes the full-scale voltage of REF

into 216 levels, resulting in an LSB size of 76µV with

REF = 5V. The ideal transfer function is shown in Figure2.

The output data is in straight binary format.

APPLICATIONS INFORMATION

Figure 2. LTC2367-16 Transfer Function

Figure 3. The Equivalent Circuit for the

Differential Analog Input of the LTC2367-16

ANALOG INPUT

The analog inputs of the LTC2367-16 are pseudo-differen-

tial in order to reduce any unwanted signal that is common

to both inputs. The analog inputs can be modeled by the

equivalent circuit shown in Figure 3. The diodes at the input

provide ESD protection. In the acquisition phase, each

input sees approximately 45pF (CIN) from the sampling

CDAC in series with 40Ω (RON) from the on-resistance

of the sampling switch. The IN+ input draws a current

spike while charging the CIN capacitor during acquisition.

During conversion, the analog inputs draw only a small

leakage current.

INPUT VOLTAGE (V)

OUTPUT CODE

236716 F02

111...111

111...110

111...101

111...100

000...001

000...000

000...010

000...011

LSB

UNIPOLAR

ZERO

FS – 1LSB

1LSB = FS/65536

RON

40Ω

CIN

45pF

RON

40Ω

REF

CIN

45pF

IN+

IN–

BIAS

VOLTAGE

236716 F03

LTC2367-16

236716fa

APPLICATIONS INFORMATION

INPUT DRIVE CIRCUITS

A low impedance source can directly drive the high im-

pedance input of the LTC2367-16 without gain error. A

high impedance source should be buffered to minimize

settling time during acquisition and to optimize the dis-

tortion performance of the ADC. Minimizing settling time

is important even for DC inputs, because the ADC input

draws a current spike when entering acquisition.

For best performance, a buffer amplifier should be used

to drive the analog input of the LTC2367-16. The ampli-

fier provides low output impedance, which produces fast

settling of the analog signal during the acquisition phase.

It also provides isolation between the signal source and

the current spike the ADC input draws.

Input Filtering

The noise and distortion of the buffer amplifier and signal

source must be considered since they add to the ADC noise

and distortion. Noisy input signals should be filtered prior

to the buffer amplifier input with an appropriate filter to

minimize noise. The simple 1-pole RC lowpass filter (LPF1)

shown in Figure 4 is sufficient for many applications.

High quality capacitors and resistors should be used in the

RC filters since these components can add distortion. NPO

and silver mica type dielectric capacitors have excellent

linearity. Carbon surface mount resistors can generate

distortion from self heating and from damage that may

occur during soldering. Metal film surface mount resistors

are much less susceptible to both problems.

Pseudo-Differential Unipolar Inputs

For most applications, we recommend the low power

LT6202 ADC driver to drive the LTC2367-16. With a low

noise density of 1.9nV/√Hz and a low supply current of

3mA, the LT6202 is flexible and may be configured to

convert signals of various amplitudes to the 0V to 5V input

range of the LTC2367-16.

To achieve the full distortion performance of the

LTC2367-16, a low distortion single-ended signal source

driven through the LT6202 configured as a unity-gain

buffer as shown in Figure 4 can be used to get the full

data sheet THD specification of –119dB.

The LT6202 can also be used to buffer and convert large

true bipolar signals which swing below ground to the 0V

to 5V input range of the LTC2367-16. Figure 5a shows the

LT6202 being used to convert a ±10V true bipolar signal

for use by the LTC2367-16. In this case, the LT6202 is

configured as an inverting amplifier stage, which acts to

attenuate and level shift the input signal to the 0V to 5V input

range of the LTC2367-16. In the inverting configuration, the

single-ended input signal source no longer directly drives

a high impedance input. The input impedance is instead

set by resistor RIN. RIN must be chosen carefully based on

the source impedance of the signal source. Higher values

of RIN tend to degrade both the noise and distortion of

the LT6202 and LTC2367-16 as a system. Table 1 shows

the resulting SNR and THD for several values of RIN, R1,

R2, R3 and R4 in this configuration. Figure 5b shows the

resulting FFT when using the LT6202 as shown in Figure 5a.

Figure 4. Input Signal Chain

Another filter network consisting of LPF2 should be used

between the buffer and ADC input to both minimize the

noise contribution of the buffer and to help minimize distur-

bances reflected into the buffer from sampling transients.

Long RC time constants at the analog inputs will slow

down the settling of the analog inputs. Therefore, LPF2

requires a wider bandwidth than LPF1. A buffer amplifier

with a low noise density must be selected to minimize

degradation of the SNR.

10Ω

10nF

66nF

50Ω LPF2

LPF1

BW = 1.6MHz

BW = 48kHz LTC2367-16

IN+

IN–

236716 F04

–

LT6202

REF

LTC2367-16

236716af

Table 1. SNR, THD vs RIN for ±10V Input Signal

RIN

(Ω)

SNR

(dB)

THD

(dB)

2k 499 499 2k 402 94.6 –99.2

10k 2.49k 2.49k 10k 2k 94.4 –93.7

100k 24.9k 24.9k 100k 20k 92.8 –93.8

APPLICATIONS INFORMATION

ADC REFERENCE

The LTC2367-16 requires an external reference to define

its input range. A low noise, low temperature drift refer-

ence is critical to achieving the full data sheet performance

of the ADC. Linear Technology offers a portfolio of high

performance references designed to meet the needs of

many applications. With its small size, low power and high

accuracy, the LTC6655-5 is particularly well suited for

use with the LTC2367-16. The LTC6655-5 offers 0.025%

(max) initial accuracy and 2ppm/°C (max) temperature

coefficient for high precision applications. The LTC6655-5

is fully specified over the H-grade temperature range and

complements the extended temperature operation of the

LTC2367-16 up to 125°C. We recommend bypassing the

LTC6655-5 with a 47µF ceramic capacitor (X5R, 0805

size) close to the REF pin.

The REF pin of the LTC2367-16 draws charge (QCONV) from

the 47µF bypass capacitor during each conversion cycle.

The reference replenishes this charge with a DC current,

IREF = QCONV/tCYC. The DC current draw of the REF pin,

IREF, depends on the sampling rate and output code. If

the LTC2367-16 is used to continuously sample a signal

at a constant rate, the LTC6655-5 will keep the deviation

of the reference voltage over the entire code span to less

than 0.5LSBs.

When idling, the REF pin on the LTC2367-16 draws only

a small leakage current (< 1µA). In applications where a

burst of samples is taken after idling for long periods as

shown in Figure 6, IREF quickly goes from approximately

0µA to a maximum of 0.32mA at 500ksps. This step in DC

current draw triggers a transient response in the reference

that must be considered since any deviation in the refer-

ence output voltage will affect the accuracy of the output

Figure 6. CNV Waveform Showing Burst Sampling

Figure 5a. LT6202 Converting a ±10V Bipolar Signal

to a 0V to 5V Input Signal

Figure 5b. 32k Point FFT Plot with fIN = 2kHz

for Circuit Shown in Figure 5a

–

LT6202

402Ω

499Ω

RIN

499Ω

10µF

10V

–10V

200pF

VCM = VREF/2

236716 F05a

FREQUENCY (kHz)

AMPLITUDE (dBFS)

–80

–60

–40

250

236716 F05b

–100

–120

–180

–160

100 200

50 150

–140

–20

SNR = 94.6dB

THD = –99.2dB

SINAD = 92.2dB

SFDR = 99.9dB

CNV

IDLE

PERIOD

IDLE

PERIOD

236716 F06

LTC2367-16

236716fa

APPLICATIONS INFORMATION

code. In applications where the transient response of the

reference is important, the fast settling LTC6655-5 refer-

ence is also recommended.

In applications where power management is critical and

the external reference may be powered down, it is rec-

ommended that REF is kept greater than 2V in order to

guarantee a maximum shutdown current of 140µA. In such

applications, a Schottky diode can be placed between REF

and VDD, as shown in Figure 7.

the RMS amplitude of all other frequency components

except the first five harmonics and DC. Figure 8 shows

that the LTC2367-16 achieves a typical SNR of 94.7dB at

a 500kHz sampling rate with a 2kHz input.

Figure 8. 32k Point FFT with fIN = 2kHz of the LTC2367-16

REF

236716 F07

LTC2367-16

VDD

Figure 7. A Schottky Diode Between REF and VDD Maintains

REF > 2V for Applications Where the Reference May Be

Powered Down

DYNAMIC PERFORMANCE

Fast Fourier Transform (FFT) techniques are used to test

the ADC’s frequency response, distortion and noise at the

rated throughput. By applying a low distortion sine wave

and analyzing the digital output using an FFT algorithm,

the ADC’s spectral content can be examined for frequen-

cies outside the fundamental. The LTC2367-16 provides

guaranteed tested limits for both AC distortion and noise

measurements.

Signal-to-Noise and Distortion Ratio (SINAD)

The signal-to-noise and distortion ratio (SINAD) is the

ratio between the RMS amplitude of the fundamental input

frequency and the RMS amplitude of all other frequency

components at the A/D output. The output is band-limited

to frequencies from above DC and below half the sampling

frequency. Figure 8 shows that the LTC2367-16 achieves

a typical SINAD of 94.7dB at a 500kHz sampling rate with

a 2kHz input.

Signal-to-Noise Ratio (SNR)

The signal-to-noise ratio (SNR) is the ratio between the

RMS amplitude of the fundamental input frequency and

FREQUENCY (kHz)

0 50 100 150 200 250

–180

AMPLITUDE (dBFS)

–60

–40

–20

–80

–100

–120

–140

–160

236716 F08

SNR = 94.7dB

THD = –119dB

SINAD = 94.7dB

SFDR = 123dB

Total Harmonic Distortion (THD)

Total Harmonic Distortion (THD) is the ratio of the RMS sum

of all harmonics of the input signal to the fundamental itself.

The out-of-band harmonics alias into the frequency band

between DC and half the sampling frequency (fSMPL/2).

THD is expressed as:

THD=20log V22+V32+V42+ …+ VN

where V1 is the RMS amplitude of the fundamental fre-

quency and V2 through VN are the amplitudes of the second

through Nth harmonics.

POWER CONSIDERATIONS

The LTC2367-16 provides two power supply pins: the

2.5V power supply (VDD), and the digital input/output

interface power supply (OVDD). The flexible OVDD supply

allows the LTC2367-16 to communicate with any digital

logic operating between 1.8V and 5V, including 2.5V and

3.3V systems.

Power Supply Sequencing

The LTC2367-16 does not have any specific power supply

sequencing requirements. Care should be taken to adhere

LTC2367-16

236716af

APPLICATIONS INFORMATION

to the maximum voltage relationships described in the

Absolute Maximum Ratings section. The LTC2367-16

has a power-on-reset (POR) circuit that will reset the

LTC2367-16 at initial power-up or whenever the power

supply voltage drops below 1V. Once the supply voltage

re-enters the nominal supply voltage range, the POR will

reinitialize the ADC. No conversions should be initiated

until 20µs after a POR event to ensure the reinitialization

period has ended. Any conversions initiated before this

time will produce invalid results.

TIMING AND CONTROL

CNV Timing

The LTC2367-16 conversion is controlled by CNV. A ris-

ing edge on CNV will start a conversion and power up

the LTC2367-16. Once a conversion has been initiated,

it cannot be restarted until the conversion is complete.

For optimum performance, CNV should be driven by a

clean low jitter signal. Converter status is indicated by the

BUSY output which remains high while the conversion is

in progress. To ensure that no errors occur in the digitized

results, any additional transitions on CNV should occur

within 40ns from the start of the conversion or after the

conversion has been completed. Once the conversion has

completed, the LTC2367-16 powers down and begins

acquiring the input signal.

Acquisition

A proprietary sampling architecture allows the LTC2367-16

to begin acquiring the input signal for the next conver-

sion 527ns after the start of the current conversion. This

extends the acquisition time to 1.460µs, easing settling

requirements and allowing the use of extremely low power

ADC drivers. (Refer to the Timing Diagram.)

Internal Conversion Clock

The LTC2367-16 has an internal clock that is trimmed

to achieve a maximum conversion time of 1.5µs.

Auto Power-Down

The LTC2367-16 automatically powers down after a

conversion has been completed and powers up once a

new conversion is initiated on the rising edge of CNV.

During power down, data from the last conversion can

be clocked out. To minimize power dissipation during

power down, disable SDO and turn off SCK. The auto

power-down feature will reduce the power dissipation of

the LTC2367-16 as the sampling frequency is reduced.

Since power is consumed only during a conversion, the

LTC2367-16 remains powered down for a larger fraction of

the conversion cycle (tCYC) at lower sample rates, thereby

reducing the average power dissipation which scales with

the sampling rate as shown in Figure 9.

Figure 9. Power Supply Current of the LTC2367-16

Versus Sampling Rate

SAMPLING RATE (kHz)

POWER SUPPLY CURRENT (mA)

0.5

1.0

1.5

2.0

2.5

3.0

100 200 300 400

IVDD

IREF

IOVDD

236716 F09

500

DIGITAL INTERFACE

The LTC2367-16 has a serial digital interface. The flexible

OVDD supply allows the LTC2367-16 to communicate with

any digital logic operating between 1.8V and 5V, including

2.5V and 3.3V systems.

The serial output data is clocked out on the SDO pin when

an external clock is applied to the SCK pin if SDO is enabled.

Clocking out the data after the conversion will yield the

best performance. With a shift clock frequency of at least

40MHz, a 500ksps throughput is still achieved. The serial

output data changes state on the rising edge of SCK and

can be captured on the falling edge or next rising edge of

SCK. D15 remains valid till the first rising edge of SCK.

The serial interface on the LTC2367-16 is simple and

straightforward to use. The following sections describe the

operation of the LTC2367-16. Several modes are provided

LTC2367-16

236716fa

TIMING DIAGRAMS

depending on whether a single or multiple ADCs share the

SPI bus or are daisy chained.

Normal Mode, Single Device

When CHAIN = 0, the LTC2367-16 operates in normal

mode. In normal mode, RDL/SDI enables or disables the

serial data output pin SDO. If RDL/SDI is high, SDO is in

high impedance. If RDL/SDI is low, SDO is driven.

Figure 10 shows a single LTC2367-16 operated in nor-

mal mode with CHAIN and RDL/SDI tied to ground. With

RDL/SDI grounded, SDO is enabled and the MSB(D15) of

the new conversion data is available at the falling edge of

BUSY. This is the simplest way to operate the LTC2367-16.

Figure 10. Using a Single LTC2367-16 in Normal Mode

CNV

LTC2367-16

BUSY

CONVERT

IRQ

DATA IN

DIGITAL HOST

CLK

SDO

SCK

RDL/SDI

CHAIN

236718 F10

CONVERT CONVERT

tACQ

tACQ = tCYC – tHOLD

POWER-DOWNPOWER-DOWN

CNV

CHAIN = 0

BUSY

SCK

SDO

RDL/SDI = 0

tBUSYLH

tDSDOBUSYL

tSCK

tHSDO

tSCKH tQUIET

tSCKL

tDSDO

tCONV

tCNVH

tHOLD

ACQUIRE

tCYC

tCNVL

D15 D14 D13 D1 D0

1 2 3 14 15 16

ACQUIRE

LTC2367-16

236716af

TIMING DIAGRAMS

Figure 11. Normal Mode With Multiple Devices Sharing CNV, SCK and SDO

Normal Mode, Multiple Devices

Figure 11 shows multiple LTC2367-16 devices operating

in normal mode (CHAIN = 0) sharing CNV, SCK and SDO.

By sharing CNV, SCK and SDO, the number of required

signals to operate multiple ADCs in parallel is reduced.

Since SDO is shared, the RDL/SDI input of each ADC must

be used to allow only one LTC2367-16 to drive SDO at a

time in order to avoid bus conflicts. As shown in Figure 11,

the RDL/SDI inputs idle high and are individually brought

low to read data out of each device between conversions.

When RDL/SDI is brought low, the MSB of the selected

device is output onto SDO.

RDLB

RDLA

CONVERT

IRQ

DATA IN

DIGITAL HOST

CLK

CNV

LTC2367-16 SDO

SCK

RDL/SDI

CNV

LTC2367-16 SDO

SCK

RDL/SDI

CHAIN BUSY

CHAIN

236716 F11

D15A

SDO

SCK

CNV

BUSY

CHAIN = 0

RDL/SDIB

RDL/SDIA

D15BD14BD1BD0B

D13B

D14AD13AD1AD0A

Hi-Z Hi-ZHi-Z

tEN

tHSDO

tDSDO tDIS

tSCKL

tSCKH

tCNVL

1 2 3 14 15 16 17 18 19 30 31 32

tSCK

CONVERTCONVERT

tQUIET

tCONV

tHOLD

tBUSYLH

POWER-DOWN

ACQUIRE ACQUIRE

POWER-DOWN

LTC2367-16

236716fa

TIMING DIAGRAMS

Chain Mode, Multiple Devices

When CHAIN = OVDD, the LTC2367-16 operates in

chain mode. In chain mode, SDO is always enabled and

RDL/SDI serves as the serial data input pin (SDI) where

daisy-chain data output from another ADC can be input.

This is useful for applications where hardware constraints

may limit the number of lines needed to interface to a large

number of converters. Figure 12 shows an example with

two daisy-chained devices. The MSB of converter A will

appear at SDO of converter B after 16 SCK cycles. The

MSB of converter A is clocked in at the SDI/RDL pin of

converter B on the rising edge of the first SCK.

Figure 12. Chain Mode Timing Diagram

OVDD

CONVERT

IRQ

DATA IN

DIGITAL HOST

CLK

CNV

LTC2367-16

BUSY

SDO

SCK

RDL/SDI

CNV

LTC2367-16

SDO

SCK

RDL/SDI

CHAIN

OVDD

CHAIN

236718 F12

D0A

D1A

D14A

D15A

D13B

D14B

D15B

SDOB

SDOA = RDL/SDIB

RDL/SDIA = 0

D0B

D1B

D13A

D14A

D15AD0A

D1A

1 2 3 14 15 16 17 18 30 31 32

tDSDOBUSYL

tSSDISCK

tHSDISCK

tBUSYLH

tCONV

tHOLD

tHSDO

tDSDO

tSCKL

tSCKH

tSCKCH

tCNVL

tCYC

CONVERT

SCK

CNV

BUSY

CHAIN = OVDD

tQUIET

POWER-DOWN

ACQUIREACQUIRE

LTC2367-16

236716af

BOARD LAYOUT

To obtain the best performance from the LTC2367-16

a printed circuit board is recommended. Layout for the

printed circuit board (PCB) should ensure the digital and

analog signal lines are separated as much as possible.

In particular, care should be taken not to run any digital

clocks or signals alongside analog signals or underneath

the ADC.

Recommended Layout

The following is an example of a recommended PCB layout.

A single solid ground plane is used. Bypass capacitors to

the supplies are placed as close as possible to the supply

pins. Low impedance common returns for these bypass

capacitors are essential to the low noise operation of the

ADC. The analog input traces are screened by ground.

For more details and information refer to DC1813A, the

evaluation kit for the LTC2367-16.

Partial Top Silkscreen

LTC2367-16

236716fa

BOARD LAYOUT

Partial Layer 1 Component Side

Partial Layer 2 Ground Plane

LTC2367-16

236716af

BOARD LAYOUT

Partial Layer 3 PWR Plane

Partial Layer 4 Bottom Layer

LTC2367-16

236716fa

BOARD LAYOUT

Partial Schematic of Demoboard

NC7SZ66P5X

C13

0.1µF

CNV

SCK

C20

47µF

6.3V

0805

C56

0.1µF

CNV

REF

GND

REF

VDD

VREF

0.8VREF

OVDD

SCK

SDO

BUSY

RDL/SDI

SDO

BUSY

LTC2367-16

IN–

IN+

413

B A

GND

VCC

+3.3V

49.9Ω

1206

NC7SZ04P5X

NC7SVU04P5X

U20

LTC6655AHMS8-5

NL17SZ74

NC7SVU04P5X

CNVST_33

FROM CPLD

CLK

TO CPLD

0.1µF

C11

0.1µF

SHDN

GND

OUT_F

GND

9V TO 10V 1

+3.3V +3.3V +3.3V

0.1µF

33Ω

+3.3V

33Ω

R58

ØΩ

0.1µF

33Ω

0.1µF

VIN OUT_S GND VCC

CLR\

PR\

4 2

+3.3V

DC590 DETECT

TO CPLD

+3.3V

C58

OPT

NC7SZ04P5X C15

0.1µF

C16

0.1µF

+3.3V

R13

R17

R10

4.99k

24LC025-I/ST R11

4.99k

R12

4.99k

C14

0.1µF

2367167 BL

SCL

SDA

ARRAY

EEPROM

VSS

VCC

DC590

SDO

SCK

CNV

9V TO

10V

JP6

HD1X3-100

OPT

0.1µF

10µF

6.3V

+2.5V

C10

0.1µF

C39

0.01µF

NPO

C65

OPT

0805 NPO

R38

OPT

R35

OPT

R45

ØΩ

C40

OPT

NPO

10µF

6.3V

R16

0Ω

R32

10Ω

OUT1

V+

V–

V+

–IN1

+IN13

R19

0Ω

R46

ØΩ

R31

OPT

U15

LT6202CS5

R32

0Ω

C42

15pF

C55

1µF V+

V–

C57

0.1µF

OPT

C61

10µF

6.3V

C63

10µF

6.3V

C43

0.1µF

R15

OPT

C18

OPT

C17

10µF

JP2

EXT_CM

+2.5V

VREF/2

EXT

HD1X3-100

1µF

C46

1µF

R40

OPT

R39

0Ω

COUPLING

AC DC

JP1

HD1X3-100

C44

1µF

C49

OPT

C48

10µF

6.3V

C47

OPT

R41

OPT

C59

1µF

C60

0.1µF

JP5

HD1X3-100

COUPLING

AC DC

DB16

DB17

DB0

DB1

DB2

DB3

DB4

DB5

DB6

DB7

DB8

DB9

DB10

DB11

DB12

DB13

DB14

DB15

CLKOUT

CON-EDGE 40-100

CLKIN

R14

0Ω

AIN+

AIN–

–

LTC2367-16

236716af

MSOP (MS16) 1107 REV Ø

0.53 ± 0.152

(.021 ± .006)

SEATING

PLANE

0.18

(.007)

1.10

(.043)

MAX

0.17 –0.27

(.007 – .011)

TYP

0.86

(.034)

REF

0.50

(.0197)

BSC

16151413121110

12345678

NOTE:

1. DIMENSIONS IN MILLIMETER/(INCH)

2. DRAWING NOT TO SCALE

3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.

MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE

4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.

INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE

5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX

0.254

(.010) 0° – 6° TYP

DETAIL “A”

GAUGE PLANE

5.23

(.206)

MIN

3.20 – 3.45

(.126 – .136)

0.889 ± 0.127

(.035 ± .005)

RECOMMENDED SOLDER PAD LAYOUT

0.305 ± 0.038

(.0120 ± .0015)

TYP

0.50

(.0197)

BSC

4.039 ± 0.102

(.159 ± .004)

(NOTE 3)

0.1016 ± 0.0508

(.004 ± .002)

3.00 ± 0.102

(.118 ± .004)

(NOTE 4)

0.280 ± 0.076

(.011 ± .003)

REF

4.90 ± 0.152

(.193 ± .006)

MS Package

16-Lead Plastic MSOP

(Reference LTC DWG # 05-08-1669 Rev Ø)

3.00 ±0.10

(2 SIDES)

4.00 ±0.10

(2 SIDES)

NOTE:

1. DRAWING PROPOSED TO BE MADE VARIATION OF VERSION (WGED-3) IN JEDEC

PACKAGE OUTLINE MO-229

2. DRAWING NOT TO SCALE

3. ALL DIMENSIONS ARE IN MILLIMETERS

4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE

MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE

5. EXPOSED PAD SHALL BE SOLDER PLATED

6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE

TOP AND BOTTOM OF PACKAGE

0.40 ±0.10

BOTTOM VIEW—EXPOSED PAD

1.70 ±0.10

0.75 ±0.05

R = 0.115

TYP

R = 0.05

TYP

3.15 REF

169

PIN 1

TOP MARK

(SEE NOTE 6)

0.200 REF

0.00 – 0.05

(DE16) DFN 0806 REV Ø

PIN 1 NOTCH

R = 0.20 OR

0.35 × 45°

CHAMFER

3.30 ±0.10

1.70 ±0.05

3.15 REF

RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS

APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED

2.20 ±0.05

0.70 ±0.05

3.60 ±0.05 PACKAGE

OUTLINE

0.25 ±0.05

3.30 ±0.05

0.45 BSC

0.23 ±0.05

0.45 BSC

DE Package

16-Lead Plastic DFN (4mm × 3mm)

(Reference LTC DWG # 05-08-1732 Rev Ø)

PACKAGE DESCRIPTION

Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.

LTC2367-16

236716fa

Information furnished by Linear Technology Corporation is believed to be accurate and reliable.

However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-

tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.

REVISION HISTORY

REV DATE DESCRIPTION PAGE NUMBER

A 08/12 Corrected resolution from 18-bit to 16-bit in Description section 1

LTC2367-16

236716af

Linear Technology Corporation

1630 McCarthy Blvd., Milpitas, CA 95035-7417

(408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com

 LINEAR TECHNOLOGY CORPORATION 2012

LT 0812 REV A • PRINTED IN USA

LTC2367-16

IN+REF VDD

2.5V

IN–

10nF

47µF

10Ω

402Ω

499Ω

RIN

10µF

200pF

LT6202

V+

V–

–3V

236716 TA02

VOUT_S

VOUT_F

VIN LTC6655-5

4–

220pF

10V

–10V

PART NUMBER DESCRIPTION COMMENTS

ADCs

LTC2379-18/LTC2378-18

LTC2377-18/LTC2376-18

18-Bit, 1.6Msps/1Msps/500ksps/250ksps Serial, Low

Power ADC

2.5V Supply, Differential Input, 101.2dB SNR, ±5V Input Range,

DGC, Pin-Compatible Family in MSOP-16 and 4mm × 3mm DFN-16

Packages

LTC2380-16/LTC2378-16

LTC2377-16/LTC2376-16

16-Bit, 2Msps/1Msps/500ksps/250ksps Serial, Low

Power ADC

2.5V Supply, Differential Input, 96.2dB SNR, ±5V Input Range, DGC,

Pin-Compatible Family in MSOP-16 and 4mm × 3mm DFN-16

Packages

LTC2383-16/LTC2382-

16/LTC2381-16

16-Bit, 1Msps/500ksps/250ksps Serial, Low

Power ADC

2.5V Supply, Differential Input, 92dB SNR, ±2.5V Input Range, Pin-

Compatible Family in MSOP-16 and 4mm × 3mm DFN-16 Packages

LTC2393-16/LTC2392-

16/LTC2391-16

16-Bit, 1Msps/500ksps/250ksps Parallel/Serial ADC 5V Supply, Differential Input, 94dB SNR, ±4.096V Input Range, Pin-

Compatible Family in 7mm × 7mm LQFP-48 and QFN-48 Packages

LTC2302/LTC2306 12-Bit, 500ksps, 1-/2-Channel, Low Noise, ADC 5V Supply, 14mW at 500ksps, DFN-10 Package

LTC2362 12-Bit, 500ksps, Serial ADC 2.35V to 3.6V, 3.3mW, 6- and 8-Lead TSOT-23 Packages

DACS

LTC2757 18-Bit, Single Parallel IOUT SoftSpan™ DAC ±1LSB INL/DNL, Software-Selectable Ranges, 7mm × 7mm

LQFP-48 Package

LTC2641 16-Bit/14-Bit/12-Bit Single Serial VOUT DACs ±1LSB INL/DNL, MSOP-8, 3mm × 3mm DFN, SO-8 Packages, 0V to 5V

Output

LTC2630 12-Bit/10-Bit/8-Bit Single VOUT DACs SC70 6-Pin Package, Internal Reference, ±1LSB INL (12 Bits)

References

LTC6655 Precision Low Drift Low Noise Buffered Reference 5V/2.5V, 2ppm/°C, 0.25ppm Peak-to-Peak Noise, MSOP-8 Package

LTC6652 Precision Low Drift Low Noise Buffered Reference 5V/2.5V, 5ppm/°C, 2.1ppm Peak-to-Peak Noise, MSOP-8 Package

Amplifiers

LT6202/LT6203 Single/Dual 100MHz Rail-to-Rail Input/Output Noise

Low Power Amplifiers

1.9nV√Hz, 3mA Maximum, 100MHz Gain Bandwidth

LT6200/LT6200-5/

LT6200-10

165MHz/800MHz/1.6GHz Op Amp with

Unity Gain/AV = 5/AV = 10

Low Noise Voltage: 0.95nV/√Hz (100kHz), Low Distortion: –80dB at

1MHz, TSOT23-6, SO-8 Packages

RELATED PARTS

TYPICAL APPLICATION

LT6202 Converting a ±10V Bipolar Signal to a 0V to 5V Input Signal Into the LTC2367-16