FUNCTIONAL BLOCK DIAGRAM
PIN CONNECTIONS
14-Pin Epoxy DIP
(P-Suffix)
16-Pin SOL
(S-Suffix)
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
a
Dual Audio
Analog Switches
SSM2402/SSM2412
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700 Fax: 617/326-8703
FEATURES
“Clickless” Bilateral Audio Switching
Guaranteed “Break-Before-Make” Switching
Low Distortion: 0.003% typ
Low Noise: 1 nV/√Hz
Superb OFF-Isolation: 120 dB typ
Low ON-Resistance: 60 V typ
Wide Signal Range: VS = 618 V; 10 V rms
Wide Power Supply Range: 620 V max
Available in Dice Form
GENERAL DESCRIPTION
The SSM2402/SSM2412 are dual analog switches designed spe-
cifically for high performance audio applications. Distortion and
noise are negligible over the full audio operating range of 20 Hz to
20 kHz at signal levels of up to 10 V rms. The SSM2402/
SSM2412 offer a monolithic integrated alternative to expensive
and noisy relays or complex discrete JFET circuits. Unlike conven-
tional general-purpose CMOS switches, the SSM2402/SSM2412
provide superb fidelity without audio “clicks” during switching.
Conventional TTL or CMOS logic can be used to control the
switch state. No external pull-up resistors are needed. A “T”
configuration provides superb OFF-isolation and true bilateral
operation. The analog inputs and outputs are protected against
overload and overvoltage.
An important feature is the guaranteed “break-before-make”
for all units, even IC-to-IC. In large systems with multiple
switching channels, all separate switching units must open be-
fore any switch goes into the ON-state. With the SSM2402/
SSM2412, you can be certain that multiple circuits will all
break-before-make.
The SSM2402/SSM2412 represent a significant step forward in
audio switching technology. Distortion and switching noise are
significantly reduced in the new SSM2402/SSM2412 bipolar-
JFET switches relative to CMOS switching technology. Based
on a new circuit topology that optimizes audio performance,
the SSM2402/SSM2412 make use of a proprietary bipolar-
JFET process with thin-film resistor network capability. Nitride
capacitors, which are very area efficient, are used for the propri-
etary ramp generator that controls the switch resistance transi-
tion. Very wide bandwidth amplifiers control the gate-to-source
voltage over the full audio operating range for each switch. The
ON-resistance remains constant with changes in signal amplitude
and frequency, thus distortion is very low, less than 0.01% max.
The SSM2402 is the first analog switch truly optimized for
high-performance audio applications. For broadcasting and
other switching applications which require a faster switching
time, we recommend the SSM2412—a dual analog switch with
one-third of the switching time of the SSM2402.
REV. A
–2–
SSM2402/SSM2412–SPECIFICATIONS
ELECTRICAL CHARACTERISTICS
SSM2402/SSM2412
Parameter Symbol Conditions Min Typ Max Units
POSITIVE SUPPLY CURRENT +I
SY
V
IL
= 0.8 V, 2.0 V
1
6.0 7.5 mA
NEGATIVE SUPPLY CURRENT –I
SY
V
IL
= 0.8 V, 2.0 V
1
4.8 6.0 mA
GROUND CURRENT I
GND
V
IL
= 0.8 V, 2.0 V
1
0.6 1.5 mA
DIGITAL INPUT HIGH V
INH
T
A
= Full Temperature Range 20 V
DIGITAL INPUT LOW V
INL
T
A
= Full Temperature Range 0.8 V
LOGIC INPUT CURRENT I
LOGIC
V
IN
= 0 V to 15 V
2
1.0 5.0 µA
ANALOG VOLTAGE RANGE
3
V
ANALOG
–14.2 +14.2 V
ANALOG CURRENT RANGE
3
I
ANALOG
–10 +10 mA
OVERVOLTAGE INPUT CURRENT V
IN
= ±V
SUPPLY
±40 mA
SWITCH ON RESISTANCE R
ON
–14.2 V ≤ V
A
≤ +14.2 V
I
A
= ±10 mA, V
IL
= 2.0 V
T
A
= +25°C6085Ω
T
A
= Full Temperature Range 115 Ω
Tempco (∆R
ON
/∆T) 0.2 Ω/°C
R
ON
MATCH R
ON
MATCH –14.2 V ≤ V
A
≤ +14.2 V 1 5 %
I
A
= ±10 mA, V
IL
= 2.0 V
SWITCH ON LEAKAGE CURRENT I
S(ON)
V
IL
= 2.0 V
–14.2 V ≤ V
A
≤ +14.2 V 0.05 1.0 µA
V
A
= 0 V 0.05 10.0 nA
SWITCH OFF LEAKAGE CURRENT I
S(OFF)
V
IL
= 0.8 V
–14.2 V ≤ V
A
≤ +14.2 V 0.05 1.0 µA
V
A
= 0 V 0.05 10.0 nA
TURN-ON TIME
4
t
ON
V
A
= +10 V, R
L
= 2 kΩSSM2402 10.0 ms
T
A
= +25°C, See Test Circuit SSM2412 3.5
TURN-OFF TIME
5
t
OFF
V
A
= +10 V, R
L
= 2 kΩSSM2402 4.0 ms
T
A
= +25°C, See Test Circuit SSM2412 1.5
BREAK-BEFORE-MAKE t
OFF
–t
ON
T
A
= +25°C SSM2402 6.0 ms
TIME DELAY
6
SSM2412 2.0
CHARGE INJECTION Q T
A
= +25°C SSM2402 50 pC
SSM2412 150
ON-STATE INPUT CS
(ON)
V
A
= 1 V rms 12 pF
CAPACITANCE f = 5 kHz, T
A
= +25°C
OFF-STATE INPUT CS
(OFF)
V
A
= 1 V rms 4 pF
CAPACITANCE f = 5 kHz, T
A
= +25°C
OFF ISOLATION I
SO(OFF)
V
A
= 10 V rms, 20 Hz to 20 kHz 120 dB
T
A
= +25°C, See Test Circuit
CHANNEL-TO-CHANNEL C
T
V
A
= 10 V rms, 20 Hz to 20 kHz 96 dB
CROSSTALK T
A
= +25°C
TOTAL HARMONIC THD 0 V to 10 V rms, 20 Hz to 20 kHz 0.003 0.01 %
DISTORTION
7
T
A
= +25°C, R
L
= 5 kΩ
SPECTRAL NOISE DENSITY e
n
20 Hz to 20 kHz, T
A
= +25°C 1 nV/√Hz
WIDEBAND NOISE DENSITY e
n
p-p 20 Hz to 20 kHz, T
A
= +25°C 0.2 µV p-p
NOTES
1
“V
IL
” is the Logic Control Input.
2
Current tested at V
IN
= 0 V. This is the worst case condition.
3
Guaranteed by R
ON
test condition.
4
Turn-ON time is measured from the time the logic input reaches the 50% point to the time the output reaches 50% of the final value.
5
Turn-OFF time is measured from the time the logic input reaches the 50% point to the time the output reaches 50% of the initial value.
6
Switch is guaranteed by design to provide break-before-make operation.
7
THD guaranteed by design and dynamic R
ON
testing.
Specifications subject to change without notice.
(@ VS = 618 V, RL = OPEN, and –408C ≤ TA ≤ +858C unless otherwise noted.
All specifications, tables, graphs, and application data apply to both the SSM2402 and SSM2412, unless otherwise noted.)
SSM2402/SSM2412
REV. A –3–
ABSOLUTE MAXIMUM RATINGS
Operating Temperature Range . . . . . . . . . . . –40°C to +85°C
Operating Supply Voltage Range . . . . . . . . . . . . . . . . . ±20 V
Analog Input Voltage Range
Continuous . . . . . . . . . . . . . . V– +3.5 V ≤ V
A
≤ V+ –3.5 V
Maximum Current Through Switch . . . . . . . . . . . . . . 20 mA
Logic Input Voltage Range . . . . . . . . . . . . V+ Supply to –2 V
V+ Supply to Ground . . . . . . . . . . . . . . . . . . . . . . . . . . +36 V
V– Supply to Ground . . . . . . . . . . . . . . . . . . . . . . . . . . . –20 V
V
A
to V– Supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +36 V
Package Type u
JA
*u
JC
Units
14-Pin Plastic DIP (P) 76 33 °C/W
16-Pin SOL (S) 92 27 °C/W
*θ
JA
is specified for worst case mounting conditions, i.e., θ
JA
is specified for device
in socket for P-DIP package; θ
JA
is specified for device soldered to printed circuit
board for SOL package.
Timing Diagram
ORDERING GUIDE
Temperature Package
Model Range Description
SSM2402P –40°C to +85°C 14-Pin Plastic DIP
SSM2402S –40°C to +85°C 16-Pin SOL
SSM2412P –40°C to +85°C 14-Pin Plastic DIP
SSM2412S –40°C to +85°C 16-Pin SOL
DICE CHARACTERISTICS
Die Size 0.105 × 0.097 Inch, 10,185 sq. mils
(2.667 × 2.464 mm, 6.57 sq. mm)
WAFER TEST LIMITS
Parameter Symbol Conditions
1
Limit Units
POSITIVE SUPPLY CURRENT +I
SY
V
IL
= 0.8 V 7.5 mA max
NEGATIVE SUPPLY CURRENT –I
SY
V
IL
= 0.8 V 6.0 mA max
GROUND CURRENT I
GND
V
IL
= 0.8 V 1.5 mA max
LOGIC INPUT CURRENT I
LOGIC
V
IN
= 0 V
2
5.0 µA max
SWITCH ON RESISTANCE R
ON
–14.2 V ≤ V
A
≤ +14.2 V 85 Ω max
I
A
= ±10 mA, V
IL
= 2.0 V
R
ON
MATCH BETWEEN SWITCHES R
ON
MATCH –14.2 V ≤ V
A
≤ +14.2 V 5 % max
I
A
= ±10 mA, V
IL
= 2.0 V
SWITCH ON LEAKAGE CURRENT I
S(ON)
–14.2 V ≤ V
A
≤ +14.2 V, V
IL
= 2.0 V 1.0 µA max
SWITCH OFF LEAKAGE CURRENT I
S(OFF)
–14.2 V ≤ V
A
≤ +14.2 V, V
IL
= 0.8 V 1.0 µA max
NOTES
1
V
IL
= Logic Control Input; V
A
= Applied Analog Input Voltage; I
A
= Applied Analog Input Current.
2
Worst Case Condition.
Electrical tests are performed at wafer probe to the limits shown. Due to variations in assembly methods and normal yield loss, yield after packaging is not
guaranteed for standard product dice. Consult factory to negotiate specifications based on dice lot qualifications through sample lot assembly and testing.
“ON” Resistance vs. Analog Voltage
Channel Separation vs. Frequency
Leakage Current vs. Analog Voltage
Total Harmonic Distortion vs.
Frequency
SSM2402 Switching Time
vs. Temperature
Supply Current vs. Temperature
“OFF” Isolation vs. Frequency
SSM2412 Switching Time
vs. Temperature
Overvoltage Characteristics
SSM2402/SSM2412–Typical Performance Characteristics
REV. A–4–
SSM2402/SSM2412
REV. A –5–
SSM2402 T
ON
/T
OFF
Switching Response
SSM 2412 T
ON
/T
OFF
Switching Response
Switching ON/OFF Transition
T
ON
/T
OFF
Switching Response Test Circuit
Switch ON/OFF Transition Test Circuit
“OFF” Isolation Test Circuit
SSM2402/SSM2412
REV. A
–6–
Switching Time Test Circuit
Simplified Schematic
SSM2402/SSM2412
REV. A –7–
APPLICATIONS INFORMATION
FUNCTIONAL SECTIONS
Each half of the SSM2402/SSM2412 are made up of three major
functional blocks:
1. “T” Switch
Consists of JFET switches S
1
and S
2
in series as the main
switches and switch S
3
as a shunt.
2. Ramp Generator
Generates a ramp voltage on command of the Control Input
(see Figure 1). A LOW-to-HIGH TTL input at Control
Input initiates a ramp that goes from approximately –7 V to
+7 V in 12 ms. Conversely, a HIGH-to-LOW TTL transi-
tion at Control Input will cause a downward ramp from ap-
proximately +7 V to –7 V in 12 ms for the SSM2402, and
4 ms for the SSM2412. The Ramp Generator also supplies
the +3 V and –3 V reference levels for Switch Control.
3. Switch Control
The ramp from the Ramp Generator section is applied to two
differential amplifiers (DA
1
and DA
2
) in the Switch Control
block. (See Simplified Schematic). One amplifier is refer-
enced to –3 V and the other is referenced to +3 V. Switch
Control Outputs are:
—Main Switch Control—Drives two 0.25 mA current
sources that control the inverting inputs of each op amp.
When ON, the current sources cause a gate-to-source volt-
age of approximately 2.5 V which is sufficient to turn off
S
1
and S
2
. When the current sources from Main Switch
Control are OFF, each op amp acts as a unity-gain fol-
lower (V
GS
= 0) and both switches (S
1
and S
2
) will be ON.
—Shunt Switch Control—Controls the Shunt Switch of
the “T” configuration.
SWITCH OPERATION
Unlike conventional analog switches, the SSM2402/SSM2412
are designed to ramp on and off gradually over several millisec-
onds. The soft transition prevents popping or clicking in audio
systems. Transients are minimized in active filters when the
SSM2402/SSM2412 are used to switch component values.
To see how the SSM2402/SSM2412 switches work, first con-
sider an OFF-to-ON transition. The Control Input is initially
LOW and the Ramp Output is at approximately –7 V. The
Main Switch Control is HIGH which drives current sources Q
3
and Q
4
to 0.25 mA each. These currents generate 2.5 V gate-
to-source back bias for each JFET switch (S
1
and S
2
) which
holds them OFF.
The Shunt Switch Control is negative which holds the shunt
JFET S
3
ON. Undesired feedthrough signals in the series JFET
switches S
1
and S
2
are shunted to the negative supply rail
through S
3
.
Figure 1. Ramp Generator
Figure 2. Switch Control
When the Control Input goes from LOW to HIGH, the Ramp
Generator slews in the positive direction as shown in Figure 2.
When the ramp goes more positive than –3 V, the Shunt Switch
Control is pulled positive by differential amplifier DA
2
which
thereby puts shunt switch S
3
into the OFF state. Note that S
1
and S
2
are still OFF, so at this time all three switches in the
“T” are OFF.
SSM2402/SSM2412
REV. A
–8–
When the Ramp Output reaches +3 V, and the drive for the
Main Switch Control output is gated OFF by differential ampli-
fier DA
1
, current sources Q
3
and Q
4
go to the OFF state and the
V
GS
of each main switch goes to zero. The high speed op amp
followers provide essentially zero gate-to-source voltage over the
full audio signal range; this in turn assures a constant low im-
pedance in the ON state over the full audio signal range. Total
time to turn on the SSM2402 switch is approximately 10.0 ms
and 3.5 ms for the SSM2412.
In systems using a large number of separate switches, there are
advantages to having faster switching into OFF state than into
the ON state. Break-before-make can be maintained at the sys-
tem level. To see how the SSM2402/SSM2412 guarantee
break-before-make, consider the ON-to-OFF transition.
A Control Input LOW initiates the ON-to-OFF transition. The
Ramp Generator integrates down from approximately +7 V to-
wards –7 V. As the ramp goes through +3 V, the comparator
controlling the Main Switches (S
1
and S
2
) goes HIGH and turns
on current sources Q
3
and Q
4
which thereby puts S
1
and S
2
into
the OFF state. At this time, all switches in the “T” are OFF.
When the ramp integrates down to –3 V, the Shunt Switch Con-
trol changes state and pulls shunt switch S
3
into the ON state.
This completes the ON-to-OFF transition; S
1
and S
2
are OFF,
and S
3
is ON to shunt away any undesired feedthrough. Note
though that the ON-to-OFF time for main switches S
1
and S
2
is
only the time interval required for the ramp to go from +7 V to
+3 V, about 4 ms for the SSM2402, and 1.5 ms for the
SSM2412. The time to turn on is about 2.5 times as long as the
time to turn off.
Typical Configuration
The SSM2402/SSM2412 are much more than simple single
solid state switches. The “T” configuration provides superb
OFF-isolation through shunting of feedthrough via shunt switch
S
3
. Break-before-make is inherent in the design. The ramp pro-
vides a controlled gating action that softens the ON/OFF transi-
tions. Distortion is minimized by holding zero gate-to-source
voltage for the two main FET switches, S
1
and S
2
, using the two
op amp followers. Figure 3 shows a distortion comparison be-
tween the SSM2402 and a typical CMOS switch. In summary,
the SSM2402/SSM2412 are designed specifically for high per-
formance audio system usage.
OVERVOLTAGE PROTECTION
The SSM2402/SSM2412 are designed to guarantee correct op-
eration with inputs of up to ±14.2 V with ±18 V supplies. The
switch input should never be forced to go beyond the supply
rails. In the OFF condition, if the inputs exceeds +14.2 V,
there is a risk of turning the respective input pass FET “ON.”
When the input voltage rises to within 3.8 V of the positive
supply, the op amp follower saturates and will not be able to
maintain the full 2.5 V of back bias on the gate-to-source
junction. Under this condition, current will flow from the input
through the shunt FET to the negative supply. This current is
substantial, but is limited by the FET I
DSS
. Although this cur-
rent will not damage the device, there is a danger of also turn-
ing on the output pass FET, especially if the output is close to
the negative rail.
This risk of signal “breakthrough” for inputs above +14.2 V can
be e liminated by using a source resistor of 100 Ω–500 Ω in series
with the analog input to provide additional current limiting.
Near the negative supply, transistors Q
3
and Q
4
saturate and
can no longer keep the switch OFF. Signal breakthrough can-
not happen, but the danger here is latch-up via a path to V–
through the shunt FET. Additional circuitry (not shown) has
been incorporated to turn OFF the shunt FET under these
conditions, and the potential for latch-up is thereby eliminated.
Figure 3. Comparison of the SSM2402 and
Typical CMOS Switch for Distortion
SSM2402/SSM2412
REV. A –9–
DIGITALLY-CONTROLLED ATTENUATOR
Figure 4 shows the usual approach to digitally-controlled at-
tenuation. With S
1
closed, the signal passes unattenuated to the
output. With S
1
open and S
2
closed, the signal is attenuated by
R
1
and R
2
. The advantage of this configuration is that the at-
tenuator current does not have to flow through the switches.
The disadvantage is that the output is undefined during the
switching period, which can be several milliseconds.
The low distortion characteristics of the SSM2402/SSM2412
enable the alternate arrangement of Figure 5 to be used. Now
only one switch is required to change between two gains, and
there is always a signal path to the output. Values for R
2
will
typically be in the low kilohm range.
For more gain steps and higher attenuation, the ladder arrange-
ment of Figure 6 can be used. This enables a wide dynamic
range to be achieved without the need for large value resistors,
which would result in degradation of the noise performance.
Figure 4.
Figure 5.
Figure 6.
HIGH PERFORMANCE STEREO ROUTING SWITCHER
The SSM2402 Dual Audio Switch comprises the nucleus for
this 16 channels-to-one high performance stereo audio routing
switcher, which features negligible noise and low distortion over
the frequency range of 20 Hz to 20 kHz. This performance is
achieved even while driving 600 Ω loads at signal levels up to
+30 dBu.
The SSM2402 affords a much simplified electrical design and
printed circuit board layout, along with reduced manufacturing
cost, when compared with discrete JFET circuits of similar per-
formance. The electrical performance of the design described is
vastly superior to CMOS switch designs, which are more prone
to failure resulting from electrical static discharge.
The switching control of the SSM2402 may be activated by
conventional mechanical switches or 5 volt TTL or CMOS logic
circuits. The application shown utilizes a simple mechanical
control switch for illustration purposes only. Many diverse X/Y
control schemes, destination control, or computer controlled
designs can be utilized.
The “T” configuration of the SSM2402 switch provides excel-
lent ON-OFF isolation. The SSM2402 also features ms ramped
turn on and ms ramped turn off for click-free switching. Addi-
tionally, the switch has a break-before-make switching sequence.
Both features become significant in large audio switching sys-
tems where the audio path can pass through multiple switching
elements. Such controlled switching is very important in large
systems used in broadcast program switching or in production
work.
The application circuit design also employs the SSM2015 bal-
anced input amplifier (Figure 7). The input impedance is high
(≈100 kΩ), balanced or unbalanced. The input circuit incorpo-
rates a single pole RFI filter with a cutoff frequency set at
145 kHz. In addition, the input circuit attenuates the signal by
25 dB and extends the common-mode input voltage range to
±98 volts peak, with common-mode rejection greater than
70 dB from 20 Hz to 20 kHz. The SSM2015 is set to produce a
15 dB gain. The signal drive level into the SSM2402 switch is
then +10 dBu with a +20 dBu input level and +14 dBu peak,
well within ideal operating range. Good signal-to-noise is main-
tained, with generous head-room available by electing to use
±18 V dc power supply voltages.
SSM2402/SSM2412
REV. A
–10–
Figure 7. Switcher Schematic
SSM2402/SSM2412
REV. A –11–
Figure 8. Switcher Functional Block Diagram
Overall performance of the 16 × 1 stereo switcher is noteworthy.
Input-to-output frequency response is flat to within 1 dB over a
10 Hz to 50 kHz band. Total harmonic distortion plus noise is
less than 0.03%, from 20 Hz to 20 kHz. SMPTE intermodula-
tion distortion is less than 0.02%. The use of ±18 V dc power
supplies produces a +30 dBm clip level, even when driving
600 Ω loads.
Table I. Circuit Performance Specifications
Max Input Level +30 dBu
Input Impedance, Unbalanced 100 kΩ
Input Impedance, Balanced 200 kΩ
Common-Mode Rejection (20 Hz to 20 kHz) >70 dB
Common-Mode Voltage Limit ±98 V Peak
Max Output Level +30 dBu/dBm
Output Impedance 67 Ω
Gain Control Range ±2 dB
Output Voltage Slew Rate 6 V/µs
Frequency Response (±0.05 dB) 20 Hz to 20 kHz
Frequency Response (±0.5 dB) 10 Hz to 50 kHz
THD + Noise (20 Hz to 20 kHz, +8 dBu) 0.005%
THD + Noise (20 Hz to 20 kHz, +24 dBu) 0.03%
IMD (SMPTE 60 Hz & 4 kHz, 4:1, +24 dBu) 0.02%
Crosstalk (20 Hz to 20 kHz) >80 dB
S/N Ratio @ 0 dB Gain 135 dB
The routing switcher bus carries high level unbalanced audio,
but is driven with low impedance sources. With the output im-
pedance of the SSM2015 at virtually 0 Ω and the SSM2402
switch ON, resistance is typically 60 Ω. Bus-to-bus crosstalk is
exceptionally low. For example, assuming 14 pF coupling be-
tween buses and 20 kHz signal, the crosstalk (isolation) exceeds
80 dB. The 14 pF would be representative for the 16 × 1 stereo
design shown. Shielding of the buses with a printed circuit
board ground plane and physically isolating the input and out-
put circuits will reduce the crosstalk even further. The “T” con-
figuration of the SSM2402 switch virtually eliminates crosstalk
between the various input signal sources.
The output amplifier incorporates a buffer amplifier that pro-
vides 4 dB of gain (nominally), with adjustable output level trim
control. The buffer also isolates the switching bus from the bal-
anced output amplifier circuit. The balanced output is designed
to drive 600 Ω loads and utilizes two SSM2134 IC amplifiers.
The differential design increases drive capability, yet increases
the heat dissipation surface area, and keeps IC package tem-
perature well within safe operating limits, even when driving
600 Ω loads. The SSM2134 is recommended due to its low
noise, wide frequency response, and output drive current
capabilities.
SSM2402/SSM2412
REV. A
–12–
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
14-Pin Epoxy DIP
(P-Suffix)
14
17
8
0.795 (20.19)
0.725 (18.42)
0.280 (7.11)
0.240 (6.10)
PIN 1
0.325 (8.25)
0.300 (7.62)
0.015 (0.381)
0.008 (0.204)
0.195 (4.95)
0.115 (2.93)
SEATING
PLANE
0.022 (0.558)
0.014 (0.356)
0.060 (1.52)
0.015 (0.38)
0.210 (5.33)
MAX 0.130
(3.30)
MIN
0.070 (1.77)
0.045 (1.15)
0.100
(2.54)
BSC
0.160 (4.06)
0.115 (2.93)
16-Pin SOL
(S-Suffix)
16 9
81
0.4133 (10.50)
0.3977 (10.00)
0.4193 (10.65)
0.3937 (10.00)
0.2992 (7.60)
0.2914 (7.40)
PIN 1
SEATING
PLANE
0.0118 (0.30)
0.0040 (0.10)
0.0192 (0.49)
0.0138 (0.35)
0.1043 (2.65)
0.0926 (2.35)
0.0500
(1.27)
BSC 0.0125 (0.32)
0.0091 (0.23)
0.0500 (1.27)
0.0157 (0.40)
8°
0°
0.0291 (0.74)
0.0098 (0.25) x 45°
PRINTED IN U.S.A.
