LT1028/LT1128 Ultralow Noise Precision High Speed Op Amps U FEATURES DESCRIPTIO The LT(R)1028(gain of -1 stable)/LT1128(gain of +1 stable) achieve a new standard of excellence in noise performance with 0.85nV/Hz 1kHz noise, 1.0nV/Hz 10Hz noise. This ultralow noise is combined with excellent high speed specifications (gain-bandwidth product is 75MHz for LT1028, 20MHz for LT1128), distortion-free output, and true precision parameters (0.1V/C drift, 10V offset voltage, 30 million voltage gain). Although the LT1028/ LT1128 input stage operates at nearly 1mA of collector current to achieve low voltage noise, input bias current is only 25nA. Voltage Noise 1.1nV/Hz Max at 1kHz 0.85nV/Hz Typ at 1kHz 1.0nV/Hz Typ at 10Hz 35nVP-P Typ, 0.1Hz to 10Hz Voltage and Current Noise 100% Tested Gain-Bandwidth Product LT1028: 50MHz Min LT1128: 13MHz Min Slew Rate LT1028: 11V/s Min LT1128: 5V/s Min Offset Voltage: 40V Max Drift with Temperature: 0.8V/C Max Voltage Gain: 7 Million Min Available in 8-Pin SO Package The LT1028/LT1128's voltage noise is less than the noise of a 50 resistor. Therefore, even in very low source impedance transducer or audio amplifier applications, the LT1028/LT1128's contribution to total system noise will be negligible. U APPLICATIO S Low Noise Frequency Synthesizers High Quality Audio Infrared Detectors Accelerometer and Gyro Amplifiers 350 Bridge Signal Conditioning Magnetic Search Coil Amplifiers Hydrophone Amplfiers U , LTC and LT are registered trademarks of Linear Technology Corporation TYPICAL APPLICATIO Voltage Noise vs Frequency Flux Gate Amplifier DEMODULATOR SYNC + OUTPUT TO DEMODULATOR LT1028 SQUARE WAVE DRIVE 1kHz FLUX GATE TYPICAL SCHONSTEDT #203132 - 1k VOLTAGE NOISE DENSITY (nV/Hz) 10 MAXIMUM 1/f CORNER = 14Hz TYPICAL 1 1/f CORNER = 3.5Hz 0.1 0.1 50 1028/1128 TA01 VS = 15V TA = 25C 1 10 100 FREQUENCY (Hz) 1k 1028/1128 TA02 1 LT1028/LT1128 W W W AXI U U ABSOLUTE RATI GS (Note 1) Supply Voltage -55C to 105C ................................................ 22V 105C to 125C ................................................ 16V Differential Input Current (Note 9) ...................... 25mA Input Voltage ............................ Equal to Supply Voltage Output Short Circuit Duration .......................... Indefinite Operating Temperature Range LT1028/LT1128AM, M (OBSOLETE) . - 55C to 125C LT1028/LT1128AC, C (Note 11) ......... - 40C to 85C Storage Temperature Range All Devices ........................................ - 65C to 150C Lead Temperature (Soldering, 10 sec.)................. 300C U W U PACKAGE/ORDER I FOR ATIO TOP VIEW ORDER PART NUMBER VOS TRIM 8 VOS TRIM 1 7 V+ - -IN 2 + +IN 3 4 V- (CASE) 6 OUT 5 OVERCOMP LT1028AMH LT1028MH LT1028ACH LT1028CH ORDER PART NUMBER TOP VIEW VOS TRIM 1 -IN 2 - 7 +IN 3 + 6 8 V- 4 5 VOS TRIM V+ OUT OVERCOMP S8 PACKAGE 8-LEAD PLASTIC SOIC TJMAX = 135C, JA = 140C/W H PACKAGE 8-LEAD TO-5 METAL CAN TJMAX = 175C, JA = 140C/W, JC = 40C/W LT1028CS8 LT1128CS8 S8 PART MARKING 1028 1128 OBSOLETE PACKAGE Consider S8 or N8 Packages for Alternate Source TOP VIEW VOS TRIM 1 -IN 2 - V 8 OS TRIM 7 V+ +IN 3 + 6 V- 4 OUT 5 OVERCOMP N8 PACKAGE 8-LEAD PLASTIC DIP TJMAX = 130C, JA = 130C/W J8 PACKAGE 8-LEAD CERAMIC DIP TJMAX = 165C, JA = 100C/W LT1028ACN8 LT1028CN8 LT1128ACN8 LT1128CN8 LT1028AMJ8 LT1028MJ8 LT1028ACJ8 LT1028CJ8 LT1128AMJ8 LT1128MJ8 LT1128CJ8 OBSOLETE PACKAGE Consider N8 Package for Alternate Source Consult LTC Marketing for parts specified with wider operating temperature ranges. 2 ORDER PART NUMBER ORDER PART NUMBER TOP VIEW NC 1 16 NC NC 2 15 NC 14 TRIM TRIM 3 -IN 4 - 13 V + +IN 5 + NC 7 12 OUT 11 OVERCOMP 10 NC NC 8 9 V- 6 NC SW PACKAGE 16-LEAD PLASTIC SOL TJMAX = 140C, JA = 130C/W NOTE: THIS DEVICE IS NOT RECOMMENDED FOR NEW DESIGNS LT1028CSW LT1028/LT1128 ELECTRICAL CHARACTERISTICS VS = 15V, TA = 25C, unless otherwise noted. LT1028AM/AC LT1128AM/AC SYMBOL VOS VOS Time IOS IB en PARAMETER Input Offset Voltage Long Term Input Offset Voltage Stability Input Offset Current Input Bias Current Input Noise Voltage CONDITIONS (Note 2) (Note 3) Input Noise Voltage Density In Input Noise Current Density CMRR PSRR AVOL Input Resistance Common Mode Differential Mode Input Capacitance Input Voltage Range Common Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain VOUT Maximum Output Voltage Swing SR Slew Rate GBW Gain-Bandwidth Product ZO IS Open-Loop Output Impedance Supply Current MIN TYP 10 0.3 MAX 40 VCM = 0V VCM = 0V 0.1Hz to 10Hz (Note 4) 12 25 35 fO = 10Hz (Note 5) fO = 1000Hz, 100% tested fO = 10Hz (Note 4 and 6) fO = 1000Hz, 100% tested 1.00 0.85 4.7 1.0 VCM = 11V VS = 4V to 18V RL 2k, VO = 12V RL 1k, VO = 10V RL 600, VO = 10V RL 2k RL 600 AVCL = -1 AVCL = -1 fO = 20kHz (Note 7) fO = 200kHz (Note 7) VO = 0, IO = 0 ELECTRICAL CHARACTERISTICS -55C TA 125C. VS = 15V, unless otherwise noted. 300 20 5 11.0 12.2 114 126 117 133 7.0 30.0 5.0 20.0 3.0 15.0 12.3 13.0 11.0 12.2 11.0 15.0 5.0 6.0 50 75 13 20 80 7.4 LT1028 LT1128 LT1028 LT1128 LT1028M/C LT1128M/C MIN TYP 20 0.3 MAX 80 UNITS V V/Mo 50 90 75 18 30 35 100 180 90 nA nA nVP-P 1.7 1.1 10.0 1.6 1.0 0.9 4.7 1.0 1.9 1.2 12.0 1.8 nV/Hz nV/Hz pA/Hz pA/Hz 9.5 300 20 5 12.2 126 132 30.0 20.0 15.0 13.0 12.2 15.0 6.0 75 20 80 7.6 10.5 M k pF V dB dB V/V V/V V/V V V V/s V/s MHz MHz mA 11.0 110 110 5.0 3.5 2.0 12.0 10.5 11.0 4.5 50 11 The denotes the specifications which apply over the temperature range LT1028M LT1128M LT1028AM LT1128AM SYMBOL VOS VOS Temp IOS IB PARAMETER Input Offset Voltage Average Input Offset Drift CONDITIONS (Note 2) (Note 8) VCM = 0V VCM = 0V CMRR PSRR AVOL Input Offset Current Input Bias Current Input Voltage Range Common Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain VOUT IS Maximum Output Voltage Swing Supply Current MIN VCM = 10.3V VS = 4.5V to 16V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k TYP 30 0.2 25 40 10.3 11.7 106 122 110 130 3.0 14.0 2.0 10.0 10.3 11.6 8.7 MAX 120 0.8 MIN 90 150 10.3 100 104 2.0 1.5 10.3 11.5 TYP 45 0.25 MAX 180 1.0 UNITS V V/C 30 50 11.7 120 130 14.0 10.0 11.6 9.0 180 300 nA nA V dB dB V/V V/V V mA 13.0 3 LT1028/LT1128 ELECTRICAL CHARACTERISTICS 0C TA 70C. VS = 15V, unless otherwise noted. The denotes the specifications which apply over the temperature range LT1028C LT1128C LT1028AC LT1128AC SYMBOL VOS V OS Temp IOS IB PARAMETER Input Offset Voltage Average Input Offset Drift CONDITIONS (Note 2) (Note 8) VCM = 0V VCM = 0V CMRR PSRR AVOL Input Offset Current Input Bias Current Input Voltage Range Common Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain VOUT Maximum Output Voltage Swing IS Supply Current MIN VCM = 10.5V VS = 4.5V to 18V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k RL 600 (Note 10) TYP 15 0.1 15 30 10.5 12.0 110 124 114 132 5.0 25.0 4.0 18.0 11.5 12.7 9.5 11.0 8.0 MAX 80 0.8 MIN 65 120 10.5 106 107 3.0 2.5 11.5 9.0 10.5 TYP 30 0.2 MAX 125 1.0 UNITS V V/C 22 40 12.0 124 132 25.0 18.0 12.7 10.5 8.2 130 240 nA nA V dB dB V/V V/V V V mA 11.5 ELECTRICAL CHARACTERISTICS The denotes the specifications which apply over the temperature range - 40C TA 85C. VS = 15V, unless otherwise noted. (Note 11) LT1028C LT1028AC LT1128C LT1128AC SYMBOL VOS V OS Temp IOS IB PARAMETER Input Offset Voltage Average Input Offset Drift CMRR PSRR AVOL Input Offset Current Input Bias Current Input Voltage Range Common Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain VOUT IS Maximum Output Voltage Swing Supply Current CONDITIONS (Note 8) VCM = 0V VCM = 0V VCM = 10.5V VS = 4.5V to 18V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: Input Offset Voltage measurements are performed by automatic test equipment approximately 0.5 sec. after application of power. In addition, at TA = 25C, offset voltage is measured with the chip heated to approximately 55C to account for the chip temperature rise when the device is fully warmed up. Note 3: Long Term Input Offset Voltage Stability refers to the average trend line of Offset Voltage vs. Time over extended periods after the first 30 days of operation. Excluding the initial hour of operation, changes in VOS during the first 30 days are typically 2.5V. Note 4: This parameter is tested on a sample basis only. Note 5: 10Hz noise voltage density is sample tested on every lot with the exception of the S8 and S16 packages. Devices 100% tested at 10Hz are available on request. Note 6: Current noise is defined and measured with balanced source resistors. The resultant voltage noise (after subtracting the resistor noise 4 MIN TYP 20 0.2 20 35 10.4 11.8 108 123 112 131 4.0 20.0 3.0 14.0 11.0 12.5 8.5 MAX 95 0.8 MIN 80 140 10.4 102 106 2.5 2.0 11.0 11.0 TYP 35 0.25 MAX 150 1.0 UNITS V V/C 28 45 11.8 123 131 20.0 14.0 12.5 8.7 160 280 nA nA V dB dB V/V V/V V mA 12.5 on an RMS basis) is divided by the sum of the two source resistors to obtain current noise. Maximum 10Hz current noise can be inferred from 100% testing at 1kHz. Note 7: Gain-bandwidth product is not tested. It is guaranteed by design and by inference from the slew rate measurement. Note 8: This parameter is not 100% tested. Note 9: The inputs are protected by back-to-back diodes. Current-limiting resistors are not used in order to achieve low noise. If differential input voltage exceeds 1.8V, the input current should be limited to 25mA. Note 10: This parameter guaranteed by design, fully warmed up at TA = 70C. It includes chip temperature increase due to supply and load currents. Note 11: The LT1028/LT1128 are designed, characterized and expected to meet these extended temperature limits, but are not tested at -40C and 85C. Guaranteed I grade parts are available. Consult factory. LT1028/LT1128 U W TYPICAL PERFOR A CE CHARACTERISTICS 10Hz Voltage Noise Distribution Wideband Voltage Noise (0.1Hz to Frequency Indicated) Wideband Noise, DC to 20kHz 180 10 VS = 15V TA = 25C 500 UNITS MEASURED FROM 4 RUNS NUMBER OF UNITS 140 120 VS = 15V TA = 25C RMS VOLTAGE NOISE (V) 158 148 160 100 80 70 57 60 40 28 20 8 74 3 2 2 2 12 0 0.6 0.1 VERTICAL SCALE = 0.5V/DIV HORIZONTAL SCALE = 0.5ms/DIV 3 21 1 1 0.8 1.0 1.2 1.4 1.6 1.8 2.0 VOLTAGE NOISE DENSITY (nV/Hz) 1 0.01 100 2.2 1k 100k 10k BANDWIDTH (Hz) Total Noise vs Matched Source Resistance Total Noise vs Unmatched Source Resistance 100 RS + 10 AT 10Hz AT 1kHz 1 2 RS NOISE ONLY VS = 15V TA = 25C 0.1 CURRENT NOISE DENSITY (pA/Hz) RS TOTAL NOISE DENSITY (nV/Hz) TOTAL NOISE DENSITY (nV/Hz) Current Noise Spectrum 100 100 - 10 AT 1kHz AT 10Hz 1 2 RS NOISE ONLY VS = 15V TA = 25C 10 30 100 300 1k 3k 3 MATCHED SOURCE RESISTANCE () 1 10k 10 LT1028/1128 * TPC07 100 1k FREQUENCY (Hz) 0 20 LT1028/1128 * TPC06 RMS VOLTAGE DENSITY (nV/Hz) 60 40 TIME (SEC) 80 10k Voltage Noise vs Temperature 10nV 8 10 2.0 VS = 15V TA = 25C 6 4 TIME (SEC) 1/f CORNER = 250Hz 0.01Hz to 1Hz Voltage Noise VS = 15V TA = 25C 2 TYPICAL 1 LT1028/1128 * TPC05 0.1Hz to 10Hz Voltage Noise 10nV MAXIMUM 1/f CORNER = 800Hz 10 30 100 300 1k 3k 10k 3 UNMATCHED SOURCE RESISTANCE () LT1028/1128 * TPC04 0 10 0.1 0.1 1 10M LT1028/1128 * TPC03 LT1020/1120 * TPC01 RS 1M 100 LT1028/1128 * TPC08 VS = 15V 1.6 1.2 AT 10Hz 0.8 AT 1kHz O.4 0 -50 -25 50 25 0 75 TEMPERATURE (C) 100 125 LT1028/1128 * TPC09 5 LT1028/LT1128 U W TYPICAL PERFOR A CE CHARACTERISTICS Distribution of Input Offset Voltage Offset Voltage Drift with Temperature of Representative Units VS = 15V TA = 25C 800 UNITS TESTED FROM FOUR RUNS 16 40 14 12 10 8 6 20 10 0 -10 -20 -30 4 2 -40 0 -50 -40 -30 -20 -10 0 10 20 30 40 50 OFFSET VOLTAGE (V) -50 -50 -25 50 25 0 75 TEMPERATURE (C) METAL CAN (H) PACKAGE 12 8 DUAL-IN-LINE PACKAGE PLASTIC (N) OR CERDIP (J) 5 1 2 3 4 TIME AFTER POWER ON (MINUTES) 50 BIAS CURRENT 20 10 OFFSET CURRENT 50 25 75 0 TEMPERATURE (C) SUPPLY CURRENT (mA) RMS VOLTAGE NOISE DENSITY (nV/Hz) AT 1kHz 0.75 20 LT1028/1128 * TPC16 40 5 POSITIVE INPUT CURRENT (UNDERCANCELLED) DEVICE 20 0 -20 -40 NEGATIVE INPUT CURRENT (OVERCANCELLED) DEVICE -60 100 125 -80 -15 10 5 -10 0 -5 COMMON MODE INPUT VOLTAGE (V) LT1028/1128 * TPC15 50 9 40 VS = 15V 7 VS = 5V 5 4 3 30 0 -20 -30 -40 LT1028/1128 * TPC17 125C -10 -50 125 VS = 15V 10 1 100 -50C 25C 20 0 -50 -25 50 25 0 75 TEMPERATURE (C) 15 Output Short-Circuit Current vs Time 2 5 10 15 SUPPLY VOLTAGE (V) 60 10 6 4 RCM = 20V 300M VS = 15V 65nA TA = 25C 80 30 8 AT 10Hz 3 2 TIME (MONTHS) LT1028/1128 * TPC12 Supply Current vs Temperature TA = 25C 1.25 1 0 LT1028/1128 * TPC14 1.5 6 -10 Bias Current Over the Common Mode Range 40 Voltage Noise vs Supply Voltage 0 -4 -6 100 LT1028/1128 * TPC13 0.5 0 -2 125 VS = 15V VCM = 0V 0 -50 -25 0 1.0 100 INPUT BIAS CURRENT (nA) INPUT BIAS AND OFFSET CURRENTS (nA) CHANGE IN OFFSET VOLTAGE (V) 60 16 0 2 Input Bias and Offset Currents Over Temperature VS = 15V TA = 25C 4 4 LT1028/1128 * TPC11 Warm-Up Drift 20 6 -8 LT1028/1128 * TPC10 24 VS = 15V TA = 25C t = 0 AFTER 1 DAY PRE-WARM UP 8 SHORT-CIRCUIT CURRENT (mA) SINKING SOURCING UNITS (%) 10 VS = 15V 30 OFFSET VOLTAGE (V) 18 OFFSET VOLTAGE CHANGE (V) 50 20 Long-Term Stability of Five Representative Units 125C 25C -50C 3 2 0 1 TIME FROM OUTPUT SHORT TO GROUND (MINUTES) LT1028/1128 * TPC18 LT1028/LT1128 U W TYPICAL PERFOR A CE CHARACTERISTICS 160 70 VS = 15V TA = 25C RL = 2k 60 40 50 50 40 40 30 30 GAIN 20 20 20 10 0 0 10 VS = 15V TA = 25C CL = 10pF -10 10k 10 100 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) 100k 1M 10M FREQUENCY (Hz) TYPICAL PRECISION OP AMP 40 AV = -1, RS = 2k 30 AV = -10 RS = 200 AV = -100 RS = 20 10 -10 100M LT1028 0.01 0 80 60 60 70 50 50 60 40 40 30 30 20 20 GAIN 10 -10 10k 100 100k 30pF 2k Voltage Gain vs Supply Voltage + 50 CL 40 AV = -1, RS = 2k 30 AV = -10 RS = 200 10 -10 100M AV = -100, RS = 20 0 10 100 100 1000 CAPACITIVE LOAD (pF) Maximum Undistorted Output vs Frequency PEAK-TO-PEAK OUTPUT VOLTAGE (V) VOLTAGE GAIN (V/V) TA = -55C TA = 25C TA = 125C 10 10000 30 VS = 15V TA = 25C VS = 15V TA = 25C VO = 10mVP-P LT1028/1128 * TPC 24 Voltage Gain vs Load Resistance RL = 600 - LT1028/1128 * TPC23 LT1028/1128 * TPC22 RL = 2k RS 20 0 1M 10M FREQUENCY (Hz) 10000 LT1028/1128 * TPC21 70 0 GAIN ERROR = CLOSED-LOOP GAIN OPEN-LOOP GAIN 10 1 FREQUENCY (Hz) 100 1000 CAPACITIVE LOAD (pF) 10 70 VS = 15V TA = 25C CL = 10pF VS = 15V TA = 25C LT1128 Capacitance Load Handling 10 VOLTAGE GAIN (V/V) CL 20 OVERSHOOT (%) VOLTAGE GAIN (dB) LT1128 10 + PHASE 0.1 - 50 LT1128 Gain Phase vs Frequency 1 100 2k RS LT1028/1128 * TPC20 Gain Error vs Frequency Closed-Loop Gain = 1000 0.1 30pF 60 0 LT1028/1128 * TPC19 0.001 70 OVERSHOOT (%) LT1028 80 -20 0.01 0.1 1 60 PHASE MARGIN (DEG) 60 100 LT1128 80 PHASE MARGIN (DEG) VOLTAGE GAIN (dB) 120 70 PHASE VOLTAGE GAIN (dB) 140 GAIN ERROR (%) LT1028 Capacitance Load Handling LT1028 Gain, Phase vs Frequency Voltage Gain vs Frequency ILMAX = 35mA AT -55C = 27mA AT 25C = 16mA AT 125C VS = 15V TA = 25C RL = 2k 25 20 15 LT1128 LT1028 10 5 1 1 0 5 10 15 SUPPLY VOLTAGE (V) 20 LT1028/1128 * TPC25 0.1 1 LOAD RESISTANCE (k) 10 LT1028/1128 * TPC26 10k 100k 1M FREQUENCY (Hz) 10M LT1028/1128 * TPC27 7 LT1028/LT1128 U W TYPICAL PERFOR A CE CHARACTERISTICS LT1028 Slew Rate, Gain-Bandwidth Product Over Temperature LT1028 Small-Signal Transient Response LT1028 Large-Signal Transient Response 50mV SLEW RATE (V/s) 17 5V/DIV 20mV/DIV 10V 90 VS = 15V -10V -50mV 1s/DIV AV = -1, RS = RF = 2k, C F = 15pF 0.2s/DIV AV = -1, RS = RF = 2k CF = 15pF, CL = 80pF 80 GBW 16 FALL 70 15 RISE 60 14 50 13 40 12 -50 -25 50 25 75 0 TEMPERATURE (C) 100 30 125 GAIN-BANDWIDTH PRODUCT (fO = 20kHz), (MHz) 18 LT1028/1128 * TPC30 LT1128 Large-Signal Transient Response LT1128 Slew Rate, Gain-Bandwidth Product Over Temperature LT1128 Small-Signal Transient Response FALL 8 50mV 10V 0V SLEW RATE (V/s) 7 0V -10V -50mV RISE 6 30 GBW 5 4 20 3 2 2s/DIV 0.2s/DIV AV = 1, C L = 10pF AV = -1, RS = RF = 2k, C F = 30pF 10 1 0 -50 -25 75 50 25 0 TEMPERATURE (C) 100 125 GAIN-BANDWIDTH PRODUCT (fO = 200kHz), (MHz) 9 LT1028/1128 * TPC33 LT1128 Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor Closed-Loop Output Impedance 100 IO = 1mA VS = 15V TA = 25C 100 10k LT1128 LT1028 1 0.1 LT1128 SLEW GBW 10 100 SLEW RATE 1 10 SLEW RATE (V/s) AV = 1000 1k 1 100 AV = 5 0.01 COC FROM PIN 5 TO PIN 6 VS = 15V TA = 25C LT1028 0.001 10 100 10k 1k FREQUENCY (Hz) 100k 1M LT1028/1128 * TPC34 8 GBW 10 0.1 1 1 10 100 1000 10000 OVER-COMPENSATION CAPACITOR (pF) LT1028/1128 * TPC35 0.1 1 10 10 100 1000 10000 OVER-COMPENSATION CAPACITOR (pF) LT1028/1128 * TPC36 GAIN AT 20kHz SLEW RATE (V/s) 10 1k GAIN AT 200kHz OUTPUT IMPEDANCE () 100 LT1028 Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor LT1028/LT1128 U W TYPICAL PERFOR A CE CHARACTERISTICS Common Mode Rejection Ratio vs Frequency V+ COMMON MODE REJECTION RATIO (dB) 140 -2 VS = 5V -3 VS = 15V -4 4 3 VS = 5V TO 15V 2 1 V 120 100 LT1128 50 25 0 75 TEMPERATURE (C) 60 40 20 10 100k 10k 1k FREQUENCY (Hz) 100 LT1028/1128 * TPC37 TOTAL HARMONIC DISTORTION (%) AV = 1000 RL = 600 AV = -1000 RL = 2k AV = 1000 RL = 600 VO = 20VP-P VS = 15V TA = 25C 10 FREQUENCY (kHz) 0.01 INVERTING GAIN 0.001 MEASURED EXTRAPOLATED 10 100 1k 10k CLOSED LOOP GAIN 1 100 1k 10k 100k 1M 10M FREQUENCY (Hz) 10 1.0 100k 100k FREQUENCY (Hz) LT1028/1128 * TPC41 1M LT1028/1128 * TPC42 LT1128 Total Harmonic Distortion vs Closed-Loop Gain AV = 1000 RL = 2k TOTAL HARMONIC DISTORTION (%) 0.1 AV = 1000 RL = 600 AV = -1000 RL = 2k 0.001 1.0 20 0.1 10k 0.0001 100 1.0 0.01 40 High Frequency Voltage Noise vs Frequency NON-INVERTING GAIN LT1128 Total Harmonic Distortion vs Frequency and Load Resistance 0.1 60 10 VO = 20VP-P f = 1kHz VS = 15V TA = 25C RL = 10k LT1028/1128 * TPC40 TOTAL HARMONIC DISTORTION (%) 1 POSITIVE SUPPLY 80 LT1028/1128 * TPC39 0.1 AV = 1000 RL = 2k 0.001 NEGATIVE SUPPLY 100 LT1028 Total Harmonic Distortion vs Closed-Loop Gain 0.1 0.01 120 0 0.1 10M 1M VS = 15V TA = 25C 140 LT1028/1128 * TPC38 LT1028 Total Harmonic Distortion vs Frequency and Load Resistance TOTAL HARMONIC DISTORTION (%) 160 0 125 100 LT1028 80 - -50 -25 VS = 15V TA = 25C NOISE VOLTAGE DENSITY (nV//Hz) COMMON MODE LIMIT (V) REFERRED TO POWER SUPPLY -1 Power Supply Rejection Ratio vs Frequency POWER SUPPLY REJECTION RATIO (dB) Common Mode Limit Over Temperature AV = 1000 RL = 600 VO = 20VP-P VS = 15V TA = 25C 10 FREQUENCY (kHz) 100 LT1028/1128 * TPC43 VO = 20VP-P f = 1kHz VS = 15V TA = 25C RL = 10k 0.01 NON-INVERTING GAIN INVERTING GAIN 0.001 MEASURED EXTRAPOLATED 0.0001 10 1k 10k 100 CLOSED LOOP GAIN 100k LT1028/1128 * TPC44 9 LT1028/LT1128 U S I FOR ATIO - OISE U W U UO APPLICATI Voltage Noise vs Current Noise The LT1028/LT1128's less than 1nV/Hz voltage noise is three times better than the lowest voltage noise heretofore available (on the LT1007/1037). A necessary condition for such low voltage noise is operating the input transistors at nearly 1mA of collector currents, because voltage noise is inversely proportional to the square root of the collector current. Current noise, however, is directly proportional to the square root of the collector current. Consequently, the LT1028/LT1128's current noise is significantly higher than on most monolithic op amps. Therefore, to realize truly low noise performance it is important to understand the interaction between voltage noise (en), current noise (In) and resistor noise (rn). Total Noise vs Source Resistance The total input referred noise of an op amp is given by et = [en2 + rn2 + (InReq)2]1/2 where Req is the total equivalent source resistance at the two inputs, and rn = 4kTReq = 0.13Req in nV/Hz at 25C As a numerical example, consider the total noise at 1kHz of the gain 1000 amplifier shown below. 100 The plot also shows that current noise is more dominant at low frequencies, such as 10Hz. This is because resistor noise is flat with frequency, while the 1/f corner of current noise is typically at 250Hz. At 10Hz when Req > 1k, the current noise term will exceed the resistor noise. When the source resistance is unmatched, the total noise versus unmatched source resistance plot should be consulted. Note that total noise is lower at source resistances below 1k because the resistor noise contribution is less. When RS > 1k total noise is not improved, however. This is because bias current cancellation is used to reduce input bias current. The cancellation circuitry injects two correlated current noise components into the two inputs. With matched source resistors the injected current noise creates a common-mode voltage noise and gets rejected by the amplifier. With source resistance in one input only, the cancellation noise is added to the amplifier's inherent noise. In summary, the LT1028/LT1128 are the optimum amplifiers for noise performance, provided that the source resistance is kept low. The following table depicts which op amp manufactured by Linear Technology should be used to minimize noise, as the source resistance is increased beyond the LT1028/LT1128's level of usefulness. 100k - 100 largest term, as in the example above, and the LT1028/ LT1128's voltage noise becomes negligible. As Req is further increased, current noise becomes important. At 1kHz, when Req is in excess of 20k, the current noise component is larger than the resistor noise. The total noise versus matched source resistance plot illustrates the above calculations. LT1028 LT1128 + 1028/1128 AI01 Best Op Amp for Lowest Total Noise vs Source Resistance Req = 100 + 100 || 100k 200 rn = 0.13200 = 1.84nVHz en = 0.85nVHz In = 1.0pA/Hz et = [0.852 + 1.842 + (1.0 x 0.2) 2]1/2 = 2.04nV/Hz Output noise = 1000 et = 2.04V/Hz At very low source resistance (Req < 40) voltage noise dominates. As Req is increased resistor noise becomes the 10 SOURCE RESISTANCE() (Note 1) 0 to 400 400 to 4k 4k to 40k 40k to 500k 500k to 5M >5M BEST OP AMP AT LOW FREQ(10Hz) WIDEBAND(1kHz) LT1028/LT1128 LT1007/1037 LT1001 LT1012 LT1012 or LT1055 LT1055 LT1028/LT1128 LT1028/LT1128 LT1007/1037 LT1001 LT1012 LT1055 Note 1: Source resistance is defined as matched or unmatched, e.g., RS = 1k means: 1k at each input, or 1k at one input and zero at the other. LT1028/LT1128 U S I FOR ATIO - OISE U W U UO APPLICATI Noise Testing - Voltage Noise The LT1028/LT1128's RMS voltage noise density can be accurately measured using the Quan Tech Noise Analyzer, Model 5173 or an equivalent noise tester. Care should be taken, however, to subtract the noise of the source resistor used. Prefabricated test cards for the Model 5173 set the device under test in a closed-loop gain of 31 with a 60 source resistor and a 1.8k feedback resistor. The noise of this resistor combination is 0.1358 = 1.0nV/Hz. An LT1028/LT1128 with 0.85nV/Hz noise will read (0.852 + 1.02)1/2 = 1.31nV/Hz. For better resolution, the resistors should be replaced with a 10 source and 300 feedback resistor. Even a 10 resistor will show an apparent noise which is 8% to 10% too high. The 0.1Hz to 10Hz peak-to-peak noise of the LT1028/ LT1128 is measured in the test circuit shown. The frequency response of this noise tester indicates that the 0.1Hz corner is defined by only one zero. The test time to measure 0.1Hz to 10Hz noise should not exceed 10 seconds, as this time limit acts as an additional zero to eliminate noise contributions from the frequency band below 0.1Hz. Measuring the typical 35nV peak-to-peak noise performance of the LT1028/LT1128 requires special test precautions: (a) The device should be warmed up for at least five minutes. As the op amp warms up, its offset voltage changes typically 10V due to its chip temperature increasing 30C to 40C from the moment the power supplies are turned on. In the 10 second measurement interval these temperature-induced effects can easily exceed tens of nanovolts. (b) For similar reasons, the device must be well shielded from air current to eliminate the possibility of thermoelectric effects in excess of a few nanovolts, which would invalidate the measurements. (c) Sudden motion in the vicinity of the device can also "feedthrough" to increase the observed noise. A noise-voltage density test is recommended when measuring noise on a large number of units. A 10Hz noisevoltage density measurement will correlate well with a 0.1Hz to 10Hz peak-to-peak noise reading since both results are determined by the white noise and the location of the 1/f corner frequency. 0.1Hz to 10Hz Peak-to-Peak Noise Tester Frequency Response 0.1Hz to 10Hz Noise Test Circuit 100 0.1F 90 100k 2k * 10 + 4.7F + 22F 4.3k LT1001 - 2.2F 100k SCOPE x1 RIN = 1M 110k VOLTAGE GAIN = 50,000 * DEVICE UNDER TEST NOTE ALL CAPACITOR VALUES ARE FOR NONPOLARIZED CAPACITORS ONLY 24.3k GAIN (dB) 80 - 70 60 50 40 0.1F 30 0.01 1028/1128 AI02 0.1 1.0 10 FREQUENCY (Hz) 100 LT1028/1128 * AI03 11 LT1028/LT1128 U S I FOR ATIO - OISE W U U UO APPLICATI Noise Testing - Current Noise Current noise density (In) is defined by the following formula, and can be measured in the circuit shown: 10Hz current noise is not tested on every lot but it can be inferred from 100% testing at 1kHz. A look at the current noise spectrum plot will substantiate this statement. The only way 10Hz current noise can exceed the guaranteed limits is if its 1/f corner is higher than 800Hz and/or its white noise is high. If that is the case then the 1kHz test will fail. [eno2 - (31 x 18.4nV/Hz)2]1/2 In = 20k x 31 1.8k 10k 60 10k - LT1028 LT1128 10Hz voltage noise density is sample tested on every lot. Devices 100% tested at 10Hz are available on request for an additional charge. eno Automated Tester Noise Filter + 10 1028/1128 AI04 100% Noise Testing The 1kHz voltage and current noise is 100% tested on the LT1028/LT1128 as part of automated testing; the approximate frequency response of the filters is shown. The limits on the automated testing are established by extensive correlation tests on units measured with the Quan Tech Model 5173. -10 -20 CURRENT NOISE -30 -40 -50 100 1k 10k 100k FREQUENCY (Hz) LT1028/1128 * AI05 W U UO S I FOR ATIO 1k 15V General 1 2 The LT1028/LT1128 series devices may be inserted directly into OP-07, OP-27, OP-37, LT1007 and LT1037 sockets with or without removal of external nulling components. In addition, the LT1028/LT1128 may be fitted to 5534 sockets with the removal of external compensation components. Offset Voltage Adjustment The input offset voltage of the LT1028/LT1128 and its drift with temperature, are permanently trimmed at wafer testing to a low level. However, if further adjustment of VOS is necessary, the use of a 1k nulling potentiometer will not degrade drift with temperature. Trimming to a value other 12 VOLTAGE NOISE U APPLICATI 0 NOISE FILTER LOSS (dB) If the Quan Tech Model 5173 is used, the noise reading is input-referred, therefore the result should not be divided by 31; the resistor noise should not be multiplied by 31. INPUT 3 8 - LT1028 LT1128 + 7 6 OUTPUT 4 -15V 1028/1128 AI06 than zero creates a drift of (VOS/300)V/C, e.g., if VOS is adjusted to 300V, the change in drift will be 1V/C. The adjustment range with a 1k pot is approximately 1.1mV. Offset Voltage and Drift Thermocouple effects, caused by temperature gradients across dissimilar metals at the contacts to the input LT1028/LT1128 W U U UO APPLICATI S I FOR ATIO terminals, can exceed the inherent drift of the amplifier unless proper care is exercised. Air currents should be minimized, package leads should be short, the two input leads should be close together and maintained at the same temperature. The circuit shown to measure offset voltage is also used as the burn-in configuration for the LT1028/LT1128. Test Circuit for Offset Voltage and Offset Voltage Drift with Temperature 10k* 15V 2 200* 3 10k* - 7 LT1028 LT1128 + 6 VO Frequency Response The LT1028's Gain, Phase vs Frequency plot indicates that the device is stable in closed-loop gains greater than +2 or -1 because phase margin is about 50 at an open-loop gain of 6dB. In the voltage follower configuration phase margin seems inadequate. This is indeed true when the output is shorted to the inverting input and the noninverting input is driven from a 50 source impedance. However, when feedback is through a parallel R-C network (provided CF < 68pF), the LT1028 will be stable because of interaction between the input resistance and capacitance and the feedback network. Larger source resistance at the noninverting input has a similar effect. The following voltage follower configurations are stable: 4 33pF -15V VO = 100VOS * RESISTORS MUST HAVE LOW THERMOELECTRIC POTENTIAL 2k 1028/1128 AI08 - Unity-Gain Buffer Applications (LT1128 Only) When RF 100 and the input is driven with a fast, largesignal pulse (>1V), the output waveform will look as shown in the pulsed operation diagram. - LT1028 500 + 50 LT1028 + 50 1028/1128 AI09 RF - OUTPUT 6V/s + 1028/1128 AI07 During the fast feedthrough-like portion of the output, the input protection diodes effectively short the output to the input and a current, limited only by the output short-circuit protection, will be drawn by the signal generator. With RF 500, the output is capable of handling the current requirements (IL 20mA at 10V) and the amplifier stays in its active mode and a smooth transition will occur. As with all operational amplifiers when RF > 2k, a pole will be created with RF and the amplifier's input capacitance, creating additional phase shift and reducing the phase margin. A small capacitor (20pF to 50pF) in parallel with RF will eliminate this problem. Another configuration which requires unity-gain stability is shown below. When CF is large enough to effectively short the output to the input at 15MHz, oscillations can occur. The insertion of RS2 500 will prevent the LT1028 from oscillating. When RS1 500, the additional noise contribution due to the presence of RS2 will be minimal. When RS1 100, RS2 is not necessary, because RS1 represents a heavy load on the output through the CF short. When 100 < RS1 < 500, RS2 should match RS1 . For example, RS1 = RS2 = 300 will be stable. The noise increase due to RS2 is 40%. C1 R1 RS1 RS2 - LT1028 + 1028/1128 AI10 13 LT1028/LT1128 W U U UO APPLICATI S I FOR ATIO If CF is only used to cut noise bandwidth, a similar effect can be achieved using the over-compensation terminal. The Gain, Phase plot also shows that phase margin is about 45 at gain of 10 (20dB). The following configura- tion has a high (70%) overshoot without the 10pF capacitor because of additional phase shift caused by the feedback resistor - input capacitance pole. The presence of the 10pF capacitor cancels this pole and reduces overshoot to 5%. 10pF Over-Compensation 10k 1.1k The LT1028/LT1128 are equipped with a frequency overcompensation terminal (Pin 5). A capacitor connected between Pin 5 and the output will reduce noise bandwidth. Details are shown on the Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor plot. An additional benefit is increased capacitive load handling capability. - LT1028 + 50 1028/1128 AI11 U TYPICAL APPLICATIO S Strain Gauge Signal Conditioner with Bridge Excitation Low Noise Voltage Regulator 28V LT1021-5 3 5.0V + 7 LT1128 2 - 121 330 LT317A 6 10 4 350 BRIDGE 3 301k* 15V + 4 -15V 14 LT1021-10 - + LT1028 10k ZERO TRIM 2 + 4 2N6387 - 6 0V TO 10V OUTPUT 1F 30.1k* 5k GAIN TRIM 49.9* 1000pF 20V OUTPUT 2k -15V *RN60C FILM RESISTORS 6 330 LT1028 7 7 LT1028 2 1k REFERENCE OUTPUT 15V - 2.3k PROVIDES PRE-REG AND CURRENT LIMITING 28V -15V 3 10 + 15V 2k 1028/1128 TA04 330 THE LT1028's NOISE CONTRIBUTION IS NEGLIGIBLE COMPARED TO THE BRIDGE NOISE. 1028/1128 TA05 LT1028/LT1128 U TYPICAL APPLICATIO S Paralleling Amplifiers to Reduce Voltage Noise Phono Preamplifier 10 + 1.5k A1 LT1028 787 - 7.5 2 470 + 1.5k A2 LT1028 + OUTPUT 4 -15V OUTPUT ALL RESISTORS METAL FILM MAG PHONO INPUT + 470 + 47k LT1028 0.33F 6 LT1028 3 - - 1028/1128 TA06 1.5k An LT1028 Tape Head Amplifier - 7.5 10k 7 - 100pF 4.7k 7.5 0.1F 15V 0.1F 470 499 31.6k 1. ASSUME VOLTAGE NOISE OF LT1028 AND 7.5 SOURCE RESISTOR = 0.9nV/Hz. 2. GAIN WITH n LT1028s IN PARALLEL = n x 200. 3. OUTPUT NOISE = n x 200 x 0.9nV/Hz. OUTPUT NOISE 0.9 4. INPUT REFERRED NOISE = = nV/Hz. n x 200 n 5. NOISE CURRENT AT INPUT INCREASES n TIMES. 2V 6. IF n = 5, GAIN = 1000, BANDWIDTH = 1MHz, RMS NOISE, DC TO 1MHz = = 0.9V. 5 10 2 - 6 LT1028 TAPE HEAD INPUT 3 OUTPUT + 1028/1128 TA03 ALL RESISTORS METAL FILM 1028/1128 TA07 Low Noise, Wide Bandwidth Instrumentation Amplifier -INPUT Gyro Pick-Off Amplifier + 300 10k LT1028 - 820 GYRO TYPICAL- NORTHROP CORP. GR-F5AH7-5B 68pF SINE DRIVE 50 10 + - 820 - 68pF 300 LT1028 +INPUT LT1028 OUTPUT * - + OUTPUT TO SYNC DEMODULATOR LT1028 1k + 10k GAIN = 1000, BANDWIDTH = 1MHz INPUT REFERRED NOISE = 1.5nV/Hz AT 1kHz WIDEBAND NOISE -DC to 1MHz = 3VRMS IF BW LIMITED TO DC TO 100kHz = 0.55VRMS 100 1028/1128 TA09 1028/1128 TA08 15 LT1028/LT1128 U TYPICAL APPLICATIO S Super Low Distortion Variable Sine Wave Oscillator R1 C1 0.047 20 20 C2 0.047 2k 1VRMS OUTPUT 1.5kHz TO 15kHz 1 f= 2RC WHERE R1C1 = R2C2 4.7k 15V + 2k ( LT1028 R2 - 5.6k 2.4k ) LT1004-1.2V 10pF 22k 15F + 10k - 2N4338 MOUNT 1N4148s IN CLOSE PROXIMITY 100k LT1055 560 TRIM FOR LOWEST DISTORTION + 20k 10k <0.0018% DISTORTION AND NOISE. MEASUREMENT LIMITED BY RESOLUTION OF HP339A DISTORTION ANALYZER 1028/1128 TA10 Chopper-Stabilized Amplifier 15V 1N758 3 7 + 6 LT1052 2 - 8 4 1 0.1 0.1 0.01 1N758 15V -15V 100k 130 68 1 INPUT 3 7 + 8 LT1028 2 30k - 4 OUTPUT 10k -15V 10 1028/1128 TA11 16 LT1028/LT1128 W W SCHE ATIC DIAGRA NULL 8 R6 130 R5 130 NULL 1 V+ 7 Q4 R2 3k R1 3k 1.1mA 2.3mA 400A C1 257pF 500A Q17 R10 400 Q16 900A R11 400 Q19 R10 C2 500 Q18 900A Q26 Q6 Q5 3 3 1 1 Q11 NONINVERTING INPUT Q8 Q7 R11 100 Q9 C3 250pF 4.5A 3 Q10 4.5A Q22 Q24 4.5A 4.5A Q1 Q2 Q25 OUTPUT 6 1.5A Q12 R12 240 Q13 C4 35pF Q14 Q27 1.5A INVERTING INPUT 2 0 1.8mA BIAS Q3 300A Q15 Q23 Q21 R7 80 R8 480 600A Q20 V- 4 C2 = 50pF for LT1028 C2 = 275pF for LT1128 5 OVERCOMP 1028/1128 TA13 17 LT1028/LT1128 U PACKAGE DESCRIPTIO J8 Package 8-Lead CERDIP (Narrow .300 Inch, Hermetic) OBSOLETE PACKAGE (Reference LTC DWG # 05-08-1110) CORNER LEADS OPTION (4 PLCS) 0.023 - 0.045 (0.584 - 1.143) HALF LEAD OPTION 0.045 - 0.068 (1.143 - 1.727) FULL LEAD OPTION 0.405 (10.287) MAX 0.005 (0.127) MIN 8 6 7 5 0.025 (0.635) RAD TYP 0.220 - 0.310 (5.588 - 7.874) 1 2 3 0.300 BSC (0.762 BSC) 4 0.200 (5.080) MAX 0.015 - 0.060 (0.381 - 1.524) 0.008 - 0.018 (0.203 - 0.457) 0 - 15 NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS 0.045 - 0.065 (1.143 - 1.651) 0.014 - 0.026 (0.360 - 0.660) 0.125 3.175 MIN 0.100 (2.54) BSC J8 1298 N8 Package 8-Lead PDIP (Narrow .300 Inch) (Reference LTC DWG # 05-08-1510) 0.300 - 0.325 (7.620 - 8.255) 0.009 - 0.015 (0.229 - 0.381) ( 0.045 - 0.065 (1.143 - 1.651) +0.889 -0.381 0.130 0.005 (3.302 0.127) 0.065 (1.651) TYP +0.035 0.325 -0.015 8.255 0.400* (10.160) MAX ) 8 7 6 5 1 2 3 4 0.255 0.015* (6.477 0.381) 0.100 (2.54) BSC 0.125 (3.175) 0.020 MIN (0.508) MIN 0.018 0.003 (0.457 0.076) N8 1098 *THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm) S8 Package 8-Lead Plastic Small Outline (Narrow .150 Inch) 0.189 - 0.197* (4.801 - 5.004) (Reference LTC DWG # 05-08-1610) 0.010 - 0.020 x 45 (0.254 - 0.508) 0.008 - 0.010 (0.203 - 0.254) 0.053 - 0.069 (1.346 - 1.752) 0- 8 TYP 0.016 - 0.050 (0.406 - 1.270) 0.014 - 0.019 (0.355 - 0.483) TYP *DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE 18 8 7 6 5 0.004 - 0.010 (0.101 - 0.254) 0.050 (1.270) BSC 0.150 - 0.157** (3.810 - 3.988) 0.228 - 0.244 (5.791 - 6.197) SO8 1298 1 2 3 4 LT1028/LT1128 U PACKAGE DESCRIPTIO S Package 16-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610) 0.386 - 0.394* (9.804 - 10.008) 16 15 14 13 12 11 10 9 0.150 - 0.157** (3.810 - 3.988) 0.228 - 0.244 (5.791 - 6.197) 1 0.010 - 0.020 x 45 (0.254 - 0.508) 0.008 - 0.010 (0.203 - 0.254) 2 3 4 5 6 7 8 0.053 - 0.069 (1.346 - 1.752) 0.004 - 0.010 (0.101 - 0.254) 0 - 8 TYP 0.050 (1.270) BSC 0.014 - 0.019 (0.355 - 0.483) TYP 0.016 - 0.050 (0.406 - 1.270) S16 1098 *DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE H Package 3-Lead TO-39 Metal Can (Reference LTC DWG # 05-08-1330) 0.335 - 0.370 (8.509 - 9.398) DIA 0.027 - 0.045 (0.686 - 1.143) 45TYP 0.028 - 0.034 (0.711 - 0.864) 0.305 - 0.335 (7.747 - 8.509) PIN 1 0.040 (1.016) MAX 0.230 (5.842) TYP 0.050 (1.270) MAX SEATING PLANE GAUGE PLANE 0.010 - 0.045* (0.254 - 1.143) 0.110 - 0.160 (2.794 - 4.064) INSULATING STANDOFF 0.165 - 0.185 (4.191 - 4.699) 0.016 - 0.021** (0.406 - 0.533) REFERENCE PLANE 0.500 - 0.750 (12.700 - 19.050) H8 (TO-5) 0.230 PCD 1197 *LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE AND 0.045" BELOW THE REFERENCE PLANE 0.016 - 0.024 **FOR SOLDER DIP LEAD FINISH, LEAD DIAMETER IS (0.406 - 0.610) OBSOLETE PACKAGE Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LT1028/LT1128 U TYPICAL APPLICATIO Low Noise Infrared Detector 5V 10 + 100F 1k 33 SYNCHRONOUS DEMODULATOR + 100F 10k* OPTICAL CHOPPER WHEEL 267 5V 5V 1000F 3 + IR RADIATION 10k* 39 PHOTOELECTRIC PICK-OFF 2 7 + 6 LT1028 2 1/4 LTC1043 4 12 10k -5V INFRA RED ASSOCIATES, INC. HgCdTe IR DETECTOR 13 AT 77K 5V 6 LM301A 13 8 - 7 + 3 - 8 1M 1 16 -5V 30pF 7 + LT1012 3 4 14 2 - 6 DC OUT 8 1 4 -5V 10 1028/1128 TA12 RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT1806/LT1807 325MHz, 3.5nV/Hz Single and Dual Op Amps Slew Rate = 140V/s, Low Distortion at 5MHz: -80dBc 20 Linear Technology Corporation 1028fa LT/CP 0901 1.5K REV A * PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 FAX: (408) 434-0507 www.linear.com LINEAR TECHNOLOGY CORPORATION 1992