1
LT1931/LT1931A
1931fa
■
Fixed Frequency 1.2MHz/2.2MHz Operation
■
Very Low Noise: 1mV
P-P
Output Ripple
■
–5V at 350mA from 5V Input
■
–12V at 150mA from 5V Input
■
Uses Small Surface Mount Components
■
Wide Input Range: 2.6V to 16V
■
Low Shutdown Current: <1µA
■
Low V
CESAT
Switch: 400mV at 1A
■
Pin-for-Pin Compatible with the LT1611
■
Low Profile (1mm) ThinSOT
TM
Package
The LT
®
1931/LT1931A are the industry’s highest power
inverting SOT-23 current mode DC/DC converters. Both
parts include a 1A integrated switch allowing high current
outputs to be generated in a small footprint. The LT1931
switches at 1.2MHz while the LT1931A switches at 2.2MHz.
These high speeds enable the use of tiny, low cost
capacitors and inductors 2mm or less in height. The
LT1931 is capable of generating –5V at 350mA or –12V
at 150mA from a 5V supply, while the LT1931A can
generate –5V at 300mA using significantly smaller induc-
tors. Both parts are easy pin-for-pin upgrades for higher
power LT1611 applications.
The LT1931/LT1931A operate in a dual inductor inverting
topology that filters both the input side and output side
current. Very low output voltage ripple approaching 1mV
P-P
can be achieved when ceramic output capacitors are used.
Fixed frequency switching ensures a clean output free
from low frequency noise typically present with charge
pump solutions. The low impedance output remains within
1% of nominal during large load steps. The 36V switch
allows V
IN
to V
OUT
differential of up to 34V.
The LT1931/LT1931A are available in the 5-lead ThinSOT
package.
■
Disk Drive MR Head Bias
■
Digital Camera CCD Bias
■
LCD Bias
■
GaAs FET Bias
■
Local Low Noise/Low Impedance Negative Supply
1.2MHz/2.2MHz Inverting
DC/DC Converters in ThinSOT
Figure 1. 5V to –5V, 350mA Inverting DC/DC Converter
V
IN
V
IN
5V
V
OUT
–5V
350mA
1931 F01
SW
L1A
10µH
L1B
10µH
D1
GND
LT1931
C1: TAIYO YUDEN X5R JMK212BJ475MG
C2: TAIYO YUDEN X5R LMK212BJ105MG
C3: TAIYO YUDEN X5R JMK325BJ226MM
D1: ON SEMICONDUCTOR MBR0520
L1: SUMIDA CLS62-100
C1
4.7µFC3
22µF
C2
1µF
R2
10k
R1
29.4k C4
220pF
NFB
SHDN
LOAD CURRENT (mA)
0
50
EFFICIENCY (%)
55
65
70
75
100
85
100 200 250
1931 TA01
60
90
95
80
50 150 300 350
Efficiency
FEATURES
DESCRIPTIO
U
APPLICATIO S
U
TYPICAL APPLICATIO
U
, LTC and LT are registered trademarks of Linear Technology Corporation. ThinSOT is a
trademark of Linear Technology Corporation. All other trademarks are the property of their
respective owners.
2
LT1931/LT1931A
1931fa
LT1931 LT1931A
PARAMETER CONDITIONS MIN TYP MAX MIN TYP MAX UNITS
Minimum Operating Voltage 2.45 2.6 2.45 2.6 V
Maximum Operating Voltage 16 16 V
Feedback Voltage –1.275 –1.255 –1.235 –1.275 –1.255 –1.235 V
●–1.280 –1.230 –1.280 –1.230 V
NFB Pin Bias Current V
NFB
= –1.255V ●48 816 µA
Quiescent Current V
SHDN
= 2.4V, Not Switching 4.2 6 5.8 8 mA
Quiescent Current in Shutdown V
SHDN
= 0V, V
IN
= 3V 0.01 1 0.01 1 µA
Reference Line Regulation 2.6V ≤ V
IN
≤ 16V 0.01 0.05 0.01 0.05 %/V
Switching Frequency 1 1.2 1.4 1.8 2.2 2.6 MHz
●0.85 1.6 1.6 2.9 MHz
Maximum Duty Cycle ●84 90 75 82 %
Switch Current Limit (Note 3) 1 1.2 2 1 1.2 2.5 A
Switch V
CESAT
I
SW
= 1A 400 600 400 600 mV
Switch Leakage Current V
SW
= 5V 0.01 1 0.01 1 µA
SHDN Input Voltage, High 2.4 2.4 V
SHDN Input Voltage, Low 0.5 0.5 V
SHDN Pin Bias Current V
SHDN
= 3V 16 32 35 70 µA
V
SHDN
= 0V 0 0.1 0 0.1 µA
(Note 1)
V
IN
Voltage .............................................................. 16V
SW Voltage ................................................– 0.4V to 36V
NFB Voltage ............................................................. – 2V
Current Into NFB Pin............................................ ±1mA
SHDN Voltage .......................................................... 16V
Maximum Junction Temperature .......................... 125°C
Operating Temperature Range (Note 2) .. – 40°C to 85°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
ABSOLUTE AXI U RATI GS
WWWU
PACKAGE/ORDER I FOR ATIO
UU
W
The ● denotes specifications which apply over the full operating temperature range, otherwise specifications are TA = 25°C.
VIN = 3V, VSHDN = VIN, unless otherwise noted. (Note 2)
ELECTRICAL CHARACTERISTICS
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
Note 2: The LT1931E/LT1931AE are guaranteed to meet performance
specifications from 0°C to 70°C. Specifications over the –40°C to 85°C
operating temperature range are assured by design, characterization and
correlation with statistical process controls. LT1931I/LT1931AI are
guaranteed over the –40°C to 85°C temperature range.
Note 3: Current limit guaranteed by design and/or correlation to static test.
T
JMAX
= 125°C, θ
JA
= 150°C/ W
ORDER PART NUMBER S5 PART MARKING
Consult LTC Marketing for parts specified with wider operating temperature ranges.
LT1931ES5
LT1931AES5
LT1931IS5
LT1931AIS5
LTRA
LTSP
LTBZF
LTBZG
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marking: http://www.linear.com/leadfree/
SW 1
GND 2
TOP VIEW
S5 PACKAGE
5-LEAD PLASTIC TSOT-23
NFB 3
5 V
IN
4 SHDN
3
LT1931/LT1931A
1931fa
TYPICAL PERFOR A CE CHARACTERISTICS
UW
Quiescent Current
TEMPERATURE (°C)
–50
QUIESCENT CURRENT (mA)
4.5
5.0
5.5
25 75
1931 G01
4.0
3.5
3.0 –25 0 50
6.0
6.5
7.0
100
NOT SWITCHING
LT1931A
LT1931
TEMPERATURE (°C)
–50
–1.28
–1.27
–1.26
–1.25
–1.24
–1.22
–25 02550
1931 G02
75 100
–1.23
FEEDBACK VOLTAGE (V)
SHDN PIN VOLTAGE (V)
0
–10
SHDN PIN CURRENT (µA)
10
30
50
1234
1931 G03
5
70
90
0
20
40
60
80
6
LT1931A
TA = 25°C
LT1931
Feedback Pin Voltage Shutdown Pin Current
Current Limit Switch Saturation Voltage Oscillator Frequency
DUTY CYCLE (%)
10
CURRENT LIMIT (A)
0.8
1.2
90
1931 G04
0.4
030 50 70
20 40 60 80
1.6
0.6
1.0
0.2
1.4
T
A
= 25°C
SWITCH CURRENT (A)
0
0
VCESAT (V)
0.05
0.15
0.20
0.25
0.8
0.45
1931 G05
0.10
0.4
0.2 1.0
0.6 1.2
0.30
0.35
0.40
TA = 25°C
TEMPERATURE (°C)
–50
0.5
FREQUENCY (MHz)
0.9
1.3
1.7
–25 025 50
1931 G06
75
2.1
2.5
0.7
1.1
1.5
1.9
2.3
100
LT1931A
LT1931
UU
U
PI FU CTIO S
SW (Pin 1): Switch Pin. Connect inductor/diode here.
Minimize trace area at this pin to keep EMI down.
GND (Pin 2): Ground. Tie directly to local ground plane.
NFB (Pin 3): Feedback Pin. Reference voltage is –1.255V.
Connect resistive divider tap here. Minimize trace area.
The NFB bias current flows out of the pin. Set R1 and R2
according to:
For LT R V
R
OUT
1931 1 1 255
1 255
2410
6
:||–.
.•–
=
+
()
For LT A R V
R
OUT
1931 1 1 255
1 255
2810
6
:||–.
.•–
=
+
()
SHDN (Pin 4): Shutdown Pin. Tie to 2.4V or more to enable
device. Ground to shut down.
V
IN
(Pin 5): Input Supply Pin. Must be locally bypassed.
4
LT1931/LT1931A
1931fa
BLOCK DIAGRA
W
Figure 2
OPERATIO
U
The LT1931 uses a constant frequency, current mode
control scheme to provide excellent line and load regula-
tion. Operation can be best understood by referring to the
Block Diagram in Figure 2. At the start of each oscillator
cycle, the SR latch is set, turning on the power switch Q3.
A voltage proportional to the switch current is added to a
stabilizing ramp and the resulting sum is fed into the
positive terminal of the PWM comparator A2. When this
voltage exceeds the level at the negative input of A2, the SR
latch is reset, turning off the power switch. The level at the
negative input of A2 is set by the error amplifier (g
m
) and
is simply an amplified version of the difference between
the feedback voltage and the reference voltage of –1.255V.
In this manner, the error amplifier sets the correct peak
current level to keep the output in regulation. If the error
amplifier’s output increases, more current is taken from
the output; if it decreases, less current is taken. One
function not shown in Figure 2 is the current limit. The
switch current is constantly monitored and not allowed to
exceed the nominal value of 1.2A. If the switch current
reaches 1.2A, the SR latch is reset regardless of the state
of comparator A2. This current limit protects the power
switch as well as various external components connected
to the LT1931.
The Block Diagram for the LT1931A is identical except that
the oscillator is 2.2MHz and resistors R3 to R6 are one-half
the LT1931 values.
–
+
–
+
LATCH
RQ
S
0.01Ω
SW
DRIVER
COMPARATOR
2
SHUTDOWN
SHDN
4
1
–
+
Σ
RAMP
GENERATOR
R
C
C
C
1.2MHz
OSCILLATOR
GND
1931 BD
R6
80k
R4
150k
R3
30k
Q2
x10
Q1
Q3
R5
80k
V
IN
V
IN
5
NFB
C
PL
(OPTIONAL)
R2
(EXTERNAL)
R1
(EXTERNAL)
V
OUT
NFB
3
A2
A1
g
m
5
LT1931/LT1931A
1931fa
APPLICATIO S I FOR ATIO
WUUU
LT1931A AND LT1931 DIFFERENCES:
Switching Frequency
The key difference between the LT1931A and LT1931 is
the faster switching frequency of the LT1931A. At 2.2MHz,
the LT1931A switches at nearly twice the rate of the
LT1931. Care must be taken in deciding which part to use.
The high switching frequency of the LT1931A allows
smaller cheaper inductors and capacitors to be used in a
given application, but with a slight decrease in efficiency
and maximum output current when compared to the
LT1931. Generally, if efficiency and maximum output
current are critical, the LT1931 should be used. If applica-
tion size and cost are more important, the LT1931A will be
the better choice. In many applications, tiny inexpensive
chip inductors can be used with the LT1931A, reducing
solution cost.
Duty Cycle
The maximum duty cycle (DC) of the LT1931A is 75%
compared to 84% for the LT1931. The duty cycle for a
given application using the dual inductor inverting topol-
ogy is given by:
DC V
VV
OUT
IN OUT
=+
||
||| |
For a 5V to –5V application, the DC is 50% indicating that
the LT1931A can be used. A 5V to –16V application has a
DC of 76.2% making the LT1931 the right choice. The
LT1931A can still be used in applications where the DC, as
calculated above, is above 75%. However, the part must
be operated in the discontinuous conduction mode so that
the actual duty cycle is reduced.
INDUCTOR SELECTION
Several inductors that work well with the LT1931 are listed
in Table 1 and those for the LT1931A are listed in Table 2.
Besides these, there are many other inductors that can be
used. Consult each manufacturer for detailed information
and for their entire selection of related parts. Ferrite core
inductors should be used to obtain the best efficiency, as
core losses at frequencies above 1MHz are much lower for
ferrite cores than for powdered-iron units. When using
coupled inductors, choose one that can handle at least 1A
of current without saturating, and ensure that the inductor
has a low DCR (copper-wire resistance) to minimize I
2
R
power losses. If using uncoupled inductors, each inductor
need only handle one-half of the total switch current so
that 0.5A per inductor is sufficient. A 4.7µH to 15µH
coupled inductor or a 15µH to 22µH uncoupled inductor
will usually be the best choice for most LT1931 designs.
For the LT1931A, a 2.2µH to 4.7µH coupled inductor or a
3.3µH to 10µH uncoupled inductor will usually suffice. In
certain applications such as the “Charge Pump” inverting
DC/DC converter, only a single inductor is used. In this
case, the inductor must carry the entire 1A switch current.
Table 1. Recommended Inductors—LT1931
L Size
PART (µH) (L × W × H) mm VENDOR
CLS62-100 10 6.8 × 6.6 × 2.5 Sumida
CR43-150 15 4.5 × 4.0 × 3.2 (847) 956-0666
CR43-220 22 www.sumida.com
CTX10-1 10 8.9 × 11.4 × 4.2 Coiltronics
CTX15-1 15 (407) 241-7876
www. coiltronics.com
LQH3C100K24 10 3.2 × 2.5 × 2.0 Murata
LQH4C150K04 15 (404) 436-1300
www.murata.com
Table 2. Recommended Inductors—LT1931A
L Size
PART (µH) (L × W × H) mm VENDOR
ELJPC3R3MF 3.3 2.5 × 2.0 × 1.6 Panasonic
ELJPC4R7MF 4.7 (408) 945-5660
www.panasonic.com
CLQ4D10-4R7
1
4.7 7.6 × 4.8 × 1.8 Sumida
CLQ4D10-6R8
2
6.8 (847) 956-0666
www.sumida.com
LB20164R7M 4.7 2.0 × 1.6 × 1.6 Taiyo Yuden
LB20163R3M 3.3 (408) 573-4150
www.t-yuden.com
LQH3C4R7K24 4.7 3.2 × 2.5 × 2.0 Murata
LQH4C100K24 10 (404) 436-1300
www.murata.com
1
Use drawing #5382-T039
2
Use drawing #5382-T041
6
LT1931/LT1931A
1931fa
APPLICATIO S I FOR ATIO
WUUU
The inductors shown in Table 2 for use with the LT1931A
were chosen for their small size. For better efficiency, use
similar valued inductors with a larger volume. For in-
stance, the Sumida CR43 series, in values ranging from
3.3µH to 10µH, will give a LT1931A application a few
percentage points increase in efficiency.
CAPACITOR SELECTION
Low ESR (equivalent series resistance) capacitors should
be used at the output to minimize the output ripple voltage.
Multilayer ceramic capacitors are an excellent choice, as
they have an extremely low ESR and are available in very
small packages. X5R dielectrics are preferred, followed by
X7R, as these materials retain their capacitance over wide
voltage and temperature ranges. A 10µF to 22µF output
capacitor is sufficient for most LT1931 applications while
a 4.7µF to 10µF capacitor will suffice for the LT1931A.
Solid tantalum or OS-CON capacitors can be used, but
they will occupy more board area than a ceramic and will
have a higher ESR. Always use a capacitor with a sufficient
voltage rating.
Ceramic capacitors also make a good choice for the input
decoupling capacitor, which should be placed as close as
possible to the LT1931/LT1931A. A 1µF to 4.7µF input
capacitor is sufficient for most applications. Table 3 shows
a list of several ceramic capacitor manufacturers. Consult
the manufacturers for detailed information on their entire
selection of ceramic parts.
Table 3. Ceramic Capacitor Manufacturers
Taiyo Yuden (408) 573-4150
www.t-yuden.com
AVX (803) 448-9411
www.avxcorp.com
Murata (714) 852-2001
www.murata.com
The decision to use either low ESR (ceramic) capacitors or
the higher ESR (tantalum or OS-CON) capacitors can
effect the stability of the overall system. The ESR of any
capacitor, along with the capacitance itself, contributes a
zero to the system. For the tantalum and OS-CON capaci-
tors, this zero is located at a lower frequency due to the
higher value of the ESR, while the zero of a ceramic
capacitor is at a much higher frequency and can generally
be ignored.
A phase lead zero can be intentionally introduced by
placing a capacitor (C4) in parallel with the resistor (R1)
between V
OUT
and V
NFB
as shown in Figure 1. The
frequency of the zero is determined by the following
equation.
ƒ=π
ZRC
1
214••
By choosing the appropriate values for the resistor and
capacitor, the zero frequency can be designed to improve
the phase margin of the overall converter. The typical
target value for the zero frequency is between 20kHz to
60kHz. Figure 3 shows the transient response of the
inverting converter from Figure 1 without the phase lead
capacitor C4. The phase margin is reduced as evidenced
by more ringing in both the output voltage and inductor
current. A 220pF capacitor for C4 results in better phase
margin, which is revealed in Figure 4 as a more damped
response and less overshoot. Figure 5 shows the transient
response when a 22µF tantalum capacitor with no phase
lead capacitor is used on the output. The higher output
voltage ripple is revealed in the upper waveform as a
thicker line. The transient response is adequate which
implies that the ESR zero is improving the phase margin.
V
OUT
20mV/DIV
AC COUPLED
I
L1A
+ I
L1B
0.5A/DIV
AC COUPLED
200mA
100mA
LOAD
CURRENT
100µs/DIV 1931 F03
Figure 3. Transient Response of Inverting Converter
Without Phase Lead Capacitor
7
LT1931/LT1931A
1931fa
START-UP/SOFT-START
For most LT1931/LT1931A applications, the start-up in-
rush current can be high. This is an inherent feature of
switching regulators in general since the feedback loop is
saturated due to V
OUT
being far from its final value. The
APPLICATIO S I FOR ATIO
WUUU
regulator tries to charge up the output capacitor as quickly
as possible, which results in a large inrush current. Fig-
ure 6 shows a typical oscillograph of the start-up wave-
form for the application of Figure 1 starting into a load of
33Ω. The lower waveform shows SHDN being pulsed
from 0V to 5V. The middle waveform shows the input
current, which reaches as high as 0.8A. The total time
required for the output to reach its final value is approxi-
mately 500µs. For some applications, this initial inrush
current may not be acceptable. If a longer start-up time is
acceptable, a soft-start circuit consisting of R
SS
and C
SS
,
as shown in Figure 7, can be used to limit inrush current
to a lower value. Figure 8 shows the relevant waveforms
with R
SS
= 15k and C
SS
= 33nF. Input current, measured
at V
IN
, is limited to a peak value of 0.5A as the time required
to reach final value increases to 1ms. In Figure 9, C
SS
is
V
OUT
20mV/DIV
AC COUPLED
I
L1A
+ I
L1B
0.5A/DIV
AC COUPLED
200mA
100mA
LOAD
CURRENT
100µs/DIV 1931 F04
Figure 4. Transient Response of Inverting Converter
with 220pF Phase Lead Capacitor
V
OUT
0.1V/DIV
AC COUPLED
I
L1A
+ I
L1B
0.5A/DIV
AC COUPLED
200mA
100mA
LOAD
CURRENT
50µs/DIV 1931 F05
Figure 5. Transient Response of Inverting Converter with 22µF
Tantalum Output Capacitor and No Phase Lead Capacitor
VIN
VIN
5V
VSS
VOUT
VOUT
–5V
1931 F07
SW
L1A
10µH
CURRENT
PROBE L1B
10µH
D1
GND
LT1931
C1
4.7µF
RSS
15k
D2
1N4148
C3
22µF
C2
1µF
R2
10k
R1
29.4k
C4
220pF
NFB
SHDN
+
CSS
33nF/68nF C1: TAIYO YUDEN X5R JMK212BJ475MG
C2: TAIYO YUDEN X5R LMK212BJ105MG
C3: TAIYO YUDEN XR5 JMK325BJ226MM
D1: ON SEMICONDUCTOR MBR0520
L1: SUMIDA CLS62-100
Figure 7. RSS and CSS at SHDN Pin Provide Soft-Start to LT1931 Inverting Converter
V
OUT
2V/DIV
I
IN
0.5A/DIV
AC COUPLED
5V
0V
V
SHDN
500µs/DIV 1931 F06
Figure 6. Start-Up Waveforms for 5V to –5V Application
(Figure 1). No Soft-Start Circuit. VOUT Reaches –5V in
500µs; Input Current Peaks at 800mA
8
LT1931/LT1931A
1931fa
increased to 68nF, resulting in a lower peak input current
of 350mA with a V
OUT
ramp time of 1.6ms. C
SS
or R
SS
can
be increased further for an even slower ramp, if desired.
Diode D2 serves to quickly discharge C
SS
when V
SS
is
driven low to shut down the device. D2 can be omitted,
resulting in a “soft-stop” slow discharge of the output
capacitor.
1
2
3
5
4
C2
D1
R2
R1
L1B
C1
L1A
+
+
SHUTDOWN
1931 F10
–V
OUT
GND
V
IN
C3
V
OUT
2V/DIV
I
IN
0.5A/DIV
AC COUPLED
5V
0V
V
SS
200µs/DIV 1931 F08
Figure 8. RSS = 15k, CSS = 33nF; VOUT Reaches –5V in 1ms;
Input Current Peaks at 500mA
V
OUT
2V/DIV
I
IN
0.5A/DIV
AC COUPLED
5V
0V
V
SS
500µs/DIV 1931 F09
Figure 9. RSS = 15k, CSS = 68nF; VOUT Reaches –5V in 1.6ms;
Input Current Peaks at 350mA
Figure 10. Suggested Component Placement.
Note Cut in Ground Copper at D1’s Cathode
APPLICATIO S I FOR ATIO
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DIODE SELECTION
A Schottky diode is recommended for use with the LT1931/
LT1931A. The Motorola MBR0520 is a very good choice.
Where the input to output voltage differential exceeds 20V,
use the MBR0530 (a 30V diode). These diodes are rated to
handle an average forward current of 0.5 A. In applications
where the average forward current of the diode exceeds
0.5A, a Microsemi UPS5817 rated at 1A is recommended.
LAYOUT HINTS
The high-speed operation of the LT1931/LT1931A de-
mands careful attention to board layout. You will not get
advertised performance with careless layout. Figure 10
shows the recommended component placement. The
ground cut at the cathode of D1 is essential for low noise
operation.
9
LT1931/LT1931A
1931fa
TYPICAL APPLICATIO S
U
V
IN
V
IN
5V
V
OUT
–12V
150mA
1931 TA02
SW
L1A
10µH
L1B
10µH
D1
GND
LT1931
C1: TAIYO YUDEN X5R JMK212BJ475MG
C2: TAIYO YUDEN X5R TMK316BJ105ML
C3: TAIYO YUDEN X5R EMK325BJ106MM
D1: ON SEMICONDUCTOR MBR0520
L1: SUMIDA CLS62-100
C1
4.7µFC3
10µF
C2
1µF
R2
10k
R1
84.5k
NFB
SHDN
5V to –12V Inverting Converter
LOAD CURRENT (mA)
0
50
EFFICIENCY (%)
60
70
80
25 50 75 100
1931 TA03
125
90
100
55
65
75
85
95
150
Efficiency
V
IN
V
IN
5V
V
OUT
–5V
300mA
1931 TA04
SW
L1
10µH
L2
10µH
D1
GND
LT1931
C1: TAIYO YUDEN X5R JMK212BJ475MG
C2: TAIYO YUDEN X5R LMK212BJ105MG
C3: TAIYO YUDEN X5R JMK212BJ226MM
D1: ON SEMICONDUCTOR MBR0520
L1, L2: MURATA LQH3C100K04
C1
4.7µFC3
22µF
C2
1µF
R2
10k
R1
29.4k 220pF
NFB
SHDN
5V to –5V Inverting Converter Using Uncoupled Inductors
V
IN
V
IN
5V
V
OUT
–5V
300mA
1931 TA05a
SW
L1
4.7µH
L2
4.7µH
D1
GND
LT1931A
C1: TAIYO YUDEN X5R JMK212BJ475MG
C2: TAIYO YUDEN X5R LMK212BJ105MG
C3: TAIYO YUDEN X5R JMK212BJ475MG
D1: ON SEMICONDUCTOR MBR0520
L1, L2: MURATA LQH3C4R7M24
C1
4.7µFC3
4.7µF
C2
1µF
R2
10k
R1
28.7k C4
180pF
NFB
SHDN
LOAD CURRENT (mA)
0
50
EFFICIENCY (%)
55
65
70
75
100 200 250
1931 TA05b
60
80
50 150 300 350
2.2MHz, 5V to –5V Inverting Converter Efficiency
10
LT1931/LT1931A
1931fa
TYPICAL APPLICATIO S
U
V
IN
V
IN
5V
V
OUT
–5V
200mA
1931 TA06a
SW
L1
3.3µH
L2
3.3µH
D1
GND
LT1931A
C1: TAIYO YUDEN X5R JMK212BJ225MG
C2: TAIYO YUDEN X5R LMK212BJ105MG
C3: TAIYO YUDEN X5R JMK212BJ475MG
D1: ON SEMICONDUCTOR MBR0520
L1, L2: PANASONIC ELJPC3R3MF
C1
2.2µFC3
4.7µF
C2
1µF
R2
10k
R1
28.7k C4
68pF
NFB
SHDN
LOAD CURRENT (mA)
0
50
EFFICIENCY (%)
55
60
65
70
75
80
50 100 150 200
1931 TA06b
250
2.2MHz, 5V to –5V Converter Uses Tiny Chip Inductors Efficiency
VIN
VIN
12V
VSS
SW
L1
22µH
GND
R2
1k
LT1931
NFB
SHDN
RSS
15k
R3
25.5k
R1
1Ω
R4
2.7k
C6
1000pF
CSS
68nF
C1
4.7µF
16V
C3
1µF
35V
*TOTAL OUTPUT POWER NOT TO EXCEED 3.3W
C1 TO C5: X5R OR X7R
D1, D2: BAV99 OR EQUIVALENT
L1: SUMIDA CR43-220
C5
4.7µF
35V
32
D2
1
1931 TA08
C4
4.7µF
35V VOUT1
–33V
100mA*
COM
VOUT2
–66V
48mA*
C2
1µF
35V
32
D1
1
SLIC Power Supply with –33V and – 68V Outputs, Uses Soft-Start
11
LT1931/LT1931A
1931fa
U
PACKAGE DESCRIPTIO
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
SLIC Power Supply with –21.6V and – 65V Outputs, Uses Soft-Start
TYPICAL APPLICATIO S
U
V
IN
V
IN
5V
V
SS
SW
L1
10µH
GND
R2
1k
LT1931
NFB
SHDN
R
SS
15k
R3
16.2k
R1
1Ω
R4
2.7k
C8
1000pF
C1
4.7µF
16V
C
SS
68nF
C3
1µF
35V
C4
1µF
35V
*TOTAL OUTPUT POWER NOT TO EXCEED 1.3W
C1 TO C7: X5R OR X7R
D1, D2: BAV99 OR EQUIVALENT
L1: SUMIDA CR43-100
C7
4.7µF
25V
32
D3
C6
4.7µF
25V
32
1
D2
1
1931 TA09
C5
4.7µF
25V V
OUT1
–21.6V
48mA*
COM
V
OUT2
–65V
20mA*
C2
1µF
35V
32
D1
1
1.50 – 1.75
(NOTE 4)
2.80 BSC
0.30 – 0.45 TYP
5 PLCS (NOTE 3)
DATUM ‘A’
0.09 – 0.20
(NOTE 3)
S5 TSOT-23 0302 REV B
PIN ONE
2.90 BSC
(NOTE 4)
0.95 BSC
1.90 BSC
0.80 – 0.90
1.00 MAX 0.01 – 0.10
0.20 BSC
0.30 – 0.50 REF
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
3.85 MAX
0.62
MAX
0.95
REF
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
1.4 MIN
2.62 REF
1.22 REF
S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
12
LT1931/LT1931A
1931fa
LT/LT 1005 REV A • PRINTED IN USA
© LINEAR TECHNOLOGY CORPORATION 2000
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900
●
FAX: (408) 434-0507
●
www.linear-tech.com
RELATED PARTS
PART NUMBER DESCRIPTION COMMENTS
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LT1317 2-Cell Micropower DC/DC with Low-Battery Detector 3.3V at 200mA from Two Cells, 600kHz Fixed Frequency
LT1610 Single Cell Micropower DC/DC Converter 3V at 30mA from 1V, 1.7MHz Fixed Frequency
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LT1615 Micropower Constant Off-Time DC/DC Converter in 5-Lead ThinSOT 20V at 12mA from 2.5V. Tiny SOT-23 Package
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Burst Mode operation is a trademark of Linear Technology Corporation.
TYPICAL APPLICATIO
U
2.2MHz, 12V to –5V Converter Uses Low Profile Coupled Inductor
Efficiency
V
IN
V
IN
12V
V
OUT
–5V
450mA
1931 TA07a
SW
L1A
4.7µH
L1B
4.7µH
D1
GND
LT1931A
C1: TAIYO YUDEN Y5V EMK212F225ZG
C2: 0.1µF 25V X5R
C3: TAIYO YUDEN X5R JMK212BJ475MG
D1: ON SEMICONDUCTOR MBR0520
L1: SUMIDA CLQ4D10-4R7 DRAWING #5382-T039
C1
2.2µFC3
4.7µF
C2
0.1µF
R2
10k
R1
28.7k
NFB
SHDN
LOAD CURRENT (mA)
0
50
EFFICIENCY (%)
55
60
65
70
75
80
100 200 300 400
1931 TA07b
500
