IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
Power Factor Controllers
The are active power factor controllers specifically designed for use as a preconverter in
electronic ballast and in off-line power converter applications. These integrated circuits feature an
internal startup timer for stand-alone applications, a one quadrant multiplier for near unity power
factor, zero current detector to ensure critical conduction operation, transconductance error
amplifier, quickstart circuit for enhanced startup, trimmed internal bandgap reference, current
sensing comparator, and a totem pole output ideally suited for driving a power MOSFET.
Also included are protective features consisting of an overvoltage comparator to eliminate
runaway output voltage due to load removal, input undervoltage lockout with hysteresis, cycle-by-
cycle current limiting, multiplier output clamp that limits maximum peak switch current, an RS latch
for single pulse metering, and a drive output high state clamp for MOSFET gate protection. These
devices are available in dual-in-line and surface mount plastic packages.
Features
• Overvoltage Comparator Eliminates Runaway Output
Voltage
• Internal Startup Timer
• One Quadrant Multiplier
• Zero Current Detector
• Trimmed 2% Internal Bandgap Reference
• Totem Pole Output with High State Clamp
• Undervoltage Lockout with 6.0 V of Hysteresis
• Low Startup and Operating Current
• Supersedes Functionality of SG3561 andTDA4817
8
1
Figure 1. Package and pin connection
Figure 2. Simplified Block Diagram
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
MAXIMUM RATINGS
Rating Symbol Value Unit
Total Power Supply and Zener Current (Icc + Iz) 30 mA
Output Current, Source or Sink lo 500 mA
Current Sense, Multiplier, and Voltage Feedback Inputs Vin -1.0 to +10 V
Zero Current Detect Input
High State Forward Current Low
State Reverse Current hn 50
-10 mA
Power Dissipation and Thermal Characteristics
P Suffix, Plastic Package, Case 626
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance, Junction-to-Air
D Suffix, Plastic Package, Case 751
Maximum Power Dissipation @ TA = 70°C
Thermal Resistance, Junction-to-Air
PD
RθJA
PD
RθJA
800
100
450
178
mW
°C/W
mW
0C/W
Operating Junction Temperature TJ +150 °C
Operating Ambient Temperature TA 0 to + 85
°C
Storage Temperature Tstg -65 to +150 °C
ELECTRICAL CHARACTERISTICS (\/cc =12 V, for typical values TA = 25°C, for min/max values TA is the operating
ambient temperature range that applies unless otherwise noted.)
Test list
Position #
Symbol Min Typ Max Unit
ERROR AMPLIFIER
Voltage Feedback Input Threshold
TA=25°C
TA = Tlow to Thigh (Vcc = 12 V to 28 V)
2
3
VFB
2.465
2.44
2.5
—
2.535
2.54
V
Line Regulation (VCC = 12 V to 28 V, TA = 25°C)
35 Regline — 1.0 10 mV
Input Bias Current (VFB = 0 V) 4 IIB — -0.1 -0.5 µA
Transconductance (TA = 25°C) 36 gm 80 100 130 µmho
Output Current
Source (VFB = 2.3 V)
Sink (VFB = 2.7 V)
25
26
lo
—
—
10
10
—
—
µA
Output Voltage Swing
High State (VFB = 2.3 V)
Low State (VFB = 2.7 V)
7
8
VOH(ea)
VOL(ea)
5.8
—
6.4
1.7
—
2.4
V
OVERVOLTAGE COMPARATOR
Voltage Feedback Input Threshold 9 VFB(OV) 1.065VFB 1.08VFB 1.095VFB
V
MULTIPLIER
Input Bias Current, Pin 3 (VFB = 0 V) 5 IIB — -0.1 -0.5 µA
Input Threshold, Pin 2 14 Vth(M) 1.05VOL(EA) 1.2VOL(EA)
— V
Dynamic Input Voltage Range
Multiplier Input (Pin 3)
Compensation (Pin 2)
33
34
Vpin3
Vpin2
0 to 2.5
Vth(M) to
(Vth(M)+1.0)
0 to 3.5
Vth(M) to
(Vth(M)+ 1.5)
—
—
V
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
Multiplier Gain (Vpin 3 = 0.5 V, Vpin 2 = Vth(M) +
1.0 V) (Note 4) 15 K 0.43 0.65 0.87 1/V
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
ELECTRICAL CHARACTERISTICS
Test list
Position #
Symbol Min Typ Max Unit
ZERO CURRENT DETECTOR
Input Threshold Voltage (Vjn Increasing) 10 Vth 1.33 1.6 1.87 V
Hysteresis (Vin Decreasing) 11 VH 100 200 300 mV
Input Clamp Voltage
High State (IDET = + 3.0 mA)
High State (IDET = - 3.0 mA)
16
17
VIH
VIL
6.1
0.3
6.7
0.7
—
1.0
V
CURRENT SENSE COMPARATOR
Input Bias Current (Vpin 4 = 0 V) 6 IIB — -0.15 -1.0 ?A
Input Offset Voltage (Vpm 2 = 1.1 V, Vpm 3 = 0
V) 12 VIO — 9.0 25 mV
Maximum Current Sense Input Threshold (Note
5) 13 Vth(max) 1.3 1.5 1.8 V
Delay to Output 38 tPHL(in/out) — 200 400 ns
DRIVE OUTPUT
Output Voltage (VCC = 12 V)
Low State (Isink = 20 mA)
(Isink = 200 mA)
High State (Isource = 20 mA)
(Isource = 200 mA)
27
28
29
30
VOL
VOH
—
—
9.8
7.8
0.3
2.4
10.3
8.4
—
—
0.8
3.3
V
Output Voltage (VCC = 30 V)
High State (Isource = 20 mA, CL = 15 pF) 31 VO(max) 14 16 18 V
Output Voltage Rise Time (CL 1.0 nF) 41 tr — 50 120 ns
Output Voltage Fall Time (CL 1.0 nF) 39 tf — 50 120 ns
Output Voltage with UVLO Activated
(Vcc = 7.0 V,lSink= 1.0mA) 32 VO(UVLO) — 0.1 0.5 V
RESTART TIMER
Restart Time Delay 40 tDLY 200 620 — µs
UNDERVOLTAGE LOCKOUT
Startup Threshold (VCC Increasing) 19 Vth(on) 11.5 13 14.5 V
Minimum Operating Voltage After Turn-On (VCC
Decreasing) 20 VShutdown 7.0 8.0 9.0 V
Hysteresis 21 VH 3.8 5.0 6.2 V
TOTAL DEVICE
Power Supply Current
Startup (Vcc = 7.0 V)
Operating Dynamic Operating (50 kHz, CL = 1.0
nF)
22
23
37
ICC
—
0.25
6.5
9.0
0.4
12
20
mA
Power Supply Zener Voltage (Ice = 25 mA) 24 VZ 30 36 — V
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
Figure 3. Current Sense Input Threshold versus Multiplier
Input. Figure 4. Current Sense Input Threshold versus
Multiplier Input, Expanded View
Figure 5. Voltage Feedback Input Threshold Change versus
Temperature. Figure 4. Overvoltage Comparator Input Threshold
versus Temperature.
Figure 7. Error Amp Transconductance and Phase versus
Frequency Figure 8. Quickstart Charge Current versus
Temperature
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
Figure 9. Restart Timer Delay versus Temperature
.
Figure 10. Zero Current Detector Input Threshold Voltage
versus Temperature
.
Figure 11. Output Saturation Voltage versus Load Current Figure 12. Supply Current versus Supply Voltage
Figure 13. Undervoltage Lockout Thresholds versus Temperature
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
APPLICATIONS INFORMATION
The application circuits shown in Figures 14, 15 and 16 reveal that few external components are required for a
complete power factor preconverter. Each circuit is a peak detecting current–mode boost converter that operates in
critical conduction mode with a fixed on–time and variable off–time. A major benefit of critical conduction operation is
that the current loop is inherently stable, thus eliminating the need for ramp compensation. The application in Figure
14 operates over an input voltage range of 90 Vac to 138 Vac and provides an output power of 80 W (230 V at 350 mA)
with an associated power factor of approximately 0.998 at
nominal line. Figures 15 and 16 are universal input preconverter examples that operate over a continuous input
voltage range of 90 Vac to 268 Vac. Figure 15 provides an output power of 175 W (400 V at 440 mA) while Figure 16
provides 450 W (400 V at 1.125 A). Both circuits have an observed worst–case power factor of approximately 0.989.
Table 3. Design Equations
Notes Calculation Formula
Calculate the maximum required output power. Required Converter Output
Power P O = V O I O
Calculated at the minimum required ac line voltage
for output regulation. Let the efficiency ? = 0.92 for
low line operation.
Peak Inductor Current
(LL)
O
L(pk) çVacP22
I=
Let the switching cycle t = 40 ?s for universal
input
(85 to 265 Vac) operation and 20 ?s for fixed input
(92 to 138 Vac, or 184 to 276 Vac) operation.
Inductance
VoPo2
Vac
çVac-
2
Vo
t
Lp (LL)
2
(LL)
=
In theory the on–time ton is constant. In practice ton
tends to increase at the ac line zero crossings due
to the charge on capacitor C5. Let Vac = Vac(LL)
for initial ton and toff calculations.
Switch On–Time
Vac
ç
2PoLp
t2
on =
The off–time toff is greatest at the peak of the ac
line
voltage and approaches zero at the ac line zero
crossings. Theta (?) represents the angle of the
ac line voltage.
Switch Off–Time
1-
|èSin | Vac 2
Vo
t
ton
off =
The minimum switching frequency occurs at the
peak of the ac line voltage. As the ac line voltage
traverses from peak to zero, toff approaches zero
producing an increase in switching frequency.
Switching Frequency
offon tt 1
f+
=
Set the current sense threshold VCS to 1.0 V for
universal input (85 Vac to 265 Vac) operation
and to 0.5 V for fixed input (92 Vac to 138 Vac, or
184 Vac to 276 Vac) operation. Note that VCS
must be <1.4 V.
Peak Switch Current
L(pk)IVcs
R7 =
Set the multiplier input voltage VM to 3.0 V at High
line. Empirically adjust VM for the lowest distortion
over the ac line voltage range while guaranteeing
startup at minimum line.
Multiplier Input Voltage
+
=1
R3
R5 2Vac
VM
The IIB R1 error term can be minimized with a divider
current in excess of 50 ?A.
Converter Output Voltage R1I1
R1
R2
VrefVo IB−
+=
The calculated peak–to–peak ripple must be less
than 16% of the average dc output voltage to
prevent false tripping of the Overvoltage
Comparator. Refer to the Overvoltage Comparator
text. ESR is the equivalent series resistance of C3
Converter Output
Peak to Peak
Ripple Voltage
(
)
ESR2
C3 fac 2ð 12
IoÄVo P)(P +=−
The bandwidth is typically set to 20 Hz. When
operating
at high ac line, the value of C1 may need to be
increased. (See Figure 17)
Error Amplifier Bandwidth
C1 ð2gm
BW =
The following converter characteristics must be chosen:
VO — Desired output voltage Vac — AC RMS line voltage
IO — Desired output current Vac(LL) — AC RMS low line voltage
?V
O — Converter output peak–to–peak ripple voltage
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
IL34262
Figure 14. 80 W Power Factor Controller
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
IL34262
Figure 15. 175 W Universal Input Power Factor Controller
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
IL34262
Figure 16. 450 W Universal Input Power Factor Controller
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
Figure 17. Error Amp Compensation
The Error Amp output is a high impedance node and is susceptible to noise pickup. To minimize pickup, compensation
capacitor C
1 must be connected as close to Pin 2 as possible with a short, heavy ground returning directly to Pin 6. When
operating at high ac line, the voltage at Pin 2 may approach the lower threshold of the Multiplier, ??2.0 V. If there is excessive
ripple on Pin 2, the Multiplier will be driven into cut–off causing circuit instability, high distortion and poor power factor. This
problem can be eliminated by increasing the value of C1.
.
Figure 18. Current Waveform Spike Suppression Figure 19. Negative Current Waveform Spike
Suppression
A narrow turn–on spike is usually present on the leading edge of
the current waveform and can cause circuit instability. The
IL34262 provides an internal RC filter with a time constant of 220
ns. An additional external RC filter may be required in universal
input applications that are above 200 W. It is suggested that the
external filter be placed directly at the Current Sense Input and
have a time constant that approximates the spike duration.
A negative turn–off spike can be observed on the trailing
edge of the current waveform. This spike is due to the
parasitic inductance of resistor R
7, and if it is excessive, it
can cause circuit instability. The addition of Shottky diode D1
can effectively clamp the negative spike. The addition of the
external RC filter shown in Figure 18 may provide sufficient
spike attenuation.
IL34262
Korzhenevsky 12, Minsk, 220064, Republic of Belarus
Fax: +375 (17) 278 28 22,
Phone: +375 (17) 278 07 11, 277 24 70, 277 24 61,
277 69 16
E-mail: belms@belms.belpak.minsk.by
URL: www.bms.by
Figure 20. Bonding diagram of Il34262
Chip size 2,1x2,1mm2
Chip holder size 2,9x2,9mm2
Chip contact pads 04, 12, 13, 14, 15 are not to be wired.
