Precision CMOS Single-Supply Rail-to-Rail Input/Output Wideband Operational Amplifiers AD8601/AD8602/AD8604 FEATURES Low Offset Voltage: 500 V Max Single-Supply Operation: 2.7 V to 5.5 V Low Supply Current: 750 A/Amplifier Wide Bandwidth: 8 MHz Slew Rate: 5 V/s Low Distortion No Phase Reversal Low Input Currents Unity Gain Stable APPLICATIONS Current Sensing Barcode Scanners PA Controls Battery-Powered Instrumentation Multipole Filters Sensors ASIC Input or Output Amplifiers Audio GENERAL DESCRIPTION The AD8601, AD8602, and AD8604 are single, dual, and quad rail-to-rail input and output single-supply amplifiers featuring very low offset voltage and wide signal bandwidth. These amplifiers use a new, patented trimming technique that achieves superior performance without laser trimming. All are fully specified to operate on a 3 V to 5 V single supply. The combination of low offsets, very low input bias currents, and high speed make these amplifiers useful in a wide variety of applications. Filters, integrators, diode amplifiers, shunt current sensors, and high impedance sensors all benefit from the combination of performance features. Audio and other ac applications benefit from the wide bandwidth and low distortion. For the most cost-sensitive applications, the D grades offer this ac performance with lower dc precision at a lower price point. Applications for these amplifiers include audio amplification for portable devices, portable phone headsets, bar code scanners, portable instruments, cellular PA controls, and multipole filters. The ability to swing rail-to-rail at both the input and output enables designers to buffer CMOS ADCs, DACs, ASICs, and other wide output swing devices in single-supply systems. FUNCTIONAL BLOCK DIAGRAM 14-Lead TSSOP (RU Suffix) OUT A 1 5-Lead SOT-23 (RT Suffix) 14 OUT D OUT A 1 2 13 IN D V 2 IN A 3 12 IN D IN A V 4 AD8604 11 V IN B 5 10 IN C IN B 6 9 IN C OUT B 7 8 OUT C 14-Lead SOIC (R Suffix) OUT A 1 14 OUT D IN A 2 13 IN D IN A 3 V 4 5 V AD8601 IN 3 4 IN 8-Lead MSOP (RM Suffix) OUT A 1 8 V 7 OUT B IN A 3 6 IN B V 4 5 IN B IN A 2 AD8602 12 IN D AD8604 11 V IN B 5 10 IN C IN B 6 9 IN C OUT B 7 8 OUT C 8-Lead SOIC (R Suffix) OUT A 1 IN A 2 IN A 3 V 4 8 V AD8602 7 OUT B 6 IN B 5 IN B The AD8601, AD8602, and AD8604 are specified over the extended industrial (-40C to +125C) temperature range. The AD8601, single, is available in the tiny 5-lead SOT-23 package. The AD8602, dual, is available in 8-lead MSOP and narrow SOIC surface-mount packages. The AD8604, quad, is available in 14-lead TSSOP and narrow SOIC packages. SOT, MSOP, and TSSOP versions are available in tape and reel only. REV. D Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 www.analog.com Fax: 781/326-8703 (c) 2003 Analog Devices, Inc. All rights reserved. AD8601/AD8602/AD8604-SPECIFICATIONS ELECTRICAL CHARACTERISTICS Parameter Symbol INPUT CHARACTERISTICS Offset Voltage (AD8601/AD8602) VOS Offset Voltage (AD8604) Input Bias Current Input Offset Current VOS IB IOS Input Voltage Range Common-Mode Rejection Ratio Large Signal Voltage Gain CMRR AVO Offset Voltage Drift VOS/T OUTPUT CHARACTERISTICS Output Voltage High VOH Output Voltage Low VOL Output Current Closed-Loop Output Impedance IOUT ZOUT (VS = 3 V, VCM = VS/2, TA = 25C, unless otherwise noted.) Conditions Min 0 V VCM 1.3 V -40C TA +85C -40C TA +125C 0 V VCM 3 V* -40C TA +85C -40C TA +125C VCM = 0 V to 1.3 V -40C TA +85C -40C TA +125C VCM = 0 V to 3.0 V* -40C TA +85C -40C TA +125C A Grade Typ Max 80 350 80 350 0.2 25 150 0.1 -40C TA +85C -40C TA +125C -40C TA +85C -40C TA +125C VCM = 0 V to 3 V VO = 0.5 V to 2.5 V, RL = 2 k , VCM = 0 V IL = 1.0 mA -40C TA +125C IL = 1.0 mA -40C TA +125C 0 68 500 700 1,100 750 1,800 2,100 600 800 1,600 800 2,200 2,400 60 100 1,000 30 50 500 3 83 Min D Grade Typ Max 65 V V V V V V V V V V V V pA pA pA pA pA pA V dB 1,100 1,300 1,100 1,300 0.2 25 150 0.1 0 52 Unit 6,000 7,000 7,000 6,000 7,000 7,000 6,000 7,000 7,000 6,000 7,000 7,000 200 200 1,000 100 100 500 3 30 100 2 20 60 2 V/mV V/C 2.92 2.88 2.95 2.92 2.88 2.95 V V mV mV mA 20 35 50 20 30 12 f = 1 MHz, AV = 1 30 12 35 50 POWER SUPPLY Power Supply Rejection Ratio Supply Current/Amplifier PSRR ISY VS = 2.7 V to 5.5 V VO = 0 V -40C TA +125C DYNAMIC PERFORMANCE Slew Rate Settling Time Gain Bandwidth Product Phase Margin SR tS GBP o RL = 2 k To 0.01% 5.2 <0.5 8.2 50 5.2 <0.5 8.2 50 V/s s MHz Degrees en en in f = 1 kHz f = 10 kHz 33 18 0.05 33 18 0.05 nV/Hz nV/Hz pA/Hz NOISE PERFORMANCE Voltage Noise Density Current Noise Density 67 80 680 56 1,000 1,300 72 680 dB 1,000 A 1,300 A *For VCM between 1.3 V and 1.8 V, V OS may exceed specified value. Specifications subject to change without notice. -2- REV. D AD8601/AD8602/AD8604 ELECTRICAL CHARACTERISTICS Parameter Symbol INPUT CHARACTERISTICS Offset Voltage (AD8601/AD8602) VOS Offset Voltage (AD8604) VOS Input Bias Current IB Input Offset Current IOS Input Voltage Range Common-Mode Rejection Ratio Large Signal Voltage Gain CMRR AVO Offset Voltage Drift VOS/T OUTPUT CHARACTERISTICS Output Voltage High VOH (VS = 5.0 V, VCM = VS/2, TA = 25C, unless otherwise noted.) Conditions Min 0 V VCM 5 V -40C TA +125C VCM = 0 V to 5 V -40C TA +125C VCM = 0 V to 5 V VO = 0.5 V to 4.5 V, RL = 2 k, VCM = 0 V IL = 1.0 mA IL = 10 mA -40C TA +125C IL = 1.0 mA IL = 10 mA -40C TA +125C f = 1 MHz, AV = 1 PSRR ISY VS = 2.7 V to 5.5 V VO = 0 V NOISE PERFORMANCE Voltage Noise Density Current Noise Density 89 80 4.925 4.7 4.6 4.975 4.77 15 125 67 80 750 RL = 2 k To 0.01% < 1% Distortion o 67 60 2 V/C 4.975 4.77 50 10 V V V mV mV mV mA 72 750 dB 1,200 A 0.2 0.1 6 25 0 56 20 30 175 250 15 125 56 6,000 7,000 6,000 7,000 200 200 1,000 100 100 500 5 30 175 250 1,500 A 1,500 6 <1.0 360 8.4 6 <1.0 360 8.4 V/s s kHz MHz 55 55 Degrees nV/Hz nV/Hz pA/Hz en en f = 1 kHz f = 10 kHz 33 18 33 18 in f = 1 kHz 0.05 0.05 -3- Unit V V V V pA pA pA pA pA pA V dB V/mV 1,300 4.925 4.7 4.6 1,200 D Grade Typ Max 1,300 50 10 -40C TA +125C Specifications subject to change without notice. REV. D 0 74 30 500 1,300 600 1,700 60 100 1,000 30 50 500 5 Min 2 IOUT ZOUT Phase Margin 0.1 6 25 -40C TA +85C -40C TA +125C Output Current Closed-Loop Output Impedance SR tS BWp GBP 80 0.2 VOL DYNAMIC PERFORMANCE Slew Rate Settling Time Full Power Bandwidth Gain Bandwidth Product 80 -40C TA +85C -40C TA +125C Output Voltage Low POWER SUPPLY Power Supply Rejection Ratio Supply Current/Amplifier A Grade Typ Max AD8601/AD8602/AD8604 ABSOLUTE MAXIMUM RATINGS* Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to VS Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . 6 V Storage Temperature Range R, RM, RT, RU Packages . . . . . . . . . . . . -65C to +150C Operating Temperature Range AD8601/AD8602/AD8604 . . . . . . . . . . . . -40C to +125C Junction Temperature Range R, RM, RT, RU Packages . . . . . . . . . . . . -65C to +150C Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300C ESD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 kV HBM Package Type JA* JC Unit 5-Lead SOT-23 (RT) 8-Lead SOIC (R) 8-Lead MSOP (RM) 14-Lead SOIC (R) 14-Lead TSSOP (RU) 230 158 210 120 180 92 43 45 36 35 C/W C/W C/W C/W C/W *JA is specified for worst-case conditions, i.e., JA is specified for device in socket for PDIP packages; JA is specified for device soldered onto a circuit board for surface-mount packages. *Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those listed in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. ORDERING GUIDE Model Temperature Range Package Description Package Option AD8601ART-R2 AD8601ART-REEL AD8601ART-REEL7 AD8601DRT-R2 AD8601DRT-REEL AD8601DRT-REEL7 AD8602AR AD8602AR-REEL7 AD8602AR-R2 AD8602DR AD8602DR-REEL AD8602DR-REEL7 AD8602ARM-R2 AD8602ARM-REEL AD8602DRM-REEL AD8604AR AD8604AR-REEL AD8604AR-REEL7 AD8604DR AD8604DR-REEL AD8604ARU AD8604ARU-REEL AD8604DRU AD8604DRU-REEL -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C -40C to +125C 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 8-Lead SOIC 8-Lead SOIC 8-Lead SOIC 8-Lead SOIC 8-Lead SOIC 8-Lead SOIC 8-Lead MSOP 8-Lead MSOP 8-Lead MSOP 14-Lead SOIC 14-Lead SOIC 14-Lead SOIC 14-Lead SOIC 14-Lead SOIC 14-Lead TSSOP 14-Lead TSSOP 14-Lead TSSOP 14-Lead TSSOP RT-5 RT-5 RT-5 RT-5 RT-5 RT-5 R-8 R-8 R-8 R-8 R-8 R-8 RM-8 RM-8 RM-8 R-14 R-14 R-14 R-14 R-14 RU-14 RU-14 RU-14 RU-14 Branding AAA AAA AAA AAD AAD AAD ABA ABA ABD CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although the AD8601/AD8602/AD8604 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality. -4- REV. D Typical Performance Characteristics- AD8601/AD8602/AD8604 60 3,000 50 QUANTITY - Amplifiers 2,500 QUANTITY - Amplifiers VS = 5V TA = 25C TO 85C VS = 3V TA = 25C VCM = 0V TO 3V 2,000 1,500 1,000 0 1.0 0 0.8 0.6 0.4 0.2 0.2 0.4 0.6 INPUT OFFSET VOLTAGE - mV 0 1.0 1.5 VS = 5V TA = 25C VCM = 0V TO 5V 2 3 4 5 6 TCVOS - V/C 7 8 9 10 VS = 3V TA = 25C 1.0 INPUT OFFSET VOLTAGE - mV 2,500 1 TPC 4. Input Offset Voltage Drift Distribution 3,000 QUANTITY - Amplifiers 20 0 0.8 TPC 1. Input Offset Voltage Distribution 2,000 1,500 1,000 500 0.5 0 0.5 1.0 1.5 0 1.0 0 0.8 0.6 0.4 0.2 0.2 0.4 0.6 INPUT OFFSET VOLTAGE - mV 2.0 0.8 1.0 TPC 2. Input Offset Voltage Distribution 0 1.0 1.5 2.0 COMMON-MODE VOLTAGE - V 0.5 2.5 3.0 TPC 5. Input Offset Voltage vs. Common-Mode Voltage 1.5 60 VS = 3V TA = 25C TO 85C VS = 5V TA = 25C 1.0 INPUT OFFSET VOLTAGE - mV 50 QUANTITY - Amplifiers 30 10 500 40 30 20 10 0.5 0 0.5 1.0 1.5 2.0 0 0 1 2 3 4 5 6 TCVOS - V/C 7 8 9 10 0 1 2 3 COMMON-MODE VOLTAGE - V 4 5 TPC 6. Input Offset Voltage vs. Common-Mode Voltage TPC 3. Input Offset Voltage Drift Distribution REV. D 40 -5- AD8601/AD8602/AD8604 300 30 VS = 3V VS = 3V INPUT OFFSET CURRENT - pA INPUT BIAS CURRENT - pA 250 200 150 100 50 25 20 15 10 5 0 40 25 10 5 20 35 50 65 TEMPERATURE - C 80 95 110 0 40 25 10 125 TPC 7. Input Bias Current vs. Temperature 80 95 110 125 30 VS = 5V VS = 5V INPUT OFFSET CURRENT - pA 250 INPUT BIAS CURRENT - pA 20 35 50 65 TEMPERATURE - C TPC 10. Input Offset Current vs. Temperature 300 200 150 100 50 25 20 15 10 5 0 40 25 10 5 20 35 50 65 TEMPERATURE - C 80 95 110 0 40 25 10 125 5 20 35 50 65 TEMPERATURE - C 80 95 110 125 TPC 8. Input Bias Current vs. Temperature TPC 11. Input Offset Current vs. Temperature 5 10k VS = 2.7V TA = 25C VS = 5V TA = 25C 4 1k OUTPUT VOLTAGE - mV INPUT BIAS CURRENT - pA 5 3 2 1 100 SOURCE SINK 10 1 0 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 COMMON-MODE VOLTAGE - V 4.5 0.1 0.001 5.0 TPC 9. Input Bias Current vs. Common-Mode Voltage 0.01 0.1 1 LOAD CURRENT - mA 10 100 TPC 12. Output Voltage to Supply Rail vs. Load Current -6- REV. D AD8601/AD8602/AD8604 10k 35 VS = 5V TA = 25C VS = 2.7V 30 OUTPUT VOLTAGE - mV OUTPUT VOLTAGE - mV 1k SOURCE 100 SINK 10 25 VOL @ 1mA LOAD 20 15 10 1 5 0.1 0.001 0.1 1 LOAD CURRENT - mA 0.01 10 0 40 25 10 100 TPC 13. Output Voltage to Supply Rail vs. Load Current 20 35 50 65 TEMPERATURE - C 80 95 110 125 TPC 16. Output Voltage Swing vs. Temperature 5.1 2.67 VS = 5V VS = 2.7V 5.0 2.66 VOH @ 1mA LOAD OUTPUT VOLTAGE - V OUTPUT VOLTAGE - V 5 4.9 4.8 VOH @ 10mA LOAD 4.7 2.65 VOH @ 1mA LOAD 2.64 2.63 4.6 4.5 40 25 10 5 20 35 50 65 TEMPERATURE - C 80 95 110 2.62 40 25 10 125 TPC 14. Output Voltage Swing vs. Temperature 5 20 35 50 65 TEMPERATURE - C 80 95 110 125 TPC 17. Output Voltage Swing vs. Temperature 250 VS = 5V 100 150 VOL @ 10mA LOAD 100 45 40 90 20 135 0 180 -20 -40 50 VOL @ 1mA LOAD 0 40 25 10 5 20 35 50 65 TEMPERATURE - C -60 80 95 110 125 1k TPC 15. Output Voltage Swing vs. Temperature REV. D 60 PHASE SHIFT - Degrees 80 GAIN - dB OUTPUT VOLTAGE - mV 200 VS = 3V RL = NO LOAD TA = 25C 10k 100k 1M FREQUENCY - Hz 10M 100M TPC 18. Open-Loop Gain and Phase vs. Frequency -7- AD8601/AD8602/AD8604 3.0 VS = 5V RL = NO LOAD TA = 25C 2.5 60 45 40 90 20 135 0 180 -20 OUTPUT SWING - V p-p GAIN - dB 80 PHASE SHIFT - Degrees 100 -40 2.0 VS = 2.7V VIN = 2.6V p-p RL = 2k TA = 25C AV = 1 1.5 1.0 0.5 -60 1k 10k 100k 1M FREQUENCY - Hz 10M 0 1k 100M TPC 19. Open-Loop Gain and Phase vs. Frequency 10k 100k FREQUENCY - Hz 1M 10M TPC 22. Closed-Loop Output Voltage Swing vs. Frequency 6 CLOSED-LOOP GAIN - dB 40 AV = 100 5 OUTPUT SWING - V p-p VS = 3V TA = 25C AV = 10 20 AV = 1 0 4 3 VS = 5V VIN = 4.9V p-p RL = 2k TA = 25C AV = 1 2 1 1k 100k 1M FREQUENCY - Hz 10k 10M 0 1k 100M TPC 20. Closed-Loop Gain vs. Frequency 10k 100k FREQUENCY - Hz 1M 10M TPC 23. Closed-Loop Output Voltage Swing vs. Frequency 200 CLOSED-LOOP GAIN - dB 40 180 AV = 100 AV = 10 20 AV = 1 0 VS = 3V TA = 25C 160 OUTPUT IMPEDANCE - VS = 5V TA = 25C 140 AV = 100 120 100 AV = 10 80 AV = 1 60 40 20 1k 10k 100k 1M FREQUENCY - Hz 10M 0 100 100M TPC 21. Closed-Loop Gain vs. Frequency 1k 10k 100k FREQUENCY - Hz 1M 10M TPC 24. Output Impedance vs. Frequency -8- REV. D AD8601/AD8602/AD8604 160 200 VS = 5V TA = 25C 140 POWER SUPPLY REJECTION - dB 180 OUTPUT IMPEDANCE - 160 140 120 AV = 100 100 AV = 10 80 AV = 1 60 40 120 100 80 60 40 20 0 20 20 0 100 1k 10k 100k FREQUENCY - Hz 1M 40 100 10M TPC 25. Output Impedance vs. Frequency SMALL SIGNAL OVERSHOOT - % COMMON-MODE REJECTION - dB 60 100 80 60 40 20 0 20 1k 10k 100k FREQUENCY - Hz 1M 50 OS 40 30 +OS 20 10 100 CAPACITANCE - pF 1k 70 VS = 5V TA = 25C 140 60 120 SMALL SIGNAL OVERSHOOT - % COMMON-MODE REJECTION - dB 10M TPC 29. Small Signal Overshoot vs. Load Capacitance 160 100 80 60 40 20 0 20 50 VS = 5V RL = TA = 25C AV = 1 40 30 20 OS 10 +OS 1k 10k 100k FREQUENCY - Hz 1M 0 10 10M 20M TPC 27. Common-Mode Rejection Ratio vs. Frequency REV. D 1M VS = 2.7V RL = TA = 25C AV = 1 0 10 10M 20M TPC 26. Common-Mode Rejection Ratio vs. Frequency 40 10k 100k FREQUENCY - Hz 70 VS = 3V TA = 25C 120 40 1k TPC 28. Power Supply Rejection Ratio vs. Frequency 160 140 VS = 5V TA = 25C 100 CAPACITANCE - pF 1k TPC 30. Small Signal Overshoot vs. Load Capacitance -9- AD8601/AD8602/AD8604 0.1 VS = 5V TA = 25C VS = 5V RL = 10k 0.01 0.8 0.6 RL = 600 RL = 2k G=1 RL = 10k 0.001 0.4 0.2 5 20 35 50 65 TEMPERATURE - C 80 95 110 0.0001 125 100 20 1k FREQUENCY - Hz 10k 20k TPC 34. Total Harmonic Distortion + Noise vs. Frequency TPC 31. Supply Current per Amplifier vs. Temperature 1.0 64 VS = 3V VOLTAGE NOISE DENSITY - nV/ Hz SUPPLY CURRENT PER AMPLIFIER - mA RL = 2k G = 10 0 40 25 10 0.8 0.6 0.4 0.2 VS = 2.7V TA = 25C 56 48 40 32 24 16 8 0 40 25 10 5 20 35 50 65 TEMPERATURE - C 80 95 110 0 125 TPC 32. Supply Current per Amplifier vs. Temperature 0.8 208 0.7 182 0.6 0.5 0.4 0.3 0.2 5 10 15 FREQUENCY - kHz 20 25 VS = 2.7V TA = 25C 156 130 104 78 52 26 0.1 0 0 TPC 35. Voltage Noise Density vs. Frequency VOLTAGE NOISE DENSITY - nV/ Hz SUPPLY CURRENT PER AMPLIFIER - mA RL = 600 1.0 THD + N - % SUPPLY CURRENT PER AMPLIFIER - mA 1.2 0 0 1 2 3 4 SUPPLY VOLTAGE - V 5 6 TPC 33. Supply Current per Amplifier vs. Supply Voltage 0 0.5 1.0 1.5 FREQUENCY - kHz 2.0 2.5 TPC 36. Voltage Noise Density vs. Frequency -10- REV. D AD8601/AD8602/AD8604 VS = 5V TA = 25C VS = 5V TA = 25C 182 156 VOLTAGE - 2.5V/DIV VOLTAGE NOISE DENSITY - nV/ Hz 208 130 104 78 52 26 0 0 0.5 1.0 1.5 FREQUENCY - kHz 2.0 2.5 TIME - 1s/DIV TPC 37. Voltage Noise Density vs. Frequency TPC 40. 0.1 Hz to 10 Hz Input Voltage Noise 64 VOLTAGE NOISE DENSITY - nV/ Hz VS = 5V RL = 10k CL = 200pF TA = 25C VS = 5V TA = 25C 56 48 40 32 24 16 8 50.0mV/DIV 0 0 5 10 15 FREQUENCY - kHz 20 200ns/DIV 25 TPC 38. Voltage Noise Density vs. Frequency TPC 41. Small Signal Transient Response VS = 2.7V RL = 10k CL = 200pF TA = 25C VOLTAGE - 2.5V/DIV VS = 2.7V TA = 25C 50.0mV/DIV 200ns/DIV TIME - 1s/DIV TPC 39. 0.1 Hz to 10 Hz Input Voltage Noise REV. D TPC 42. Small Signal Transient Response -11- VS = 5V RL = 10k CL = 200pF AV = 1 TA = 25C VIN VOLTAGE - 1V/DIV VOLTAGE - 1.0V/DIV AD8601/AD8602/AD8604 VOUT TIME - 400ns/DIV TIME - 2.0s/DIV TPC 43. Large Signal Transient Response TPC 46. No Phase Reversal VS = 2.7V RL = 10k CL = 200pF AV = 1 TA = 25C VS = 5V RL = 10k VO = 2V p-p TA = 25C VOLTAGE - V VOLTAGE - 500mV/DIV VS = 5V RL = 10k AV = 1 TA = 25C VIN +0.1% ERROR VOUT 0.1% ERROR VIN TRACE - 0.5V/DIV VOUT TRACE - 10mV/DIV TIME - 100ns/DIV TIME - 400ns/DIV TPC 44. Large Signal Transient Response TPC 47. Settling Time 2.0 VS = 2.7V TA = 25C 1.5 1.0 OUTPUT SWING - V VOLTAGE - 1V/DIV VIN VS = 2.7V RL = 10k AV = 1 TA = 25C VOUT 0.1% 0.01% 0.5 0 0.5 0.1% 1.0 0.01% 1.5 2.0 300 TIME - 2.0s/DIV 350 400 450 500 550 600 SETTLING TIME - ns TPC 45. No Phase Reversal TPC 48. Output Swing vs. Settling Time -12- REV. D AD8601/AD8602/AD8604 Rail-to-Rail Input Stage 5 The input common-mode voltage range of the AD860x extends to both positive and negative supply voltages. This maximizes the usable voltage range of the amplifier, an important feature for single-supply and low voltage applications. This rail-to-rail input range is achieved by using two input differential pairs, one NMOS and one PMOS, placed in parallel. The NMOS pair is active at the upper end of the common-mode voltage range, and the PMOS pair is active at the lower end. OUTPUT SWING - V 3 2 1 0.1% 0.01% 0 0.1% 1 0.01% 2 3 4 5 0 200 400 600 800 1,000 SETTLING TIME - ns TPC 49. Output Swing vs. Settling Time THEORY OF OPERATION The AD8601/AD8602/AD8604 family of amplifiers are rail-torail input and output precision CMOS amplifiers that operate from 2.7 V to 5.0 V of power supply voltage. These amplifiers use Analog Devices' DigiTrim(R) technology to achieve a higher degree of precision than available from most CMOS amplifiers. DigiTrim technology is a method of trimming the offset voltage of the amplifier after it has already been assembled. The advantage in post-package trimming lies in the fact that it corrects any offset voltages due to the mechanical stresses of assembly. This technology is scalable and used with every package option, including SOT-23-5, providing lower offset voltages than previously achieved in these small packages. The NMOS and PMOS input stages are separately trimmed using DigiTrim to minimize the offset voltage in both differential pairs. Both NMOS and PMOS input differential pairs are active in a 500 mV transition region, when the input commonmode voltage is between approximately 1.5 V and 1 V below the positive supply voltage. Input offset voltage will shift slightly in this transition region, as shown in TPCs 5 and 6. Commonmode rejection ratio will also be slightly lower when the input common-mode voltage is within this transition band. Compared to the Burr Brown OPA2340 rail-to-rail input amplifier, shown in Figure 1, the AD860x, shown in Figure 2, exhibits lower offset voltage shift across the entire input common-mode range, including the transition region. The DigiTrim process is done at the factory and does not add additional pins to the amplifier. All AD860x amplifiers are available in standard op amp pinouts, making DigiTrim completely transparent to the user. The AD860x can be used in any precision op amp application. 0.7 0.4 0.1 0.2 0.5 0.8 1.1 The input stage of the amplifier is a true rail-to-rail architecture, allowing the input common-mode voltage range of the op amp to extend to both positive and negative supply rails. The voltage swing of the output stage is also rail-to-rail and is achieved by using an NMOS and PMOS transistor pair connected in a common-source configuration. The maximum output voltage swing is proportional to the output current, and larger currents will limit how close the output voltage can get to the supply rail. This is a characteristic of all rail-to-rail output amplifiers. With 1 mA of output current, the output voltage can reach within 20 mV of the positive rail and within 15 mV of the negative rail. At light loads of >100 k, the output swings within ~1 mV of the supplies. The open-loop gain of the AD860x is 80 dB, typical, with a load of 2 k. Because of the rail-to-rail output configuration, the gain of the output stage and the open-loop gain of the amplifier are dependent on the load resistance. Open-loop gain will decrease with smaller load resistances. Again, this is a characteristic inherent to all rail-to-rail output amplifiers. 1.4 0 1 2 3 4 5 VCM - V Figure 1. Burr Brown OPA2340UR Input Offset Voltage vs. Common-Mode Voltage, 24 SOIC Units @ 25C 0.7 0.4 0.1 VOS - mV 4 VOS - mV VS = 5V TA = 25C 0.2 0.5 0.8 1.1 1.4 0 1 2 3 4 5 VCM - V Figure 2. AD8602AR Input Offset Voltage vs. Common-Mode Voltage, 300 SOIC Units @ 25C REV. D -13- AD8601/AD8602/AD8604 Input Overvoltage Protection 10pF (OPTIONAL) As with any semiconductor device, if a condition could exist that would cause the input voltage to exceed the power supply, the device's input overvoltage characteristic must be considered. Excess input voltage will energize internal PN junctions in the AD860x, allowing current to flow from the input to the supplies. 4.7M VOUT 4.7V/A D1 AD8601 This input current will not damage the amplifier, provided it is limited to 5 mA or less. This can be ensured by placing a resistor in series with the input. For example, if the input voltage could exceed the supply by 5 V, the series resistor should be at least (5 V/5 mA) = 1 k. With the input voltage within the supply rails, a minimal amount of current is drawn into the inputs, which, in turn, causes a negligible voltage drop across the series resistor. Therefore, adding the series resistor will not adversely affect circuit performance. Figure 3. Amplifier Photodiode Circuit High- and Low-Side Precision Current Monitoring Overdrive Recovery Overdrive recovery is defined as the time it takes the output of an amplifier to come off the supply rail when recovering from an overload signal. This is tested by placing the amplifier in a closed-loop gain of 10 with an input square wave of 2 V p-p while the amplifier is powered from either 5 V or 3 V. Because of its low input bias current and low offset voltage, the AD860x can be used for precision current monitoring. The true rail-to-rail input feature of the AD860x allows the amplifier to monitor current on either high-side or low-side. Using both amplifiers in an AD8602 provides a simple method for monitoring both current supply and return paths for load or fault detection. Figures 4 and 5 demonstrate both circuits. 3V R2 2.49k MONITOR OUTPUT The AD860x has excellent recovery time from overload conditions. The output recovers from the positive supply rail within 200 ns at all supply voltages. Recovery from the negative rail is within 500 ns at 5 V supply, decreasing to within 350 ns when the device is powered from 2.7 V. Q1 2N3904 3V R1 100 Power-On Time 1/2 AD8602 Power-on time is important in portable applications, where the supply voltage to the amplifier may be toggled to shut down the device to improve battery life. Fast power-up behavior ensures that the output of the amplifier will quickly settle to its final voltage, improving the power-up speed of the entire system. Once the supply voltage reaches a minimum of 2.5 V, the AD860x will settle to a valid output within 1 s. This turn-on response time is faster than many other precision amplifiers, which can take tens or hundreds of microseconds for their outputs to settle. Figure 4. A Low-Side Current Monitor RSENSE 0.1 IL V+ 3V 3V R1 100 1/2 AD8602 Using the AD8602 in High Source Impedance Applications The CMOS rail-to-rail input structure of the AD860x allows these amplifiers to have very low input bias currents, typically 0.2 pA. This allows the AD860x to be used in any application that has a high source impedance or must use large value resistances around the amplifier. For example, the photodiode amplifier circuit shown in Figure 3 requires a low input bias current op amp to reduce output voltage error. The AD8601 minimizes offset errors due to its low input bias current and low offset voltage. Q1 2N3905 MONITOR OUTPUT R2 2.49k Figure 5. A High-Side Current Monitor Voltage drop is created across the 0.1 resistor that is proportional to the load current. This voltage appears at the inverting input of the amplifier due to the feedback correction around the op amp. This creates a current through R1 which, in turn, pulls current through R2. For the low-side monitor, the monitor output voltage is given by The current through the photodiode is proportional to the incident light power on its surface. The 4.7 M resistor converts this current into a voltage, with the output of the AD8601 increasing at 4.7 V/A. The feedback capacitor reduces excess noise at higher frequencies by limiting the bandwidth of the circuit to 1 BW = 2(4.7 M)CF RETURN TO GROUND RSENSE 0.1 (1) R Monitor Output = 3V - R2 x SENSE x IL R1 (2) Using a 10 pF feedback capacitor limits the bandwidth to approximately 3.3 kHz. -14- REV. D AD8601/AD8602/AD8604 For the high-side monitor, the monitor output voltage is The AD8601, AD7476, and AD5320 are all available in spacesaving SOT-23 packages. R Monitor Output = R2 x SENSE x IL R1 (3) Using the components shown, the monitor output transfer function is 2.5 V/A. Using the AD8601 in Single-Supply Mixed-Signal Applications Single-supply mixed-signal applications requiring 10 or more bits of resolution demand both a minimum of distortion and a maximum range of voltage swing to optimize performance. To ensure that the A/D or D/A converters achieve their best performance, an amplifier often must be used for buffering or signal conditioning. The 750 V maximum offset voltage of the AD8601 allows the amplifier to be used in 12-bit applications powered from a 3 V single supply, and its rail-to-rail input and output ensure no signal clipping. Figure 6 shows the AD8601 used as an input buffer amplifier to the AD7476, a 12-bit 1 MHz A/D converter. As with most A/D converters, total harmonic distortion (THD) increases with higher source impedances. By using the AD8601 in a buffer configuration, the low output impedance of the amplifier minimizes THD while the high input impedance and low bias current of the op amp minimizes errors due to source impedance. The 8 MHz gain-bandwidth product of the AD8601 ensures no signal attenuation up to 500 kHz, which is the maximum Nyquist frequency for the AD7476. 3V 1F TANT 680nF 4 REF193 0.1F 10F 1 RS 3 5V 2 V DD 28 LEFTOUT 35 RIGHTOUT 36 C/P 1F 4 5 1 VOUT 0V TO 3.0V 3 2 AD8601 RL 2 Figure 7. Using the AD8601 as a DAC Output Buffer to Drive Heavy Loads REV. D R2 2k 5 U1-B 7 C2 100F 6 R5 20 R3 2k U1 = AD8602D The SPICE macro-model for the AD860x amplifier is available and can be downloaded from the Analog Devices website at www.analog.com. The model will accurately simulate a number of both dc and ac parameters, including open-loop gain, bandwidth, phase margin, input voltage range, output voltage swing versus output current, slew rate, input voltage noise, CMRR, PSRR, and supply current versus supply voltage. The model is optimized for performance at 27C. Although it will function at different temperatures, it may lose accuracy with respect to the actual behavior of the AD860x. 3V 1 4 R4 20 SPICE Model Figure 7 demonstrates how the AD8601 can be used as an output buffer for the DAC for driving heavy resistive loads. The AD5320 is a 12-bit D/A converter that can be used with clock frequencies up to 30 MHz and signal frequencies up to 930 kHz. The rail-to-rail output of the AD8601 allows it to swing within 100 mV of the positive supply rail while sourcing 1 mA of current. The total current drawn from the circuit is less than 1 mA, or 3 mW from a 3 V single supply. AD5320 3 C1 100F Figure 8. A PC100 Compliant Line Output Amplifier Figure 6. A Complete 3 V 12-Bit 1 MHz A/D Conversion System 6 U1-A NOTE: ADDITIONAL PINS OMITTED FOR CLARITY SERIAL INTERFACE 5 1 AD1881 (AC'97) AD7476/AD7477 3-WIRE SERIAL INTERFACE 8 CS GND 4 5V VDD 5V SUPPLY 0.1F SDATA AD8601 2 Figure 8 shows how an AD8602 can be interfaced with an AC'97 codec to drive the line output. Here, the AD8602 is used as a unity-gain buffer from the left and right outputs of the AC'97 codec. The 100 F output coupling capacitors block dc current and the 20 series resistors protect the amplifier from short circuits at the jack. SCLK VIN VIN Because of its low distortion and rail-to-rail input and output, the AD860x is an excellent choice for low-cost, single-supply audio applications, ranging from microphone amplification to line output buffering. TPC 34 shows the total harmonic distortion plus noise (THD + N) figures for the AD860x. In unity gain, the amplifier has a typical THD + N of 0.004%, or -86 dB, even with a load resistance of 600 . This is compliant with the PC100 specification requirements for audio in both portable and desktop computers. VSS VDD 5 PC100 Compliance for Computer Audio Applications -15- AD8601/AD8602/AD8604 OUTLINE DIMENSIONS 14-Lead Thin Shrink Small Outline Package [TSSOP] (RU-14) 5-Lead Small Outline Transistor Package [SOT-23] (RT-5) Dimensions shown in millimeters Dimensions shown in millimeters 5.10 5.00 4.90 2.90 BSC 5 14 8 4 2.80 BSC 1.60 BSC 4.50 4.40 4.30 1 6.40 BSC 2 3 PIN 1 1 0.95 BSC 7 PIN 1 1.05 1.00 0.80 0.65 BSC 1.20 MAX 0.15 0.05 1.90 BSC 1.30 1.15 0.90 0.30 0.19 0.20 0.09 SEATING COPLANARITY PLANE 0.10 1.45 MAX 0.75 0.60 0.45 8 0 0.15 MAX 0.50 0.30 0.22 0.08 10 5 0 SEATING PLANE 0.60 0.45 0.30 COMPLIANT TO JEDEC STANDARDS MO-153AB-1 COMPLIANT TO JEDEC STANDARDS MO-178AA 14-Lead Standard Small Outline Package [SOIC] (R-14) 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters and (inches) Dimensions shown in millimeters 8.75 (0.3445) 8.55 (0.3366) 4.00 (0.1575) 3.80 (0.1496) 3.00 BSC 14 8 1 7 8 6.20 (0.2441) 5.80 (0.2283) 5 4.90 BSC 3.00 BSC 1 0.25 (0.0098) 0.10 (0.0039) COPLANARITY 0.10 1.27 (0.0500) BSC 0.51 (0.0201) 0.31 (0.0122) 0.50 (0.0197) 45 0.25 (0.0098) 1.75 (0.0689) 1.35 (0.0531) SEATING PLANE 4 PIN 1 0.65 BSC 8 0.25 (0.0098) 0 1.27 (0.0500) 0.40 (0.0157) 0.17 (0.0067) 1.10 MAX 0.15 0.00 0.38 0.22 COPLANARITY 0.10 COMPLIANT TO JEDEC STANDARDS MS-012AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN 0.23 0.08 8 0 0.80 0.60 0.40 SEATING PLANE COMPLIANT TO JEDEC STANDARDS MO-187AA 8-Lead Standard Small Outline Package [SOIC] (R-8) Dimensions shown in millimeters and (inches) 5.00 (0.1968) 4.80 (0.1890) 4.00 (0.1574) 3.80 (0.1497) 8 5 1 4 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) COPLANARITY SEATING 0.10 PLANE 6.20 (0.2440) 5.80 (0.2284) 1.75 (0.0688) 1.35 (0.0532) 0.51 (0.0201) 0.31 (0.0122) 0.50 (0.0196) 45 0.25 (0.0099) 8 0.25 (0.0098) 0 1.27 (0.0500) 0.40 (0.0157) 0.17 (0.0067) COMPLIANT TO JEDEC STANDARDS MS-012AA CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN -16- REV. D AD8601/AD8602/AD8604 Revision History Location Page 11/03--Data Sheet changed from REV. C to REV. D. Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 3/03--Data Sheet changed from REV. B to REV. C. Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 3/03--Data Sheet changed from REV. A to REV. B. Change to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Change to FUNCTIONAL BLOCK DIAGRAMS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 Change to TPC 39 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11 Changes to Figures 4 and 5 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14 Changes to Equations 2 and 3 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14, 15 Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16 REV. D -17- -18- -19- -20- C01525-0-11/03(D)