July 2011 Doc ID 1459 Rev 2 1/23
23
TDA2030A
18 W hi-fi amplifier and 35 W driver
Features
■Output power 18 W at VS = ±16 V / 4 Ω with
0.5% distortion
■High output current
■Very low harmonic and crossover distortion
■Short-circuit protection
■Thermal shutdown
Description
The TDA2030A is a monolithic IC in a Pentawatt
package intended for use as a low-frequency
class-AB amplifier.
With V
S max
= 44 V it is particularly suited for more
reliable applications without regulated supply and
for 35 W driver circuits using low-cost
complementary pairs.
The TDA2030A provides high output current and
has very low harmonic and crossover distortion.
The device incorporates a short-circuit protection
system comprising an arrangement for
automatically limiting the dissipated power so as
to keep the operating point of the output
transistors within their safe operating range. A
conventional thermal shutdown system is also
included.
Figure 1. Typical application
Table 1. Device summary
Order code Package
TDA2030AV Pentawatt (vertical)
Pentawatt (vertical)
www.st.com
Device overview TDA2030A
2/23 Doc ID 1459 Rev 2
1 Device overview
Figure 2. Pin connections (top view)
Figure 3. Test circuit
Table 2. Thermal data
Table 3. Absolute maximum ratings
Symbol Parameter Value Unit
R
th (j-case)
Thermal resistance junction-case max. 3°C/W
Symbol Parameter Value Unit
V
s
Supply voltage ± 22 V
V
i
Input voltage V
s
V
i
Differential input voltage ± 15 V
I
o
Peak output current (internally limited) 3.5 A
P
tot
Total power dissipation at T
case
= 90 °C 20 W
T
stg
, T
j
Storage and junction temperature – 40 to + 150 °C
TDA2030A Device overview
Doc ID 1459 Rev 2 3/23
Table 4. Electrical characteristics
(Refer to the test circuit, V
S
= ±16 V, T
amb
= 25 °C unless otherwise specified)
Symbol Parameter Test condition Min. Typ. Max. Unit
V
s
Supply voltage ± 6 ± 22 V
I
d
Quiescent drain current 50 80 mA
I
b
Input bias current V
S
= ± 22 V 0.2 2 µA
V
os
Input offset voltage V
S
= ± 22 V ± 2 ± 20 mV
I
os
Input offset current ± 20 ± 200 nA
P
O
Output power
d = 0.5%, G
v
= 26 dB
f = 40 to 15000 Hz
R
L
= 4 Ω
R
L
= 8 Ω
V
S
= ± 19 V; R
L
= 8 Ω
15
10
13
18
12
16
W
BW Power bandwidth P
o
= 15 W; R
L
= 4 Ω100 kHz
SR Slew rate 8 V/µsec
G
v
Open loop voltage gain f = 1 kHz 80 dB
G
v
Closed loop voltage gain f = 1 kHz 25.5 26 26.5 dB
d Total harmonic distortion
P
o
= 0.1 to 14 W; R
L
= 4 Ω
f = 40 to 15 000 Hz; f = 1 kHz
P
o
= 0.1 to 9 W, f = 40 to 15 000Hz
R
L
= 8 Ω
0.08
0.03
0.5
%
d
2
Second order CCIF
intermodulation distortion P
O
= 4W, f
2
– f
1
= 1kHz, R
L
= 4Ω0.03 %
d3Third order CCIF
intermodulation distortion
f
1
= 14 kHz, f
2
= 15 kHz
2f
1
– f
2
= 13 kHz 0.08 %
e
N
Input noise voltage B = Curve A 2 µV
B = 22Hz to 22kHz 3 10 µV
i
N
Input noise current B = Curve A 50 pA
B = 22Hz to 22kHz 80 200 pA
S/N Signal-to-noise ratio
R
L
= 4Ω, R
g
= 10kΩ, B = Curve A
P
O
= 15W 106 dB
P
O
= 1W 94 dB
R
i
Input resistance (pin 1) (open loop) f = 1 kHz 0.5 5 MΩ
SVR Supply voltage rejection R
L
= 4 Ω, R
g
= 22 kΩ54 dB
G
v
= 26 dB, f = 100 Hz
T
j
Thermal shutdown junction
temperature 145 °C
Device overview TDA2030A
4/23 Doc ID 1459 Rev 2
Figure 4. Single supply amplifier
Figure 5. Open loop-frequency response Figure 6. Output power vs. supply voltage
TDA2030A Device overview
Doc ID 1459 Rev 2 5/23
Figure 7. Total harmonic distortion vs. output
power (test using rise filters)
Figure 8. Two-tone CCIF intermodulation
distortion
Figure 9. Large signal frequency response Figure 10. Maximum allowable power
dissipation vs. ambient temp.
Device overview TDA2030A
6/23 Doc ID 1459 Rev 2
Figure 11. Output power vs. supply voltage Figure 12. Total harmonic distortion vs. output
power
Figure 13. Output power vs. input level Figure 14. Power dissipation vs. output power
TDA2030A Device overview
Doc ID 1459 Rev 2 7/23
Figure 15. Single-supply high-power amplifier (TDA2030A + BD907/BD908)
Figure 16. PC board and component layout for the single-supply high-power amplifier
Device overview TDA2030A
8/23 Doc ID 1459 Rev 2
Table 5. Typical performance of the single-supply high-power amplifier
Figure 17. Typical amplifier with spilt power supply
Figure 18. PC board and component layout for the typical amplifier with split power supply
Symbol Parameter Test conditions Min. Typ. Max. Unit
V
s
Supply voltage 36 44 V
I
d
Quiescent drain current V
s
= 36 V 50 mA
P
o
Output power
d = 0.5%, R
L
= 4
Ω
, f = 40 z to 15 Hz
V
s
= 39 V
V
s
= 36 V
35
28
W
W
d = 10%, R
L
= 4 Ω, f = 1 kHz
V
s
= 39 V
V
s
= 36 V
44
35
W
W
G
v
Voltage gain f = 1 kHz 19.5 20 20.5 dB
SR Slew rate 8V/µs
d Total harmonic distortion f = 1kHz 0.02 %
P
o
= 20 W; f = 40 Hz to 15 kHz 0.05 %
V
i
Input sensitivity G
v
= 20 dB, f = 1 kHz, P
o
= 20 W, R
L
= 4 Ω890 mV
S/N Signal-to-noise ratio
R
L
= 4 Ω, R
g
= 10 kΩ, B = Curve A
P
o
= 25 W
P
o
= 4 W
108
100
dB
dB
TDA2030A Device overview
Doc ID 1459 Rev 2 9/23
Figure 19. Bridge amplifier with split power supply (P
O
= 34 W, V
S
= ± 16 V)
Figure 20. PC board and component layout for the bridge amplifier with split power
supply
Multiway speaker systems and active boxes TDA2030A
10/23 Doc ID 1459 Rev 2
2 Multiway speaker systems and active boxes
Multiway loudspeaker systems provide the best possible acoustic performance since each
loudspeaker is specially designed and optimized to handle a limited range of frequencies.
Commonly, these loudspeaker systems divide the audio spectrum into two or three bands.
To maintain a flat frequency response over the hi-fi audio range, the bands covered by each
loudspeaker must overlap slightly. Imbalance between the loudspeakers produces
unacceptable results, therefore it is important to ensure that each unit generates the correct
amount of acoustic energy for its segment of the audio spectrum. In this respect it is also
important to know the energy distribution of the music spectrum to determine the cutoff
frequencies of the crossover filters (see Figure 21). As an example, a 100 W three-way
system with crossover frequencies of 400 Hz and 3 kHz would require 50 W for the woofer,
35 W for the midrange unit and 15 W for the tweeter.
Figure 21. Power distribution vs. frequency
Both active and passive filters can be used for crossovers, but today active filters cost
significantly less than a good passive filter using air cored inductors and non-electrolytic
capacitors. In addition, active filters do not suffer from the typical defects of passive filters:
●power less
●increased impedance seen by the loudspeaker (lower damping)
●difficulty of precise design due to variable loudspeaker impedance.
Obviously, active crossovers can only be used if a power amplifier is provided for each drive
unit. This makes it particularly interesting and economically sound to use monolithic power
amplifiers.
In some applications, complex filters are not really necessary and simple RC low-pass and
high-pass networks (6 dB/octave) can be recommended. The results obtained are excellent
because this is the best type of audio filter and the only one free from phase and transient
distortion.
TDA2030A Multiway speaker systems and active boxes
Doc ID 1459 Rev 2 11/23
The rather poor out-of-band attenuation of single RC filters means that the loudspeaker
must operate linearly well beyond the crossover frequency to avoid distortion.
A more effective solution, "Active Power Filter" by STMicroelectronics is shown in Figure 22.
Figure 22. Active Power Filter
The proposed circuit can realize combined power amplifiers and 12 dB/octave or
18 dB/octave high-pass or low-pass filters.
In practice, at the input pins of the amplifier two equal and in-phase voltages are available,
as required for the active filter operation.
The impedance at the pin (-) is of the order of 100 Ω, while that of the pin (+) is very high,
which is also what was wanted.
The component values calculated for f
c
= 900 Hz using a Bessek 3rd order Sallen and Key
structure are :
Using this type of crossover filter, a complete 3-way 60 W active loudspeaker system is
shown in Figure 23.
It employs 2
nd
order Butterworth filters with the crossover frequencies equal to 300 Hz and
3 kHz. The midrange section consists of two filters, a high-pass circuit followed by a low-
pass network. With V
S
= 36 V the output power delivered to the woofer is 25 W at d = 0.06%
(30 W at d = 0.5%).
The power delivered to the midrange and the tweeter can be optimized in the design phase
taking in account the loudspeaker efficiency and impedance (R
L
= 4 Ω to 8 Ω).
It is quite common that midrange and tweeter speakers have an efficiency 3 dB higher than
woofers.
C
1
= C
2
= C
3
R
1
R
2
R
3
22 nF 8.2 kΩ5.6 kΩ33 kΩ
Multiway speaker systems and active boxes TDA2030A
12/23 Doc ID 1459 Rev 2
Figure 23. 3-way 60 W active loudspeaker system (V
S
= 36 V)
TDA2030A Musical instruments amplifiers
Doc ID 1459 Rev 2 13/23
3 Musical instruments amplifiers
Another important field of application for active systems is music.
In this area the use of several medium power amplifiers is more convenient than a single
high-power amplifier, and it is also more realiable. A typical example (see Figure 24)
consists of four amplifiers each driving a low-cost, 12-inch loudspeaker. This application can
supply 80 to 160 W
RMS
.
Figure 24. High-power active box for musical instrument
Transient intermodulation distortion (TIM) TDA2030A
14/23 Doc ID 1459 Rev 2
4 Transient intermodulation distortion (TIM)
Transient intermodulation distortion is an unfortunate phenomen associated with negative-
feedback amplifiers. When a feedback amplifier receives an input signal which rises very
steeply, i.e. contains high-frequency components, the feedback can arrive too late so that
the amplifiers overloads and a burst of intermodulation distortion will be produced as in
Figure 25. Since transients occur frequently in music this obviously a problem for the
designer of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to
reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient
intermodulation (TIM situation). The best known method for the measurement of TIM
consists of feeding sine waves superimposed onto square waves, into the amplifier under
test. The output spectrum is then examined using a spectrum analyser and compared to the
input. This method suffers from serious disadvantages : the accuracy is limited, the
measurement is a rather delicate operation and an expensive spectrum analyser is
essential. A new approach applied by STMicroelectronics to monolithic amplifiers
measurement is fast, cheap (it requires nothing more sophisticated than an oscilloscope)
and sensitive - and it can be used for values as low as 0.002% in high-power amplifiers.
Figure 25. Overshoot phenomenon in feedback amplifiers
TDA2030A Transient intermodulation distortion (TIM)
Doc ID 1459 Rev 2 15/23
The "inverting-sawtooth" method of measurement is based on the response of an amplifier
to a 20 kHz sawtooth waveform. The amplifier has no difficulty following the slow ramp, but it
cannot follow the fast edge. The output will follow the upper line in Figure 26 cutting of the
shaded area and thus increasing the mean level. If this output signal is filtered to remove the
sawtooth, direct voltage remains which indicates the amount of TIM distortion, although it is
difficult to measure because it is indistinguishable from the DC offset of the amplifier. This
problem is neatly avoided in the IS-TIM method by periodically inverting the sawtooth
waveform at a low audio frequency as shown in Figure 27.
Figure 26. 20 kHz sawtooth waveform
Figure 27. Inverting sawtooth waveform
In the case of the sawtooth in Figure 27 the mean level was increased by the TIM distortion,
for a sawtooth in the other direction, the opposite is true. The result is an AC signal at the
output whose peak-to-peak value is the TIM voltage, which can be measured easily with an
oscilloscope. If the peak-to-peak value of the signal and the peak-to-peak of the inverting
sawtooth are measured, the TIM can be found very simply from:
In Figure 28 the experimental results are shown for the 30 W amplifier using the TDA2030A
as a driver and a low-cost complementary pair. A simple RC filter on the input of the
amplifier to limit the maximum signal slope (SS) is an effective way to reduce TIM.
TIM VOUT
Vsawtooth
------------------------100⋅=
Transient intermodulation distortion (TIM) TDA2030A
16/23 Doc ID 1459 Rev 2
Figure 28. TIM distortion versus output power
The diagram of Figure 29 originated by STMicroelectronics can be used to find the slew
rate (SR) required for a given output power or voltage and a TIM design target.
For example if an anti-TIM filter with a cutoff at 30 kHz is used and the max. peak-to-peak
output voltage is 20 V then, referring to the diagram, a slew rate of 6 V/ms is necessary for
0.1% TIM. As shown slew rates of above 10 V/ms do not contribute to a further reduction in
TIM.
Slew rates of 100 V/ms are not only useless but also a disadvantage in hi-fi audio amplifiers
because they tend to turn the amplifier into a radio receiver.
Figure 29. TIM design diagram (f
C
= 30 kHz)
TDA2030A Power supply
Doc ID 1459 Rev 2 17/23
5 Power supply
Using a monolithic audio amplifier with non-regulated supply voltage, it is important to
design the power supply correctly. For any operation it must provide a supply voltage less
than the maximum value fixed by the IC breakdown voltage.
It is essential to take into account all the operating conditions, in particular mains
fluctuations and supply voltage variations with and without load. The TDA2030A
(VS max = 44 V) is particularly suitable for substitution of the standard IC power amplifiers
(with VS max = 36 V) for more reliable applications. An example, using a simple full-wave
rectifier followed by a capacitor filter, is shown in Tab l e 6 and in the diagram of Figure 30.
Figure 30. DC characteristics of 50 W non-regulated supply
Table 6. DC characteristics of 50 W non-regulated supply
A regulated supply is not usually used for the power output stages because its dimensioning
must be done taking into account the power to supply in the signal peaks. They are only a
small percentage of the total music signal, with consequently large overdimensioning of the
circuit.
Mains
(220 V)
Secondary
voltage
DC output voltage (Vo)
I
o
= 0
I
o
= 0.1 A
I
o
= 1 A
+ 20% 28.8 V 43.2 V 42 V 37.5 V
+ 15% 27.6 V 41.4 V 40.3 V 35.8 V
+ 10% 26.4 V 39.6 V 38.5 V 34.2 V
– 24 V 36.2 V 35 V 31 V
– 10% 21.6 V 32.4 V 31.5 V 27.8 V
– 15% 20.4 V 30.6 V 29.8 V 26 V
– 20% 19.2 V 28.8 V 28 V 24.3 V
Power supply TDA2030A
18/23 Doc ID 1459 Rev 2
Even if, with a regulated supply, higher output power can be obtained (V
S
is constant in all
operating conditions), the additional cost and power dissipation do not usually justify its use.
Using non-regulated supplies, there are fewer design restrictions. In fact, when signal peaks
are present, the capacitor filter acts as a flywheel, supplying the required energy. In average
conditions, the continuous power supplied is lower. The music power/continuous power ratio
is greater in this case than for the case of regulated supply, with space saving and cost
reduction.
TDA2030A Application recommendation
Doc ID 1459 Rev 2 19/23
6 Application recommendation
The recommended values of the components are those shown in the application circuit of
Figure 17. Different values can be used, please refer to the guidelines in Ta b l e 7 .
Table 7. Recommended values of components for a typical amplifier
Comp. Recom.
value Purpose Larger than
recommended value
Smaller than
recommended value
R1 22 kΩClosed loop gain setting Increase of gain Decrease of gain
R2 680 ΩClosed loop gain setting Decrease of gain(1)
1. The value of closed loop gain must be higher than 24 dB.
Increase of gain
R3 22 kΩNon inverting input
biasing Increase of input impedance Decrease of input
impedance
R4 1 ΩFrequency stability Danger of oscillation at high
frequencies with inductive loads
R5 ≅ 3 R2 Upper frequency cutoff Poor high-frequency attenuation Danger of oscillation
C1 1 μF Input DC decoupling Increase of low-frequency
cutoff
C2 22 μF Inverting DC decoupling Increase of low-frequency
cutoff
C3, C4 0.1 μF Supply voltage bypass Danger of oscillation
C5, C6 100 μF Supply voltage bypass Danger of oscillation
C7 0.22 μF Frequency stability Larger bandwidth
C8 ≅ Upper frequency cutoff Smaller bandwidth Larger bandwidth
D1, D2 1N4001 To protect the device against output voltage spikes
1
2πBR1
-------------------
Protections TDA2030A
20/23 Doc ID 1459 Rev 2
7 Protections
7.1 Short-circuit protection
The TDA2030A has an original circuit which limits the current of the output transistors. This
function can be considered as being peak power limiting rather than simple current limiting.
It reduces the possibility that the device gets damaged during an accidental short-circuit
from AC output to ground.
7.2 Thermal shutdown
The presence of a thermal limiting circuit offers the following advantages:
1. An overload on the output (even if it is permanent), or an above-limit ambient
temperature can be easily supported since Tj cannot be higher than 150 °C.
2. The heatsink can have a smaller factor of safety compared with that of a conventional
circuit. There is no possibility of device damage due to high junction temperature. If, for
any reason, the junction temperature increases up to 150 °C, the thermal shutdown
simply reduces the power dissipation and the current consumption.
TDA2030A Protections
Doc ID 1459 Rev 2 21/23
Figure 31. Pentawatt (vertical) mechanical data and package dimensions
In order to meet environmental requirements, ST offers these devices in different grades of
ECOPACK® packages, depending on their level of environmental compliance. ECOPACK®
specifications, grade definitions and product status are available at: www.st.com.
ECOPACK® is an ST trademark.
OUTLINE AND
MECHANICAL DATA
DIM. mm inch
MIN. TYP. MAX. MIN. TYP. MAX.
A 4.80 0.188
C 1.37 0.054
D 2.40 2.80 0.094 0.11
D1 1.20 1.35 0.047 0.053
E 0.35 0.55 0.014 0.022
E1 0.76 1.19 0.030 0.047
F 0.80 1.05 0.031 0.041
F1 1.00 1.40 0.039 0.055
G 3.20 3.40 3.60 0.126 0.134 0.142
G1 6.60 6.80 7.00 0.260 0.267 0.275
H2 10.40 0.41
H3 10.40 0.409
L 17.55 17.85 18.15 0.691 0.703 0.715
L1 15.55 15.75 15.95 0.612 0.620 0.628
L2 21.2 21.4 21.6 0.831 0.843 0.850
L3 22.3 22.5 22.7 0.878 0.886 0.894
L4 1.29 0.051
L5 2.60 3.00 0.102 0.118
L6 15.10 15.80 0.594 0.622
L7 6.00 6.60 0.236 0.260
L9 2.10 2.70 0.083 0.106
L10 4.30 4.80 0.170 0.189
M 4.23 4.5 4.75 0.167 0.178 0.187
M1 3.75 4.0 4.25 0.148 0.157 0.187
V4 40° (Typ.)
V5 90° (Typ.)
DIA 3.65 3.85 0.143 0.151
Pentawatt V
0015981 F
L
L1
A
C
L5
D1 L2
L3
E
M1
M
D
H3
Dia.
L7
L9
L10
L6
F1 H2
F
GG1
E1
F
E
V4
RESIN BETWEEN
LEADS
H2
V5
V4
PENTVME
L4
Weight: 2.00gr
Revision history TDA2030A
22/23 Doc ID 1459 Rev 2
8 Revision history
Table 8. Document revision history
Date Revision Changes
Oct-2000 1 Initial release.
13-Jul-2011 2
Added Features
Added Table 1: Device summary
Removed minimum value from Pentawatt (vertical) package dimension
H3 (Figure 31)
Revised general presentation, minor textual updates
TDA2030A
Doc ID 1459 Rev 2 23/23
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