DGN-8 THS3001 D-8 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 420-MHz HIGH-SPEED CURRENT-FEEDBACK AMPLIFIER Check for Samples: THS3001 FEATURES APPLICATIONS * * * * 1 2 * * * * * * High Speed: - 420-MHz Bandwidth (G = 1, -3 dB) - 6500-V/s Slew Rate - 40-ns Settling Time (0.1%) High Output Drive: IO = 100 mA Excellent Video Performance - 115-MHz Bandwidth (0.1 dB, G = 2) - 0.01% Differential Gain - 0.02 Differential Phase Low 3-mV (max) Input Offset Voltage Very Low Distortion: - THD = -96 dBc at f = 1 MHz - THD = -80 dBc at f = 10 MHz Wide Range of Power Supplies: - VCC = 4.5 V to 16 V Evaluation Module Available Communication Imaging High-Quality Video THS3001 D OR DGN PACKAGE (TOP VIEW) NC IN- IN+ 1 8 2 7 3 6 VCC- 4 5 NC VCC+ OUT NC NC - No internal connection RELATED DEVICES THS4011 /2 290-MHz VFB High-Speed Amplifier THS6012 500-mA CFB HIgh-Speed Amplifier THS6022 250-mA CFB High-Speed Amplifier DESCRIPTION The THS3001 is a high-speed current-feedback operational amplifier, ideal for communication, imaging, and high-quality video applications. This device offers a very fast 6500-V/s slew rate, a 420-MHz bandwidth, and 40-ns settling time for large-signal applications requiring excellent transient response. In addition, the THS3001 operates with a very low distortion of -96 dBc, making it well suited for applications such as wireless communication basestations or ultrafast ADC or DAC buffers. HARMONIC DISTORTION vs FREQUENCY -75 -80 8 Gain = 2 VCC = 15 V VO = 2 VPP RL = 150 RF = 750 -85 6 3rd Harmonic -90 2nd Harmonic -95 5 1M f - Frequency - Hz 10M VCC = 5 V RF = 750 4 3 2 1 0 -100 100k VCC = 15 V RF = 680 7 Output Amplitude - dB Harmonic Distortion - dBc -70 OUTPUT AMPLITUDE vs FREQUENCY G=2 RL = 150 VI = 200 mV RMS -1 100k 1M 10M 100M f - Frequency - Hz 1G 1 2 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright (c) 1998-2009, Texas Instruments Incorporated THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. AVAILABLE OPTIONS (1) PACKAGED DEVICE TA SOIC (D) 0C to 70C MSOP (DGN) THS3001CD THS3001CDGN THS3001CDR THS3001CDGNR MSOP SYMBOL ADP THS3001HVCDGN BNK THS3001HVCDGNR -40C to 85C THS3001ID THS3001IDGN THS3001IDR THS3001IDGNR ADQ THS3001HVIDGN BNJ THS3001HVIDGNR (1) TRANSPORT MEDIA, QUANTITY EVALUATION MODULE Rails, 75 THS3001EVM Tape and Reel, 2500 -- Rails, 75 -- Tape and Reel, 2500 -- Rails, 75 -- Tape and Reel, 2500 -- Rails, 75 -- Tape and Reel, 2500 -- For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI website at www.ti.com. ABSOLUTE MAXIMUM RATINGS (1) over operating free-air temperature range (unless otherwise noted) THS3001 VSS Supply voltage, VCC+ to VCC- VI Input voltage IO VID TJ TA Tstg (1) (2) (3) UNITS V 33 37 VCC VCC V Output current 175 175 mA Differential input voltage 6 6 V Continuous total power dissipation TJ THS3001HV Maximum junction temperature See Dissipation Rating Table (2) Maximum junction temperature, continuous operation, long term reliability Operating free-air temperature (3) 150 150 C 125 125 C THS3001C, THS3001HVC 0 to 70 0 to 70 C THS3001I, THS3001HVI -40 to 85 -40 to 85 C -65 to 125 -65 to 125 C Storage temperature Stresses above these ratings may cause permanent damage. Exposure to absolute maximum conditions for extended periods may degrade device reliability. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those specified is not implied. The absolute maximum temperature under any condition is limited by the constraints of the silicon process. The maximum junction temperature for continuous operation is limited by package constraints. Operation above this temperature may result in reduced reliability and/or lifetime of the device. DISSIPATION RATING TABLE (1) (2) 2 POWER RATING (2) JA (1) (C/W) TA 25C TA = 85C 38.3 97.5 1.02 W 410 mW 4.7 58.4 1.71 W 685 mW PACKAGE JC (C/W) D (8) DGN (8) This data was taken using the JEDEC standard High-K test PCB. Power rating is determined with a junction temperature of 125C. This is the point where distortion starts to substantially increase. Thermal management of the final PCB should strive to keep the junction temperature at or below 125C for best performance and long term reliability. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 RECOMMENDED OPERATING CONDITIONS MIN Split supply VSS Supply voltage, VCC+ and VCC- Single supply Split supply Single supply TA Operating free-air temperature NOM MAX THS3001C, THS3001I 4.5 9 32 THS3001HVC, THS3001HVI 4.5 18.5 9 37 0 70 -40 85 THS3001C, THS3001HVC THS3001I, THS3001HVI UNIT 16 V C ELECTRICAL CHARACTERISTICS At TA = 25C, RL = 150 , RF = 1 k (unless otherwise noted) PARAMETER TEST CONDITIONS Split supply VCC Power supply operating range Single supply VCC = 5 V ICC Quiescent current VCC = 15 V VCC = 18.5 V, THS3001HV VCC = 5 V VO Output voltage swing VCC = 15 V VCC = 5 V or 15 V Input offset voltage drift VCC = 5 V or 15 V VCC = 5 V or 15 V Negative (IN-) VICR Common-mode input voltage range Open loop transresistance CMRR Common-mode rejection ratio THS3001C THS3001I 9 33 THS3001HVx 9 TA = 25C TA = full range 6.6 TA = full range 6.9 TA = full range 9 mA 9.5 10.5 2.9 3.2 3 3.3 RL = 150 12.1 12.8 RL = 1 k 12.8 13.1 V 100 85 TA = 25C mA 120 1 TA = full range 3 mV 4 V/C 5 2 TA = full range 10 15 TA = 25C VCC = 15 V 1 10 A 15 3 3.2 12.9 13.2 VCC = 5 V, VO = 2.5 V, RL = 1 k 1.3 VCC = 15 V, VO = 7.5 V, RL = 1 k 2.4 VCC = 5 V, VCM = 2.5 V 62 70 VCC = 15 V, VCM = 10 V 65 73 TA = 25C 65 76 TA = full range 63 TA = 25C 69 TA = full range 67 Power supply rejection ratio 7.5 10 TA = 25C RL = 1 k V 8.5 TA = 25C RL = 150 UNIT 37 5.5 TA = full range VCC = 15 V (1) (2) 18.5 VCC = 5 V VCC = 5 V PSRR 4.5 TA = 25C Positive (IN+) Input bias current THS3001HVx RL = 75 Input offset voltage MAX 16.5 VCC = 15 V, VIO TYP 4.5 RL = 20 Output current (2) MIN THS3001C THS3001I VCC = 5 V, IO IIB (1) 76 V M dB dB dB Full range = 0C to 70C for the THS3001C and -40C to 85C for the THS3001I. Observe power dissipation ratings to keep the junction temperature below absolute maximum when the output is heavily loaded or shorted. See Absolute Maximum Ratings table. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 3 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com ELECTRICAL CHARACTERISTICS (continued) At TA = 25C, RL = 150 , RF = 1 k (unless otherwise noted) PARAMETER TEST CONDITIONS (1) MIN TYP MAX UNIT Positive (IN+) 1.5 M Negative (IN-) 15 7.5 pF RI Input resistance CI Differential input capacitance RO Output resistance Open loop at 5 MHz 10 Vn Input voltage noise VCC = 5 V or 15 V, f = 10 kHz, G = 2 1.6 nV/Hz In Input current noise Positive (IN+) Negative (IN-) 13 VCC = 5 V or 15 V, f = 10 kHz, G = 2 pA/Hz 16 OPERATING CHARACTERISTICS TA = 25C, RL = 150 , RF = 1 k (unless otherwise noted) PARAMETER SR Slew rate (1) VCC = 5 V, VO(PP) = 4 V G=5 1300 VCC = 15 V, VO(PP) = 20 V G = -5 6500 G=5 6300 Settling time to 0.1% Gain = -1, 40 Settling time to 0.1% VCC = 5 V, 0 V to 2 V Step, Gain = -1, 25 Total harmonic distortion VCC = 15 V, fc = 10 MHz, VO(PP) = 2 V, G=2 Differential gain error G = 2, 40 IRE modulation, 100 IRE Ramp, NTSC and PAL VCC = 5 V 0.015% VCC = 15 V 0.01% Differential phase error G = 2, 40 IRE modulation, 100 IRE Ramp, NTSC and PAL VCC = 5 V 0.01 VCC = 15 V 0.02 Small signal bandwidth (-3 dB) BW Bandwidth for 0.1 dB flatness Full power bandwidth (2) 4 TYP 1700 G = 1, RF = 1 k (1) (2) MIN G = -5 VCC = 15 V, 0 V to 10 V Step ts THD TEST CONDITIONS MAX UNIT V/s ns -80 dBc VCC = 5 V 330 MHz MHz VCC= 15 V 420 G = 2, RF = 750 , VCC = 5 V 300 G = 2, RF = 680 , VCC = 15 V 385 G = 5, RF = 560 , VCC = 15 V 350 G = 2, RF = 750 , VCC = 5 V 85 G = 2, RF = 680 , VCC = 15 V 115 VCC = 5 V, VO(PP) = 4 V, RL = 500 G = -5 65 G=5 62 VCC = 15 V, VO(PP) = 20 V, RL = 500 G = -5 32 G=5 31 MHz MHz MHz Slew rate is measured from an output level range of 25% to 75%. Full power bandwidth is defined as the frequency at which the output has 3% THD. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 PARAMETER MEASUREMENT INFORMATION RG RF VCC+ - VO + VI 50 VCC- RL Figure 1. Test Circuit, Gain = 1 + (RF/RG) TYPICAL CHARACTERISTICS Table of Graphs FIGURE |VO| Output voltage swing vs Free-air temperature 2 ICC Current supply vs Free-air temperature 3 IIB Input bias current vs Free-air temperature 4 VIO Input offset voltage vs Free-air temperature 5 vs Common-mode input voltage 6 vs Common-mode input voltage 7 vs Frequency 8 CMRR Common-mode rejection ratio Transresistance vs Free-air temperature 9 Closed-loop output impedance vs Frequency 10 Vn Voltage noise vs Frequency 11 In Current noise vs Frequency 11 vs Frequency 12 vs Free-air temperature 13 PSRR SR Power supply rejection ratio Slew rate Normalized slew rate vs Supply voltage vs Output step peak-to-peak vs Gain 14 15, 16 17 vs Peak-to-peak output voltage swing 18, 19 vs Frequency 20, 21 Differential gain vs Loading 22, 23 Differential phase vs Loading 24, 25 Output amplitude vs Frequency 26-30 Normalized output response vs Frequency Harmonic distortion Small and large signal frequency response 31-34 35, 36 Small signal pulse response 37, 38 Large signal pulse response 39 - 46 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 5 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com TYPICAL CHARACTERISTICS OUTPUT VOLTAGE SWING vs FREE-AIR TEMPERATURE 14 9 VCC = 15 V No Load 8 13 VCC = 15 V RL = 150 12.5 ICC - Supply Current - mA VO - Output Voltage Swing - V 13.5 CURRENT SUPPLY vs FREE-AIR TEMPERATURE 12 4 3.5 VCC = 5 V No Load 3 VCC = 5 V RL = 150 2.5 2 -40 -20 0 40 20 60 VCC = 15 V 7 6 VCC = 10 V 5 VCC = 5 V 4 80 3 -40 100 60 Figure 3. INPUT BIAS CURRENT vs FREE-AIR TEMPERATURE INPUT OFFSET VOLTAGE vs FREE-AIR TEMPERATURE 80 100 0 IIB+ VCC = 5 V -1 VCC = 15 V -1.5 VCC = 5 V -0.2 VIO - Input Offset Voltage - mV I IB - Input Bias Current - A 40 Figure 2. IIB+ IIB- -2 VCC = 15 V -2.5 -20 0 20 40 60 80 VCC = 5 V -0.4 -0.6 VCC = 15 V -0.8 -1 Gain = 1 RF = 1 k IIB- 100 -1.2 -40 TA - Free-Air Temperature - C Figure 4. 6 20 TA - Free-Air Temperature - C -0.5 -3 -40 0 -20 TA - Free-Air Temperature - C -20 0 20 40 60 80 100 TA - Free-Air Temperature - C Figure 5. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 TYPICAL CHARACTERISTICS (continued) COMMON-MODE REJECTION RATIO vs COMMON-MODE INPUT VOLTAGE COMMON-MODE REJECTION RATIO vs COMMON-MODE INPUT VOLTAGE 80 TA = -40C 70 CMRR - Common-Mode Rejection Ratio - dB CMRR - Common-Mode Rejection Ratio - dB 80 TA = 85C TA = 25C 60 50 40 VCC = 15 V 30 TA = -40C 70 TA = 85C TA = 25C 60 50 40 30 VCC = 5 V 20 0 2 4 6 8 10 12 14 0 0.5 |VIC| - Common-Mode Input Voltage - V 3 Figure 7. COMMON-MODE REJECTION RATIO vs FREQUENCY TRANSRESISTANCE vs FREE-AIR TEMPERATURE 3.5 4 2.8 VCC = 15 V 2.6 VCC = 5 V VCC = 15 V 2.4 60 50 40 30 1 k 2.2 2 VCC = 10 V 1.8 1.6 1 k 20 - + VI 0 1k 2.5 2 |VIC| - Common-Mode Input Voltage - V 70 10 1.5 Figure 6. Transresistance - M CMRR - Common-Mode Rejection Ratio - dB 80 1 1 k 10k 1.4 VO 1 k 100k 1.2 1M 10M 100M VCC = 5 V VO = VCC/2 RL = 1 k 1 -40 -20 0 20 40 60 80 100 TA - Free-Air Temperature - C f - Frequency - Hz Figure 8. Figure 9. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 7 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com TYPICAL CHARACTERISTICS (continued) CLOSED-LOOP OUTPUT IMPEDANCE vs FREQUENCY 1 VO 750 750 1 k - 0.1 + 50 VI THS3001 1000 VO Zo = -1 VI ( 0.01 100k 10M 100M f - Frequency - Hz In+ 10 1k 10k Figure 10. Figure 11. POWER SUPPLY REJECTION RATIO vs FREQUENCY POWER SUPPLY REJECTION RATIO vs FREE-AIR TEMPERATURE VCC = 15 V VCC = 15 V VCC = 5 V +PSRR 30 20 G=1 RF = 1 k 10k 100k 1M 100k 90 VCC = 5 V 10M 100M 85 VCC = -5 V VCC = -15 V 80 VCC = +5 V 75 VCC = +15 V 70 -40 -20 0 20 40 60 80 100 TA - Free-Air Temperature - C f - Frequency - Hz Figure 12. 8 100 f - Frequency - Hz 40 0 1k 10 1G -PSRR 10 In- Vn 60 50 100 ) 80 70 VCC = 15 V and 5 V TA = 25C 1 1M 90 PSRR - Power Supply Rejection Ratio - dB Vn - Voltage Noise - nV/ Hz and I n - Current Noise - pA/ Hz 10 1000 VCC = 15 V RF = 750 Gain = +2 TA = 25C VI(PP) = 2 V PSRR - Power Supply Rejection Ratio - dB Closed-Loop Output Impedance - 100 VOLTAGE NOISE AND CURRENT NOISE vs FREQUENCY Figure 13. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 TYPICAL CHARACTERISTICS (continued) SLEW RATE vs SUPPLY VOLTAGE SLEW RATE vs OUTPUT STEP 7000 10000 G = +5 RL = 150 tr/tf = 300 ps RF = 1 k SR - Slew Rate - V/s SR - Slew Rate - V/s 6000 +SR 5000 4000 3000 +SR 2000 -SR 1000 VCC = 15 V G = +5 RL = 150 tr/tf = 300 ps RF = 1 k -SR 100 1000 5 7 9 11 13 0 15 5 10 15 20 VO(PP) - Output Step - V |VCC| - Supply Voltage - V Figure 14. Figure 15. SLEW RATE vs OUTPUT STEP NORMALIZED SLEW RATE vs GAIN 2000 1.5 VCC = 5 V VO(PP) = 4 V RL = 150 RF = 1 k tr/tf = 300 ps +SR SR - Normalized Slew Rate - V/ s 1.4 SR - Slew Rate - V/s 1000 -SR VCC = 5 V G = +5 RL = 150 tr/tf = 300 ps RF= 1 k 1.3 1.2 -Gain 1.1 1 +Gain 0.9 0.8 0.7 100 0 1 2 3 4 5 1 2 3 4 5 6 7 8 9 10 G - Gain - V/V VO(PP) - Output Step - V Figure 16. Figure 17. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 9 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com TYPICAL CHARACTERISTICS (continued) HARMONIC DISTORTION vs PEAK-TO-PEAK OUTPUT VOLTAGE SWING HARMONIC DISTORTION vs PEAK-TO-PEAK OUTPUT VOLTAGE SWING -50 -50 8 MHz Gain = 2 VCC = 15 V RL = 150 RF = 750 -60 -60 Harmonic Distortion - dBc Harmonic Distortion - dBc -55 4 MHz Gain = 2 VCC = 15 V RL = 150 RF = 750 -55 3rd Harmonic -65 -70 2nd Harmonic -75 3rd Harmonic -65 -70 -75 -80 2nd Harmonic -85 -80 -90 -85 -95 0 2 4 6 8 10 12 14 16 18 20 0 VO(PP) - Peak-to-Peak Output Voltage Swing - V 6 8 10 12 Figure 18. Figure 19. HARMONIC DISTORTION vs FREQUENCY HARMONIC DISTORTION vs FREQUENCY 14 16 18 20 -60 Gain = 2 VCC = 15 V VO = 2 VPP RL = 150 RF = 750 -65 Harmonic Distortion - dBc Harmonic Distortion - dBc 4 VO(PP) - Peak-to-Peak Output Voltage Swing - V -70 -75 2 -80 3rd Harmonic -85 -90 2nd Harmonic -95 -70 Gain = 2 VCC = 5 V VO = 2 VPP RL = 150 RF = 750 -75 -80 -85 2nd Harmonic -90 -95 3rd Harmonic -100 100k 1M 10M -100 100k f - Frequency - Hz 10M f - Frequency - Hz Figure 20. 10 1M Figure 21. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 TYPICAL CHARACTERISTICS (continued) DIFFERENTIAL GAIN vs LOADING DIFFERENTIAL GAIN vs LOADING 0.04 0.04 Gain = 2 RF = 750 40 IRE NTSC Modulation Worst Case: 100 IRE Ramp Gain = 2 RF = 750 40 IRE PAL Modulation Worst Case: 100 IRE Ramp 0.03 Differential Gain - % Differential Gain - % 0.03 VCC = 15 V 0.02 VCC = 5 V 0.01 VCC = 15 V 0.02 VCC = 5 V 0.01 0 0 1 2 3 4 5 6 7 8 1 2 Number of 150 Loads 4 5 6 7 8 Number of 150 Loads Figure 22. Figure 23. DIFFERENTIAL PHASE vs LOADING DIFFERENTIAL PHASE vs LOADING 0.35 0.3 Gain = 2 RF = 750 40 IRE NTSC Modulation Worst Case: 100 IRE Ramp Gain = 2 RF = 750 40 IRE PAL Modulation Worst Case: 100 IRE Ramp 0.3 Differential Phase - Degrees 0.25 Differential Phase - Degrees 3 0.2 0.15 VCC = 15 V 0.1 VCC = 5 V 0.05 0.25 0.2 0.15 VCC = 15 V 0.1 VCC = 5 V 0.05 0 0 1 2 3 4 5 6 7 8 1 Number of 150 Loads 2 3 4 5 6 7 8 Number of 150 Loads Figure 24. Figure 25. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 11 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com TYPICAL CHARACTERISTICS (continued) OUTPUT AMPLITUDE vs FREQUENCY OUTPUT AMPLITUDE vs FREQUENCY 3 Output Amplitude - dB 1 RF = 750 2 1 Output Amplitude - dB 2 3 Gain = 1 VCC = 15 V RL = 150 VI = 200 mV RMS 0 -1 -2 RF = 1 k -3 RF = 1.5 k -1 -2 RF = 1.5 k -5 -5 10M 100M RF = 1 k -3 -4 1M -6 100k 1G Figure 27. OUTPUT AMPLITUDE vs FREQUENCY OUTPUT AMPLITUDE vs FREQUENCY 8 RF = 560 7 Output Amplitude - dB Output Amplitude - dB 9 Gain = 2 VCC = 15 V RL = 150 VI = 200 mV RMS 5 4 RF = 680 3 RF = 1 k 2 5 4 RF = 1 k 2 0 0 100M 1G RF = 750 3 1 10M RF = 560 6 1 1M Gain = 2 VCC = 5 V RL = 150 VI = 200 mV RMS -1 100k f - Frequency - Hz 1M 10M 100M 1G f - Frequency - Hz Figure 28. 12 1G f - Frequency - Hz 6 -1 100k 100M Figure 26. 9 7 10M 1M f - Frequency - Hz 8 RF = 750 0 -4 -6 100k Gain = 1 VCC = 5 V RL = 150 VI = 200 mV RMS Figure 29. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 TYPICAL CHARACTERISTICS (continued) OUTPUT AMPLITUDE vs FREQUENCY NORMALIZED OUTPUT RESPONSE vs FREQUENCY 3 70 2 50 Normalized Output Response - dB Output Amplitude - dB 60 VCC = 15 V 40 30 VCC = 5 V 20 10 0 G = +1000 RF = 10 k RL = 150 VO = 200 mV RMS -10 100k 0 -1 RF = 680 -2 -3 RF = 1 k -4 100M -6 100k 1G Figure 31. NORMALIZED OUTPUT RESPONSE vs FREQUENCY NORMALIZED OUTPUT RESPONSE vs FREQUENCY 3 Gain = -1 VCC = 5 V RL = 150 VI = 200 mV RMS RF = 390 RF = 560 Normalized Output Response - dB Normalized Output Response - dB 1G f - Frequency - Hz 0 -1 RF = 750 -2 -3 RF = 1 k -4 -5 -6 100k 100M Figure 30. 3 1 10M 1M f - Frequency - Hz 2 RF = 560 -5 10M 1M 1 Gain = -1 VCC = 15 V RL = 150 VI = 200 mV RMS 1M 10M 100M 1G 0 RF = 560 -3 RF = 1 k -6 -9 -12 Gain = +5 VCC = 15 V RL = 150 VO = 200 mV RMS -15 100k f - Frequency - Hz 1M 10M 100M 1G f - Frequency - Hz Figure 32. Figure 33. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 13 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com TYPICAL CHARACTERISTICS (continued) NORMALIZED OUTPUT RESPONSE vs FREQUENCY -3 RF = 390 VI = 500 mV 2 -6 0 -9 VI = 250 mV Output Level - dBV Normalized Output Response - dB 4 SMALL AND LARGE SIGNAL FREQUENCY RESPONSE -2 RF = 620 -4 -6 RF = 1 k -8 -12 -15 VI = 125 mV -18 -21 VI = 62.5 mV -10 -24 Gain = +5 VCC = 5 V RL = 150 VO = 200 mV RMS -12 -14 100k 1M -27 10M 100M -30 100k 1G Gain = 1 VCC = 15 V RF = 1 k RL = 150 f - Frequency - Hz SMALL AND LARGE SIGNAL FREQUENCY RESPONSE SMALL SIGNAL PULSE RESPONSE VI - Input Voltage - mV Figure 35. 0 VI = 250 mV -6 -9 VI = 125 mV VO - Output Voltage - V Output Level - dBV -3 -12 -15 VI = 62.5 mV -24 100k Gain = 2 VCC = 15 V RF = 680 RL = 150 1M 10M 100M 1G 300 100 -100 -200 200 100 0 Gain = 1 VCC = 5 V RL = 150 RF = 1 k tr/tf = 300 ps -100 -200 -300 0 f - Frequency - Hz 10 20 30 40 50 60 70 80 90 100 t - Time - ns Figure 36. 14 1G f - Frequency - Hz VI = 500 mV -21 100M Figure 34. 3 -18 10M 1M Figure 37. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 TYPICAL CHARACTERISTICS (continued) LARGE SIGNAL PULSE RESPONSE VI - Input Voltage - V 60 20 -20 -60 200 VO - Output Voltage - V VO- Output Voltage - mV VI - Input Voltage - mV SMALL SIGNAL PULSE RESPONSE 100 0 Gain = 5 VCC = 5 V RL = 150 RF = 1 k tr/tf = 300 ps -100 -200 3 1 -1 -3 2 1 0 -1 -2 -3 -300 0 10 20 30 40 50 60 70 80 Gain = +1 VCC = 15 V RL = 150 RF = 1 k tr/tf= 2.5 ns 90 100 0 10 20 30 50 60 70 80 Figure 38. Figure 39. LARGE SIGNAL PULSE RESPONSE LARGE SIGNAL PULSE RESPONSE VI - Input Voltage - V 3 1 -1 -3 2 VO - Output Voltage - V VI - Input Voltage - V t - Time - ns VO - Output Voltage - V 40 1 0 Gain = 1 VCC = 5 V RL = 150 RF = 1 k tr/tf= 2.5 ns -1 -2 90 100 t - Time - ns -3 3 1 -1 -3 10 5 0 Gain = +5 VCC = 15 V RL = 150 RF = 1 k tr/tf= 300 ps -5 -10 -15 0 10 20 30 40 50 60 70 80 90 100 0 t - Time - ns 10 20 30 40 50 60 70 80 90 100 t - Time - ns Figure 40. Figure 41. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 15 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com TYPICAL CHARACTERISTICS (continued) LARGE SIGNAL PULSE RESPONSE VI - Input Voltage - V 600 200 -200 -600 2 VO - Output Voltage - V VO - Output Voltage - V VI - Input Voltage - mV LARGE SIGNAL PULSE RESPONSE 1 0 Gain = 5 VCC = 5 V RL = 150 RF = 1 k tr/tf= 300 ps -1 -2 3 1 -1 2 1 Gain = -1 VCC = 15 V RL = 150 RF = 1 k tr/tf= 2.5 ns 0 -1 -2 -3 -3 0 10 20 30 40 50 60 70 80 0 90 100 10 20 30 70 80 LARGE SIGNAL PULSE RESPONSE LARGE SIGNAL PULSE RESPONSE VI - Input Voltage - mV Figure 43. 3 1 -1 2 1 VO - Output Voltage - V VI - Input Voltage - V VO - Output Voltage - V 60 Figure 42. Gain = -1 VCC = 5 V RL = 150 RF = 1 k tr/tf= 300 ps 0 -1 -2 -3 10 20 30 40 50 60 90 100 70 80 90 100 600 200 -200 -600 2 1 0 Gain = -5 VCC = 5 V RL = 150 RF = 1 k tr/tf= 300 ps -1 -2 -3 0 t - Time - ns 10 20 30 40 50 60 70 80 90 100 t - Time - ns Figure 44. 16 50 t - Time - ns t - Time - ns 0 40 Figure 45. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 TYPICAL CHARACTERISTICS (continued) VO - Output Voltage - V VI - Input Voltage - V LARGE SIGNAL PULSE RESPONSE 3 1 -1 -2 10 5 0 Gain = -5 VCC = 15 V RL = 150 RF = 1 k tr/tf= 300 ps -5 -10 -15 0 10 20 30 40 50 60 70 80 90 100 t - Time - ns Figure 46. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 17 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com APPLICATION INFORMATION THEORY OF OPERATION The THS3001 is a high-speed, operational amplifier configured in a current-feedback architecture. The device is built using a 30-V, dielectrically isolated, complementary bipolar process with NPN and PNP transistors possessing fTs of several GHz. This configuration implements an exceptionally high-performance amplifier that has a wide bandwidth, high slew rate, fast settling time, and low distortion. A simplified schematic is shown in Figure 47. VCC+ 7 IIB IN+ 3 2 IN- 6 OUT IIB 4 VCC- Figure 47. Simplified Schematic 18 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 RECOMMENDED FEEDBACK AND GAIN RESISTOR VALUES The THS3001 is fabricated using Texas Instruments 30-V complementary bipolar process, HVBiCOM. This process provides the excellent isolation and extremely high slew rates that result in superior distortion characteristics. As with all current-feedback amplifiers, the bandwidth of the THS3001 is an inversely proportional function of the value of the feedback resistor (see Figures 26 to 34). The recommended resistors for the optimum frequency response are shown in Table 1. These should be used as a starting point and once optimum values are found, 1% tolerance resistors should be used to maintain frequency response characteristics. For most applications, a feedback resistor value of 1 k is recommended - a good compromise between bandwidth and phase margin that yields a stable amplifier. Consistent with current-feedback amplifiers, increasing the gain is best accomplished by changing the gain resistor, not the feedback resistor. This is because the bandwidth of the amplifier is dominated by the feedback resistor value and internal dominant-pole capacitor. The ability to control the amplifier gain independent of the bandwidth constitutes a major advantage of current-feedback amplifiers over conventional voltage-feedback amplifiers. Therefore, once a frequency response is found suitable to a particular application, adjust the value of the gain resistor to increase or decrease the overall amplifier gain. Finally, it is important to realize the effects of the feedback resistance on distortion. Increasing the resistance decreases the loop gain and increases the distortion. It is also important to know that decreasing load impedance increases total harmonic distortion (THD). Typically, the third-order harmonic distortion increases more than the second-order harmonic distortion. Table 1. Recommended Resistor Values for Optimum Frequency Response GAIN RF for VCC = 15 V 1 1 k RF for VCC = 5 V 1 k 2, -1 680 750 2 620 620 5 560 620 OFFSET VOLTAGE The output offset voltage, (VOO) is the sum of the input offset voltage (VIO) and both input bias currents (IIB) times the corresponding gains. The following schematic and formula can be used to calculate the output offset voltage: Figure 48. Output Offset Voltage Model Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 19 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com NOISE CALCULATIONS Noise can cause errors on small signals. This is especially true for amplifying small signals coming over a transmission line or an antenna. The noise model for current-feedback amplifiers (CFB) is the same as for voltage feedback amplifiers (VFB). The only difference between the two is that CFB amplifiers generally specify different current-noise parameters for each input, while VFB amplifiers usually only specify one noise-current parameter. The noise model is shown in Figure 49. This model includes all of the noise sources as follows: * en = Amplifier internal voltage noise (nV/Hz) * IN+ = Nonverting current noise (pA/Hz) * IN- = Inverting current noise (pA/Hz) * eRx = Thermal voltage noise associated with each resistor (eRx = 4 kTRx) RS eRs en Noiseless + _ eni IN+ eno eRf RF eRg IN- RG Figure 49. Noise Model The total equivalent input noise density (eni) is calculated by using the following equation: e Where: ni + en ) IN ) 2 R S 2 ) IN- R F o R G 2 ) 4 kTRs ) 4 kT R o R F G k = Boltzmann's constant = 1.380658 x 10-23 T = Temperature in degrees Kelvin (273 +C) RF || RG = Parallel resistance of RF and RG To get the equivalent output noise of the amplifier, just multiply the equivalent input noise density (eni) by the overall amplifier gain (AV). e no + e ni A V + e ni 1 ) RF (Noninverting Case) RG As the previous equations show, to keep noise at a minimum, small value resistors should be used. As the closed-loop gain is increased (by reducing RG), the input noise is reduced considerably because of the parallel resistance term. This leads to the general conclusion that the most dominant noise sources are the source resistor (RS) and the internal amplifier noise voltage (en). Because noise is summed in a root-mean-squares method, noise sources smaller than 25% of the largest noise source can be effectively ignored. This can greatly simplify the formula and make noise calculations much easier. 20 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 SLEW RATE The slew rate performance of a current-feedback amplifier, like the THS3001, is affected by many different factors. Some of these factors are external to the device, such as amplifier configuration and PCB parasitics, and others are internal to the device, such as available currents and node capacitance. Understanding some of these factors should help the PCB designer arrive at a more optimum circuit with fewer problems. Whether the THS3001 is used in an inverting amplifier configuration or a noninverting configuration can impact the output slew rate. As can be seen from the specification tables as well as some of the figures in this data sheet, slew-rate performance in the inverting configuration is faster than in the noninverting configuration. This is because in the inverting configuration the input terminals of the amplifier are at a virtual ground and do not significantly change voltage as the input changes. Consequently, the time to charge any capacitance on these input nodes is less than for the noninverting configuration, where the input nodes actually do change in voltage an amount equal to the size of the input step. In addition, any PCB parasitic capacitance on the input nodes degrades the slew rate further simply because there is more capacitance to charge. Also, if the supply voltage (VCC) to the amplifier is reduced, slew rate decreases because there is less current available within the amplifier to charge the capacitance on the input nodes as well as other internal nodes. Internally, the THS3001 has other factors that impact the slew rate. The amplifier's behavior during the slew-rate transition varies slightly depending upon the rise time of the input. This is because of the way the input stage handles faster and faster input edges. Slew rates (as measured at the amplifier output) of less than about 1500 V/s are processed by the input stage in a linear fashion. Consequently, the output waveform smoothly transitions between initial and final voltage levels. This is shown in Figure 50. For slew rates greater than 1500 V/s, additional slew-enhancing transistors present in the input stage begin to turn on to support these faster signals. The result is an amplifier with extremely fast slew-rate capabilities. Figure 50 and Figure 51 show waveforms for these faster slew rates. The additional aberrations present in the output waveform with these faster-slewing input signals are due to the brief saturation of the internal current mirrors. This phenomenon, which typically lasts less than 20 ns, is considered normal operation and is not detrimental to the device in any way. If for any reason this type of response is not desired, then increasing the feedback resistor or slowing down the input-signal slew rate reduces the effect. SLEW RATE VI - Input Voltage - V VI - Input Voltage - V SLEW RATE 4 2 0 10 2 0 -2 5 VO - Output Voltage - V 5 VO - Output Voltage - V 4 SR = 1500 V/s Gain = 5 VCC = 15 V RL = 150 RF = 1 k tr/tf = 10 ns 0 -5 -10 -15 0 20 40 60 80 100 120 140 160 180 200 SR = 2400 V/s Gain = 5 VCC = 15 V RL = 150 RF = 1 k tr/tf = 5 ns 0 -5 -10 -15 0 t - Time - ns 20 40 60 80 100 120 140 160 180 200 t - Time - ns Figure 50. Figure 51. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 21 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com DRIVING A CAPACITIVE LOAD Driving capacitive loads with high-performance amplifiers is not a problem as long as certain precautions are taken. The first is to realize that the THS3001 has been internally compensated to maximize its bandwidth and slew-rate performance. When the amplifier is compensated in this manner, capacitive loading directly on the output will decrease the device's phase margin leading to high-frequency ringing or oscillations. Therefore, for capacitive loads of greater than 10 pF, it is recommended that a resistor be placed in series with the output of the amplifier, as shown in Figure 52. A minimum value of 20 should work well for most applications. For example, in 75- transmission systems, setting the series resistor value to 75 both isolates any capacitance loading and provides the proper line impedance matching at the source end. 1 k 1 k Input _ 20 Output THS3001 + CLOAD Figure 52. Driving a Capacitive Load 22 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 PCB DESIGN CONSIDERATIONS Proper PCB design techniques in two areas are important to ensure proper operation of the THS3001. These areas are high-speed layout techniques and thermal-management techniques. Because the THS3001 is a high-speed part, the following guidelines are recommended. * Ground plane - It is essential that a ground plane be used on the board to provide all components with a low inductive ground connection, but should be removed from below the output and negative input pins as noted below. * The DGN package option includes a thermal pad for increased thermal performance. When using this package, it is recommended to distribute the negative supply as a power plane, and tie the thermal pad to this supply with multiple vias for proper power dissipation. It is not recommended to tie the thermal pad to ground when using split supply (V) as this will cause worse distortion performance than shown in this data sheet. * Input stray capacitance - To minimize potential problems with amplifier oscillation, the capacitance at the inverting input of the amplifiers must be kept to a minimum. To do this, PCB trace runs to the inverting input must be as short as possible, the ground plane must be removed under any etch runs connected to the inverting input, and external components should be placed as close as possible to the inverting input. This is especially true in the noninverting configuration. An example of this can be seen in Figure 53, which shows what happens when a 1-pF capacitor is added to the inverting input terminal. The bandwidth increases at the expense of peaking. This is because some of the error current is flowing through the stray capacitor instead of the inverting node of the amplifier. Although, while the device is in the inverting mode, stray capacitance at the inverting input has a minimal effect. This is because the inverting node is at a virtual ground and the voltage does not fluctuate nearly as much as in the noninverting configuration. This can be seen in Figure 54, where a 10-pF capacitor adds only 0.35 dB of peaking. In general, as the gain of the system increases, the output peaking due to this capacitor decreases. While this can initially look like a faster and better system, overshoot and ringing are more likely to occur under fast transient conditions. So proper analysis of adding a capacitor to the inverting input node should be performed for stable operation. OUTPUT AMPLITUDE vs FREQUENCY OUTPUT AMPLITUDE vs FREQUENCY 1 7 1 k Cin Output Amplitude - dB 5 Vin Vout - + 4 50 3 RL = 150 1 0 -1 -3 CI = Stray C Only -1 2 -2 CI = 10 pF 0 Output Amplitude - dB 6 CI = 1 pF Cin -2 Vin -3 50 -4 1 k Vout - + -5 RL = 150 -6 CI = 0 pF (Stray C Only) Gain = 1 VCC = 15 V VO = 200 mV RMS -4 100k 1M 10M 100M -7 1G Gain = -1 VCC = 15 V VO = 200 mV RMS -8 100k 1M 10M 100M 1G f - Frequency - Hz f - Frequency - Hz Figure 53. * 1 k Figure 54. Proper power-supply decoupling - Use a minimum 6.8-F tantalum capacitor in parallel with a 0.1-F ceramic capacitor on each supply terminal. It may be possible to share the tantalum among several amplifiers depending on the application, but a 0.1-F ceramic capacitor should always be used on the supply terminal of every amplifier. In addition, the 0.1-F capacitor should be placed as close as possible to the supply terminal. As this distance increases, the inductance in the connecting etch makes the capacitor less effective. The designer should strive for distances of less than 0.1 inch between the device power terminal and the ceramic capacitors. Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 23 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com THERMAL INFORMATION The THS3001 incorporates output-current-limiting protection. Should the output become shorted to ground, the output current is automatically limited to the value given in the data sheet. While this protects the output against excessive current, the device internal power dissipation increases due to the high current and large voltage drop across the output transistors. Continuous output shorts are not recommended and could damage the device. Additionally, connection of the amplifier output to one of the supply rails (VCC) is not recommended. Failure of the device is possible under this condition and should be avoided. But, the THS3001 does not incorporate thermal-shutdown protection. Because of this, special attention must be paid to the device's power dissipation or failure may result. The thermal coefficient JA is approximately 169C/W for the SOIC 8-pin D package. For a given JA, the maximum power dissipation, shown in Figure 55, is calculated by the following formula: T P D + -T MAX A q JA Where: PD TMAX TA JA = Maximum power dissipation of THS3001 (watts) = Absolute maximum junction temperature (150C) = Free-ambient air temperature (C) = Thermal coefficient from die junction to ambient air (C/W) PD - Maximum Power Dissipation - W 1.5 SOIC-D Package: JA = 169C/W TJ = 150C No Airflow 1 0.5 0 -40 -20 0 20 40 60 80 100 TA - Free-Air Temperature - C Figure 55. Maximum Power Dissipation vs Free-Air Temperature 24 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 GENERAL CONFIGURATIONS A common error for the first-time CFB user is the creation of a unity gain buffer amplifier by shorting the output directly to the inverting input. A CFB amplifier in this configuration will oscillate and is not recommended. The THS3001, like all CFB amplifiers, must have a feedback resistor for stable operation. Additionally, placing capacitors directly from the output to the inverting input is not recommended. This is because, at high frequencies, a capacitor has a low impedance. This results in an unstable amplifier and should not be considered when using a current-feedback amplifier. Because of this, integrators and simple low-pass filters, which are easily implemented on a VFB amplifier, have to be designed slightly differently. If filtering is required, simply place an RC-filter at the noninverting terminal of the operational-amplifier (see Figure 56). RG RF f V O + V I - VO + VI R1 *3 dB + 1 2pR1C1 R 1) R F G 1 1 ) sR1C1 C1 Figure 56. Single-Pole Low-Pass Filter If a multiple-pole filter is required, the use of a Sallen-Key filter can work well with CFB amplifiers. This is because the filtering elements are not in the negative feedback loop and stability is not compromised. Because of their high slew rates and high bandwidths, CFB amplifiers can create accurate signals and help minimize distortion. An example is shown in Figure 57. C1 + _ VI R1 R1 = R2 = R C1 = C2 = C Q = Peaking Factor (Butterworth Q = 0.707) R2 f C2 RG RG = RF + *3 dB ( 1 2pRC RF 1 2- Q ) Figure 57. 2-Pole Low-Pass Sallen-Key Filter There are two simple ways to create an integrator with a CFB amplifier. The first, shown in Figure 58, adds a resistor in series with the capacitor. This is acceptable because at high frequencies, the resistor is dominant and the feedback impedance never drops below the resistor value. The second, shown in Figure 59, uses positive feedback to create the integration. Caution is advised because oscillations can occur due to the positive feedback. C1 RF V RG - VI + VO O + VI THS3001 S ) RF1C1 RG S R F Figure 58. Inverting CFB Integrator Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 25 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com RG RF For Stable Operation: - THS3001 VO + R2 R1 || RA ( 1+ VO VI R1 R2 RF RG RF RG sR1C1 ) VI C1 RA Figure 59. Noninverting CFB Integrator The THS3001 may also be employed as a good video distribution amplifier. One characteristic of distribution amplifiers is the fact that the differential phase (DP) and the differential gain (DG) are compromised as the number of lines increases and the closed-loop gain increases (see Figures 22 to 25 for more information). Be sure to use termination resistors throughout the distribution system to minimize reflections and capacitive loading. 750 750 75 - 75- Transmission Line VO1 + VI 75 75 THS3001 N Lines 75 VON 75 Figure 60. Video Distribution Amplifier Application 26 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 THS3001 www.ti.com................................................................................................................................................. SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009 EVALUATION BOARD An evaluation board is available for the THS3001 (THS3001EVM). The board has been configured for low parasitic capacitance in order to realize the full performance of the amplifier. A schematic of the evaluation board is shown in Figure 61. The circuitry has been designed so that the amplifier may be used in either an inverting or noninverting configuration. For more detailed information, refer to the THS3001 EVM User's Guide (literature number SLOU021). The evaluation board can be ordered online through the TI web site, or through your local TI sales office or distributor. VCC+ + C2 0.1 F C1 6.8 F R1 1 k IN + R2 49.9 + R3 49.9 OUT THS3001 _ R5 1 k + C4 0.1 F C3 6.8 F IN - R4 49.9 VCC - Figure 61. THS3001 Evaluation Board Schematic Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 27 THS3001 SLOS217H - JULY 1998 - REVISED SEPTEMBER 2009................................................................................................................................................. www.ti.com REVISION HISTORY NOTE: Page numbers for previous revisions may differ from page numbers in the current version. Changes from Revision G (March, 2008) to Revision H ................................................................................................. Page * Updated document format to current standards ................................................................................................................... 1 * Deleted references to HV version in SOIC package; this version is not available ............................................................... 2 * Updated information about THS3001EVM availability ........................................................................................................ 27 28 Submit Documentation Feedback Copyright (c) 1998-2009, Texas Instruments Incorporated Product Folder Link(s): THS3001 PACKAGE OPTION ADDENDUM www.ti.com 20-Aug-2011 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing Pins Package Qty Eco Plan (2) Lead/ Ball Finish MSL Peak Temp THS3001CD ACTIVE SOIC D 8 75 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDG4 ACTIVE SOIC D 8 75 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDGN ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDGNG4 ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDGNR ACTIVE MSOPPowerPAD DGN 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDGNRG4 ACTIVE MSOPPowerPAD DGN 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDR ACTIVE SOIC D 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001CDRG4 ACTIVE SOIC D 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001HVCDGN ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001HVCDGNG4 ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001HVIDGN ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001HVIDGNG4 ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001ID ACTIVE SOIC D 8 75 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001IDG4 ACTIVE SOIC D 8 75 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001IDGN ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001IDGNG4 ACTIVE MSOPPowerPAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001IDGNR ACTIVE MSOPPowerPAD DGN 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM Addendum-Page 1 (3) Samples (Requires Login) PACKAGE OPTION ADDENDUM www.ti.com Orderable Device 20-Aug-2011 Status (1) Package Type Package Drawing Pins Package Qty Eco Plan (2) Lead/ Ball Finish MSL Peak Temp THS3001IDGNRG4 ACTIVE MSOPPowerPAD DGN 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001IDR ACTIVE SOIC D 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM THS3001IDRG4 ACTIVE SOIC D 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM (3) Samples (Requires Login) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. Addendum-Page 2 PACKAGE MATERIALS INFORMATION www.ti.com 14-Jul-2012 TAPE AND REEL INFORMATION *All dimensions are nominal Device THS3001CDGNR Package Package Pins Type Drawing MSOPPower PAD SPQ Reel Reel A0 Diameter Width (mm) (mm) W1 (mm) B0 (mm) K0 (mm) P1 (mm) W Pin1 (mm) Quadrant DGN 8 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1 THS3001CDR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 THS3001IDGNR MSOPPower PAD DGN 8 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1 THS3001IDR SOIC D 8 2500 330.0 12.4 6.4 5.2 2.1 8.0 12.0 Q1 Pack Materials-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 14-Jul-2012 *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) THS3001CDGNR MSOP-PowerPAD DGN 8 2500 358.0 335.0 35.0 THS3001CDR SOIC D 8 2500 367.0 367.0 35.0 THS3001IDGNR MSOP-PowerPAD DGN 8 2500 358.0 335.0 35.0 THS3001IDR SOIC D 8 2500 367.0 367.0 35.0 Pack Materials-Page 2 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46C and to discontinue any product or service per JESD48B. Buyers should obtain the latest relevant information before placing orders and should verify that such information is current and complete. All semiconductor products (also referred to herein as "components") are sold subject to TI's terms and conditions of sale supplied at the time of order acknowledgment. TI warrants performance of its components to the specifications applicable at the time of sale, in accordance with the warranty in TI's terms and conditions of sale of semiconductor products. Testing and other quality control techniques are used to the extent TI deems necessary to support this warranty. Except where mandated by applicable law, testing of all parameters of each component is not necessarily performed. TI assumes no liability for applications assistance or the design of Buyers' products. Buyers are responsible for their products and applications using TI components. To minimize the risks associated with Buyers' products and applications, Buyers should provide adequate design and operating safeguards. TI does not warrant or represent that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right relating to any combination, machine, or process in which TI components or services are used. Information published by TI regarding third-party products or services does not constitute a license to use such products or services or a warranty or endorsement thereof. Use of such information may require a license from a third party under the patents or other intellectual property of the third party, or a license from TI under the patents or other intellectual property of TI. Reproduction of significant portions of TI information in TI data books or data sheets is permissible only if reproduction is without alteration and is accompanied by all associated warranties, conditions, limitations, and notices. TI is not responsible or liable for such altered documentation. Information of third parties may be subject to additional restrictions. Resale of TI components or services with statements different from or beyond the parameters stated by TI for that component or service voids all express and any implied warranties for the associated TI component or service and is an unfair and deceptive business practice. TI is not responsible or liable for any such statements. Buyer acknowledges and agrees that it is solely responsible for compliance with all legal, regulatory and safety-related requirements concerning its products, and any use of TI components in its applications, notwithstanding any applications-related information or support that may be provided by TI. Buyer represents and agrees that it has all the necessary expertise to create and implement safeguards which anticipate dangerous consequences of failures, monitor failures and their consequences, lessen the likelihood of failures that might cause harm and take appropriate remedial actions. Buyer will fully indemnify TI and its representatives against any damages arising out of the use of any TI components in safety-critical applications. In some cases, TI components may be promoted specifically to facilitate safety-related applications. With such components, TI's goal is to help enable customers to design and create their own end-product solutions that meet applicable functional safety standards and requirements. Nonetheless, such components are subject to these terms. No TI components are authorized for use in FDA Class III (or similar life-critical medical equipment) unless authorized officers of the parties have executed a special agreement specifically governing such use. Only those TI components which TI has specifically designated as military grade or "enhanced plastic" are designed and intended for use in military/aerospace applications or environments. Buyer acknowledges and agrees that any military or aerospace use of TI components which have not been so designated is solely at the Buyer's risk, and that Buyer is solely responsible for compliance with all legal and regulatory requirements in connection with such use. TI has specifically designated certain components which meet ISO/TS16949 requirements, mainly for automotive use. Components which have not been so designated are neither designed nor intended for automotive use; and TI will not be responsible for any failure of such components to meet such requirements. Products Applications Audio www.ti.com/audio Automotive and Transportation www.ti.com/automotive Amplifiers amplifier.ti.com Communications and Telecom www.ti.com/communications Data Converters dataconverter.ti.com Computers and Peripherals www.ti.com/computers DLP(R) Products www.dlp.com Consumer Electronics www.ti.com/consumer-apps DSP dsp.ti.com Energy and Lighting www.ti.com/energy Clocks and Timers www.ti.com/clocks Industrial www.ti.com/industrial Interface interface.ti.com Medical www.ti.com/medical Logic logic.ti.com Security www.ti.com/security Power Mgmt power.ti.com Space, Avionics and Defense www.ti.com/space-avionics-defense Microcontrollers microcontroller.ti.com Video and Imaging www.ti.com/video RFID www.ti-rfid.com OMAP Mobile Processors www.ti.com/omap TI E2E Community e2e.ti.com Wireless Connectivity www.ti.com/wirelessconnectivity Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265 Copyright (c) 2012, Texas Instruments Incorporated